EP1935213A1 - Procede pour faire fonctionner un systeme de chauffage par induction - Google Patents

Procede pour faire fonctionner un systeme de chauffage par induction

Info

Publication number
EP1935213A1
EP1935213A1 EP06806263A EP06806263A EP1935213A1 EP 1935213 A1 EP1935213 A1 EP 1935213A1 EP 06806263 A EP06806263 A EP 06806263A EP 06806263 A EP06806263 A EP 06806263A EP 1935213 A1 EP1935213 A1 EP 1935213A1
Authority
EP
European Patent Office
Prior art keywords
voltage
wave
induction coil
switching means
transistor
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP06806263A
Other languages
German (de)
English (en)
Other versions
EP1935213B1 (fr
Inventor
Wilfried Schilling
Ralf Dorwarth
Martin Volk
Tobias SCHÖNHERR
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
EGO Elektro Geratebau GmbH
Original Assignee
EGO Elektro Geratebau GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by EGO Elektro Geratebau GmbH filed Critical EGO Elektro Geratebau GmbH
Priority to SI200630281T priority Critical patent/SI1935213T1/sl
Publication of EP1935213A1 publication Critical patent/EP1935213A1/fr
Application granted granted Critical
Publication of EP1935213B1 publication Critical patent/EP1935213B1/fr
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B6/00—Heating by electric, magnetic or electromagnetic fields
    • H05B6/02—Induction heating
    • H05B6/06—Control, e.g. of temperature, of power
    • H05B6/062—Control, e.g. of temperature, of power for cooking plates or the like

Definitions

  • the invention relates to a method for operating an induction heating device according to the preamble of claim 1.
  • an induction coil is subjected to an alternating voltage or an alternating current, whereby eddy currents are induced in a cookware to be heated, which is magnetically coupled to the induction coil.
  • the eddy currents cause heating of the cookware.
  • the mains input voltage is usually first rectified by means of a rectifier into a DC supply voltage or DC link voltage and then processed to generate the high-frequency drive voltage with the aid of one or more switching means, generally insulated gate bipolar transistors (IGBT) 1 ,
  • IGBT insulated gate bipolar transistors
  • a first converter variant forms a converter in full-bridge circuit, in which the induction coil and a capacitor are connected in series between two so-called half bridges.
  • the half bridges are each looped between the intermediate circuit voltage and the reference potential.
  • the induction coil and the capacitor form a series resonant circuit.
  • Another converter variant forms a half-bridge circuit of two IGBTs, wherein the induction coil and two capacitors, which are connected in series between the intermediate circuit voltage and the reference potential, form a series resonant circuit.
  • the induction coil is connected to a connection to a connection point of the two capacitors and to its other connection to a connection point of the two IGBTs forming the half-bridge.
  • a variant optimized from a cost point of view uses only one switching means or an IGBT, wherein the induction coil and a capacitor form a parallel resonant circuit. Between the output terminals of the rectifier, parallel to the DC link capacitor, the parallel resonant circuit of induction coil and capacitor are connected in series with the IGBT.
  • the intermediate circuit capacitor charges during a first half-cycle to an open circuit voltage with an amount of a peak value of the mains alternating voltage, for example to 325V at an AC mains voltage of 230V, as soon as these are supplied with mains voltage. If no drive voltage for generating power of the induction coil is generated, that is to block the switching means or IGBTs, the voltage present at the intermediate circuit capacitor remains approximately constant.
  • the inverter that is, when the induction coil is driven to generate an adjustable heating power or applied with an AC voltage flows when turning on the IGBTs or first, a high current from the DC link capacitor in the resonant circuit and by the IGBTs or. This causes audible noise in a cookware heated by the induction heater, for example, in a pot bottom. Furthermore, reduces the life of the acted upon by the high inrush current components.
  • the invention is therefore based on the object of providing a method for operating an induction heating device with a converter, which enables reliable, component-saving and low-noise operation of the induction heater with low noise radiation.
  • the DC link capacitor is discharged to a threshold value by driving the switching means in a time range before a zero crossing of the AC mains voltage before the induction coil is driven to generate an adjustable heating power, wherein even during the discharge a small amount of heating , ,
  • the discharge of the DC link capacitor causes a start of a heating process, i. If the induction coil is to deliver heating power to a cookware, the DC link capacitor is substantially discharged. If at this time the switching means is turned on or conductive, there is no or only a small current pulse through the switching means and the resonant circuit of induction coil and capacitor. Consequently, there is no switch-on noise and the pulse current load of the power components is reduced, which increases their life.
  • the actual heating process can be carried out in a conventional manner, for example, the or the switching means can be controlled with a square wave signal with a working frequency and an associated Hätastwort.
  • the inverter is consequently started up with small currents or voltages in the area of the zero crossing. With the rise of the half-wave after the zero crossing, the inverter can adjust to its, the set heating power corresponding operating point with a working frequency and a duty cycle.
  • the converter is a single-transistor converter.
  • the at least one switching means preferably forms the switching means of the single-transistor converter.
  • the converter is designed in a full-bridge circuit or half-bridge circuit, wherein the at least one switching means is part of a bridge.
  • the time range starts from 1 ms to 5 ms, preferably 2.5 ms, before the zero crossing of the mains alternating voltage.
  • the threshold value is in a range from OV to 20V.
  • the DC link capacitor is discharged to OV. This allows a practically impuls current-free starting of the inverter.
  • the at least one switching means is a transistor, in particular an IGBT.
  • the transistor for discharging the intermediate circuit capacitor is driven during the discharge such that a linear operating state of the transistor is established. Since the transistor does not completely switch through in this operating mode or this operating state, the DC link capacitor is discharged slowly along the mains half-cycle. The resulting currents through the parallel resonant circuit and the transistor remain relatively low, whereby noise is avoided or significantly reduced.
  • the switching means for discharging the DC link capacitor is driven with a pulse width modulated square wave signal.
  • the square-wave voltage signal preferably has a frequency in the range from 20 kHz to 50 kHz, in particular 39 kHz, and / or an on / off ratio in the range from 1/300 to 1/500, in particular 1/378.
  • the frequency and / or the on / off ratio is preferably adapted to an IGBT type used, its drive voltage, a driver circuit used for generating the drive voltage and / or to a capacitance value of the DC link capacitor.
  • the adjustable heating power is generated by means of a half-wave pattern, wherein the intermediate circuit capacitor is discharged before activation of a half-wave.
  • a heating power generation with the help of the half-wave pattern individual half-waves of the AC mains voltage are completely hidden or deactivated, that is not used for heating power generation.
  • 1/3-Netzraumwellen simply one of three consecutive half-waves for power supply to the resonant circuit or the induction coil is used or activated. During the remaining two half-cycles, the switching means remains open, ie no power is fed into the resonant circuit.
  • a 2/3 mains half-wave operation two out of three consecutive half-waves are used or activated for supplying power to the oscillating circuit or the induction coil.
  • power adjustment is done in a conventional manner.
  • Line half-wave operation allows finer resolution of power levels over a wide power setting range.
  • Such a power setting is particularly advantageous for single-transistor converters.
  • an open-circuit voltage for example, 325V at 230V mains voltage, turns on the intermediate circuit capacitor during an inactive half-wave, during which no power is fed into the resonant circuit.
  • no high inrush current occurs during a transition, i. it can also be used in Eintransistorumrichter a half-wave control for power adjustment.
  • one of three or two out of three half waves is activated, i. 1/3 or 2/3 mains half-wave operation is set.
  • FIG. 1 is a circuit diagram of a Eintransistorumrichters, which is operated with the operating method according to the invention
  • FIG. 2 shows timing diagrams of signals of the single-transistor converter of FIG. 1, FIG.
  • FIG. 3 is a circuit diagram of a converter in half-bridge circuit, which is operated by the operating method according to the invention, and ,
  • Fig. 4 is a circuit diagram of an inverter in full bridge circuit, which is operated with the operating method according to the invention.
  • Fig. 1 shows a circuit diagram of an induction heater in the form of a Eintransistorumrichters EU.
  • the induction heating device may also include further, not shown, identically constructed single-transistor converter EU and additional conventional components, such as control elements for power adjustment, etc.
  • the single-transistor converter EU comprises a bridge rectifier GL, which generates an intermediate circuit DC voltage UG from an AC input system voltage UN of 230V, a buffer or intermediate circuit capacitor C1 for stabilizing or buffering the DC intermediate voltage UG, which is connected between output terminals N1 and N2 of the rectifier GL , an inductor L1 and a capacitor C2 which are connected in parallel and form a parallel resonant circuit, a controllable switching means in the form of an IGB transistor T1, which is connected in series with the resonant circuit between the output terminals N1 and N2 of the rectifier GL, a freewheeling diode D1 which is connected in parallel to a collector-emitter path of the IGB transistor T1, and a control unit SE, for example in the form of a microprocessor or a digital signal processor.
  • a control unit SE for example in the form of a microprocessor or a digital signal processor.
  • the control unit SE executes the operating method according to the invention, described below with reference to FIG. 2, for operating the single-turn converter EU and can comprise or be coupled to further actuators and / or sensors, not shown, for example for monitoring the mains voltage.
  • the single-transistor converter EU is operated in 2/3 mains half-wave operation, ie power is fed into the parallel resonant circuit or into the induction coil L1 only during two out of three mains half-cycles.
  • half-waves H2 and H3 are the active half-waves during which power is fed in
  • the mains half-wave H1 is the inactive half-wave during which no power feed takes place.
  • the inactive half-wave H1 locks the IGB transistor T1, up to a transition region or predeterminable Entladezeit Scheme INT 1 during which the DC bus is discharged capacitor C1.
  • UC is a voltage at the collector of the IGB transistor T1 with respect to a reference potential applied to the terminal N1 of the rectifier GL.
  • an open circuit voltage with an amount of a peak value of the mains AC voltage UN at the collector, i. in the illustrated embodiment about 325V.
  • the active half waves H2 and H3 power is fed into the induction coil L1.
  • This can be effected in a conventional manner, for example by driving the IGB transistor T1 with a square-wave voltage signal having a frequency and a duty cycle, which are adjusted depending on the power to be injected during the half-wave.
  • the IGB transistor T1 is driven with a square-wave voltage signal, not shown, with a frequency of about 39 kHz and an on / off ratio of about 1/378.
  • the drive pulses are so short that they are insufficient to clear the charge on the IGB transistor gate.
  • the IGB transistor T1 is therefore not completely turned on, but goes into a linear operation mode.
  • the voltage UC at the collector of the IGB transistor T1, which in this case corresponds to the voltage UG at the intermediate circuit capacitor C1, thereby falls as shown slowly along the network half-wave as an envelope up to about OV.
  • the signal UC is shown with greater temporal resolution. From this the switching frequency of the IGBT of approx. 39kHz becomes visible during the discharging process.
  • FIG. 2 shows the envelope of the resulting voltage UC and a detail enlargement of the signal UC with greater temporal resolution.
  • the voltage UC increases due to the vibration in the parallel resonant circuit to values well above the open circuit voltage.
  • the envelope has a sinusoidal shape, which follows the rectified input AC voltage UN.
  • the course of the voltage UC shown repeats during the half wave H3.
  • the frequency of the drive signal of the IGBT T1 in this operating state is approximately 22 kHz.
  • the IGB transistor T1 is deactivated, whereby the voltage UC rises again to its no-load value of approximately 325V.
  • the discharge process is repeated, as shown for the half-wave H1. The processes described are repeated periodically.
  • the converter circuit can start with small voltages and currents and adjust with the increase of the mains half-wave to its actual operating point of suitable frequency and duty cycle.
  • the discharge frequency and duty cycle can be adjusted to linearly operate the IGB transistor during discharge.
  • FIG. 3 shows a circuit diagram of a converter HU in a half-bridge circuit, which is operated with the operating method according to the invention.
  • Components having an identical function to FIG. 1 are identical in their function. provided with reference numerals. With regard to its functional description, reference is made to FIG.
  • a half-bridge is formed of IGBTs T2 and T3, which are serially connected between the output terminals N1 and N2 of the rectifier GL.
  • Freewheeling diodes D2 and D3 are connected in parallel to an associated collector-emitter path of the IGBTs T2 and T3, respectively.
  • Capacitors C3 and C4 are also serially connected between the output terminals N1 and N2. Between a connection node N3 of the IGBTs T2 and T3 and a connection node N4 of the capacitors C3 and C4, the induction coil L1 is looped. It forms a series resonant circuit together with the capacitors C3 and C4.
  • the IGBTs T2 and T3 are driven by the control unit SE.
  • a power setting can be done in a conventional manner, for example by a frequency adjustment of the control signals generated by the control unit SE IGBTs.
  • the intermediate circuit capacitor C1 and the capacitors C3 and C4 are discharged by driving the IGBTs T2 and T3. This is done analogously to the method described with reference to FIG. 2 by controlling the IGBTs T2 and T3 with square-wave voltage signals of suitable frequency and suitable on / off ratio. Again, the drive pulses are so short that they are insufficient to clear the charge at the respective IGB transistor gate. The IGB transistors T2 and T3 are therefore not completely turned on, but go into a linear operation mode. _
  • FIG. 4 shows a circuit diagram of an inverter VU in full-bridge circuit, which is operated with the operating method according to the invention.
  • Components with an identical function to FIG. 1 are provided with the same reference numerals. With regard to its functional description, reference is made to FIG.
  • a first half-bridge is formed of IGBTs T4 and T5 and a second half-bridge of IGBTs T6 and T7, which are respectively connected in series between the output terminals N1 and N2 of the rectifier GL.
  • Free-wheeling diodes D4 to D7 are connected in parallel with in each case one associated collector-emitter path of the IGBTs T4 to T7.
  • the induction coil L1 and a capacitor C5 are connected in series.
  • the inductor L1 and the capacitor C5 form a series resonant circuit.
  • the IGBTs T4 to T7 are driven by the control unit SE.
  • a power setting can be done in a conventional manner, for example by a frequency adjustment of the control signals generated by the control unit SE IGBTs.
  • the DC link capacitor C1 is discharged by driving the IGBTs T4 to T7.
  • This is done analogously to the method described with reference to FIG. 2 by driving the IGBTs T4 to T7 with square-wave voltage signals of suitable frequency and suitable on / off ratio.
  • the drive pulses are again so short that they are insufficient to clear the charge at the respective IGB transistor gate.
  • the IGB transistors T4 to T7 are therefore not completely turned on, but go into a linear operation mode.
  • all the IGBTs T4 to 17 or only certain IGBTs can be driven in such a way that a current path is formed for discharging the DC link capacitor C1.
  • T4 and T5 only T6 and T7, only T4 and T7 or only T6 and T5 for discharge can be controlled.
  • the mains voltage is 230V and the mains frequency is 50Hz.
  • the operating method shown can be adapted to other mains voltages and mains frequencies.

Landscapes

  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Inverter Devices (AREA)
  • General Induction Heating (AREA)
  • Control Of High-Frequency Heating Circuits (AREA)
  • Rectifiers (AREA)
EP06806263A 2005-10-14 2006-10-13 Procede pour faire fonctionner un systeme de chauffage par induction Active EP1935213B1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
SI200630281T SI1935213T1 (sl) 2005-10-14 2006-10-13 Postopek za obratovanje indukcijske grelne priprave

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102005050038A DE102005050038A1 (de) 2005-10-14 2005-10-14 Verfahren zum Betrieb einer Induktionsheizeinrichtung
PCT/EP2006/009916 WO2007042318A1 (fr) 2005-10-14 2006-10-13 Procede pour faire fonctionner un systeme de chauffage par induction

Publications (2)

Publication Number Publication Date
EP1935213A1 true EP1935213A1 (fr) 2008-06-25
EP1935213B1 EP1935213B1 (fr) 2009-01-28

Family

ID=37667339

Family Applications (1)

Application Number Title Priority Date Filing Date
EP06806263A Active EP1935213B1 (fr) 2005-10-14 2006-10-13 Procede pour faire fonctionner un systeme de chauffage par induction

Country Status (10)

Country Link
US (1) US8415594B2 (fr)
EP (1) EP1935213B1 (fr)
JP (1) JP2009512147A (fr)
CN (1) CN101326857B (fr)
AT (1) ATE422146T1 (fr)
CA (1) CA2625765C (fr)
DE (2) DE102005050038A1 (fr)
ES (1) ES2320594T3 (fr)
SI (1) SI1935213T1 (fr)
WO (1) WO2007042318A1 (fr)

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CN109047786B (zh) * 2018-09-25 2020-11-24 大连理工大学 一种纤维状分裂模式下高效制备3d打印用球形金属粉末的装置及方法
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KR20210123045A (ko) * 2020-04-02 2021-10-13 엘지전자 주식회사 공진형 전력 변환 장치의 구동 개시 시 커패시터를 방전시키는 방법 및 그 공진형 전력 변환 장치
DE102020207103A1 (de) 2020-06-05 2021-12-09 E.G.O. Elektro-Gerätebau GmbH Verfahren zum Betreiben eines Induktionskochfelds und Induktionskochfeld
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US8415594B2 (en) 2013-04-09
CA2625765C (fr) 2015-06-16
SI1935213T1 (sl) 2009-08-31
CA2625765A1 (fr) 2007-04-19
CN101326857A (zh) 2008-12-17
ATE422146T1 (de) 2009-02-15
WO2007042318A1 (fr) 2007-04-19
DE502006002762D1 (de) 2009-03-19
ES2320594T3 (es) 2009-05-25
CN101326857B (zh) 2011-11-23
DE102005050038A1 (de) 2007-05-24
EP1935213B1 (fr) 2009-01-28
JP2009512147A (ja) 2009-03-19
US20080203087A1 (en) 2008-08-28

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