EP1066739B1 - Procede et dispositif permettant de detecter l'effet redresseur apparaissant dans une lampe a decharge - Google Patents

Procede et dispositif permettant de detecter l'effet redresseur apparaissant dans une lampe a decharge Download PDF

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Publication number
EP1066739B1
EP1066739B1 EP98956934A EP98956934A EP1066739B1 EP 1066739 B1 EP1066739 B1 EP 1066739B1 EP 98956934 A EP98956934 A EP 98956934A EP 98956934 A EP98956934 A EP 98956934A EP 1066739 B1 EP1066739 B1 EP 1066739B1
Authority
EP
European Patent Office
Prior art keywords
gas discharge
rectifier effect
lamp
discharge lamp
voltage
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP98956934A
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German (de)
English (en)
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EP1066739A1 (fr
Inventor
Norbert Primisser
Reinhard BÖCKLE
Stefan Koch
Stefan Rhyner
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Tridonic Bauelemente GmbH
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Tridonic Bauelemente GmbH
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Publication of EP1066739A1 publication Critical patent/EP1066739A1/fr
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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
    • H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
    • H05B41/2985—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against abnormal lamp operating conditions

Definitions

  • the present invention relates to a method for detecting the rectification effect occurring in a gas discharge lamp and an electronic ballast for operating at least one gas discharge lamp, with the aid of which a rectification effect occurring in the gas discharge lamp can be detected.
  • gas discharge lamps are operated with the aid of so-called electronic ballasts.
  • Such an electronic ballast is known for example from EP-B1-0338 109.
  • Fig. 10 shows the basic structure of this electronic ballast.
  • the electronic ballast shown in FIG. 10 first comprises a circuit A which is connected to the AC network.
  • This circuit A serves as an RF harmonic filter for reducing the harmonic harmonics of the mains frequency and for radio interference suppression.
  • the circuit A is followed by a rectifier circuit B, which converts the mains voltage into a rectified intermediate voltage and supplies it to an inverter circuit D via a harmonic filter C, which serves to smooth the intermediate voltage.
  • This inverter D serves as a controllable AC voltage source and converts the DC voltage of the rectifier B into a variable AC voltage.
  • the inverter D generally comprises two controllable switches (not shown), for example MOS field-effect transistors. The two switches are connected in the form of a half-bridge circuit and are alternately controlled with the aid of a corresponding bridge driver such that one of the switches is switched on and the other is switched off.
  • the two inverter switches are connected in series between a supply voltage and ground, a load circuit or output circuit E, in which a gas discharge lamp or fluorescent lamp G is arranged, being connected to the common node between the two inverter switches.
  • This output circuit E comprises a series resonance circuit, via which the "chopped" high-frequency AC voltage of the inverter D is fed to the fluorescent lamp G.
  • the lamp electrodes of the fluorescent lamp G are preheated in order to extend the life of the lamp.
  • the preheating can be carried out, for example, with the aid of a heating transformer, the primary winding of which is connected to the series resonant circuit, while the secondary windings of the heating transformer are coupled to the individual lamp filaments. In this way it is possible to supply the lamp filaments with energy even in the ignited mode.
  • the frequency of the alternating voltage supplied by the inverter D is changed in relation to the resonant frequency of the series resonant circuit of the output circuit E such that the voltage applied to the gas discharge lamp G does not cause the lamp to ignite.
  • the electronic ballast has a control circuit F, which monitors various circuit sizes of the electronic ballast and generates a corresponding control signal for the inverter D when a limit value is exceeded, in order to change the frequency of the alternating voltage generated by the inverter D depending on the detected fault .
  • the control circuit F can monitor the lamp voltage, the preheating voltage, the lamp operating current, the impedance phase angle of the output circuit E or the DC voltage generated by the rectifier B and set the inverter frequency such that the lamp voltage, the preheating voltage or the lamp current have a predetermined limit value not exceed, the direct current power taken from the rectifier B is as constant as possible or a capacitive operation of the series resonance output circuit E is avoided.
  • gas discharge lamps due to wear and tear on the heating filaments, have the effect at the end of the life of the gas discharge lamp that the lamp electrodes wear out unevenly over time, ie the removal of the emission layers on the lamp electrodes is different. This different wear of the lamp electrodes creates differences in the emissivity of the two lamp electrodes.
  • This different emissivity means that a higher current flows from one lamp electrode to the other lamp electrode in the corresponding gas discharge lamp than vice versa, so that the time course of the lamp current during a half-wave has an increase.
  • asymmetries arise which not only produce a stronger light flickering at the end of the life of the gas discharge lamp, but even in extreme cases the gas discharge lamp only operates during one half-wave, i.e. allow during the inflated half wave.
  • the gas discharge lamp acts like a rectifier, so that the effect described above is referred to as the "rectification effect".
  • the work function for the electrons is higher on the lamp electrode that has worn out more over time than on the less worn electrode.
  • Work function is generally referred to as the minimum energy required to pull an electron out of a metal, in the present case from the lamp electrode.
  • the dipole layer on the surface of the metal, i.e. the lamp electrode is an important factor in determining the work function.
  • the more worn lamp electrode, which has a higher work function for the electrons, consequently heats up more than the less worn electrode when the gas discharge lamp is started up.
  • the heating of the lamp electrode can become so strong, especially in the case of lamps with a small diameter, that even parts of the lamp glass bulb can melt.
  • the rectifying effect must consequently be recognized and the gas discharge lamp may have to be switched off or its power consumption reduced.
  • the rectification effect can also be recognized by monitoring the peak value of the lamp voltage, since the asymmetries that occur in the lamp current are transmitted to the lamp voltage. If, for example, the lamp voltage exceeds a certain limit value due to the asymmetrical emission of the lamp electrodes, the gas discharge lamp is switched off automatically.
  • the sensitivity of this method is severely limited, since in the event of a fault, ie when the rectification effect occurs, the peak value of the lamp voltage detected is only 60% higher than in normal operation.
  • the lamp voltage also changes when the gas discharge lamp is dimmed, so that if the gas discharge lamp is dimmed, it is erroneously concluded that the rectification effect is present as a result of the increasing lamp voltage. Overall, the detection of the rectification effect with the aid of monitoring the peak value of the lamp voltage is therefore problematic.
  • the rectification effect is a creeping error that occurs with a time delay. It should therefore be ensured that there is no premature conclusion about the presence of a rectifying effect and that there is a corresponding reaction.
  • the present invention is therefore based on the object of proposing a possibility of detecting the rectification effect occurring in a gas discharge lamp, so that the rectification effect can be detected more easily and in particular more precisely.
  • the present invention it is proposed, as in the ballast of EP 0 695 157 A1, to detect and integrate the lamp voltage or a variable dependent thereon.
  • the detected quantity is integrated over a full period or a multiple of the full period, and a presence of a rectification effect is concluded if the integration result deviates from zero as the rectification effect condition. If a DC component is superimposed on the detected lamp voltage or the quantity dependent on it, this DC component is not specified as the target value for the integration result, but not zero.
  • the presence of the rectification effect is only concluded if the integration result deviates 32 times in succession every 255th period of the lamp voltage from the specified setpoint value or from the specified setpoint range.
  • the lamp voltage or the quantity dependent thereon is "integrated" in that the duration of the positive half-wave of the detected variable is compared with the duration of the negative half-wave, so that the The presence of a rectification effect is then closed if the difference in the time duration of the positive and negative half-waves exceeds a predetermined tolerance value or tolerance range.
  • a counter can be used which receives a reference clock signal and is then started at the zero crossing of the detected variable in order to count up or down during the subsequent half-wave. When the measured quantity subsequently reaches zero crossing again, the counter begins to count in the opposite direction. In order not to conclude that the rectification effect is present, the counter must have returned to its initial counter reading after a period of the detected quantity or its final counter reading must be within a predetermined tolerance range in the vicinity of the initial counter reading.
  • the electronic ballast shown in FIG. 1 first comprises a circuit A, which is connected on the input side to a supply voltage, for example a mains voltage, and is used for radio interference suppression.
  • the circuit A is constructed in the usual way and includes, for example, capacitive input filters and, if necessary, harmonic chokes.
  • a capacitor C2 and a symmetry transformer L1 are shown only by way of example, it being possible for a surge arrester or a VDR with the designation F1 to be connected in parallel.
  • the circuit B following the circuit A comprises a full-wave rectifier bridge with diodes V1-V4.
  • the rectifier circuit B converts the supply AC voltage present on the input side into a rectified intermediate voltage.
  • the rectifier circuit B can therefore be omitted if the electronic ballast is operated with DC voltage.
  • the following circuit part C serves for harmonic filtering and smoothing the intermediate voltage supplied by the rectifier B.
  • the circuit C shown in FIG. 1 comprises, for example, capacitors C3, C11, a diode V5, a coil L2, a MOS field effect transistor T1 and a control circuit IC1 designed as an integrated circuit.
  • the control circuit IC1 is connected to a supply voltage potential VCC and can be connected to the other circuit elements in such a way that it receives different voltage potentials U or currents I.
  • the structure of the circuit C shown in FIG. 1 is of course to be understood purely by way of example.
  • An inverter circuit D is driven by the harmonic filter C shown in FIG. 1, the essential elements of which are two controllable switches connected in series between a supply voltage line and ground, in the present case Example in the form of MOS field effect transistors T2 and T3.
  • the two inverter switches T2, T3 are connected to form a half bridge and are each controlled, ie opened and closed, with the aid of a control circuit IC2 designed as an integrated circuit.
  • the control circuit IC2 thus also takes on the function of a bridge driver and is connected to or coupled to a corresponding supply voltage line VCC.
  • the inverter circuit D Depending on the rectified intermediate voltage generated by the rectifier circuit B, the inverter circuit D generates an alternating voltage with a variable frequency and / or duty cycle.
  • the inverter D is constructed in the usual way and its function is sufficiently known, so that a further explanation can be dispensed with here. It is only important at this point that the control circuit IC2 controls the two inverter switches T2 and T3 alternately depending on the control signals supplied to them, so that a "chopped", high-frequency AC voltage occurs at the connection point between the two inverter switches T2 and T3.
  • a series resonance output circuit or load circuit E is connected to the inverter D.
  • the load circuit E is designed for the connection of two gas discharge lamps G1, G2 in a tandem configuration.
  • the load circuit E can also be modified such that only one gas discharge lamp or more than two gas discharge lamps can be operated.
  • the load circuit E has a series resonance circuit consisting of a resonance circuit coil L3 and a resonance circuit capacitor C14.
  • This series resonant circuit or the resonant circuit coil L3 is connected to the connection point between the two inverter switches T2 and T3 and the resonant circuit capacitor C14 is arranged such that it is connected in parallel to the gas discharge lamp or gas discharge lamps G1, G2 to be operated.
  • the high-frequency AC voltage generated by the inverter D is supplied to the gas discharge lamps G1 and G2 via the series resonant circuit.
  • the two gas discharge lamps G1 and G2 are connected in a tandem configuration to the load circuit E or the electronic ballast.
  • the upper filament of the upper gas discharge lamp G1 and the lower filament of the lower gas discharge lamp G2 are connected directly to the load circuit E, while the lower filament of the upper gas discharge lamp G1 and the upper filament of the lower one Gas discharge lamp G2 connected to each other and connected to the load circuit E.
  • a heat exchanger L4 is provided according to FIG.
  • the frequency of the alternating voltage supplied by the inverter E is set with respect to the resonant frequency of the series resonant circuit in such a way that the voltage across the resonant circuit capacitor C14 and thus across the gas discharge lamps G1 and G2 does not cause the gas discharge lamps to ignite.
  • an essentially constant preheating current flows through the filaments of the gas discharge lamps G1, G2.
  • FIG. 1 adapts the preheating voltage in the tandem configuration of the gas discharge lamps G1 and G2 shown in FIG. 1.
  • the previously explained principle of preheating can of course also be transferred in a simple manner to the operation of a gas discharge lamp or more than two gas discharge lamps.
  • a parallel configuration or parallel connection of a plurality of gas discharge lamps G1, G2 is also conceivable.
  • the tandem configuration of the gas discharge lamps G1, G2 is shown, since in such a lamp configuration with the help of the electronic ballast shown in Fig. 1, a lamp change of both the upper and the lower gas discharge lamp can advantageously be determined in a simple manner.
  • the lamp change detection is explained in more detail below.
  • Resistor R12 shown in FIG. 1 also serves for the purpose of detecting lamp changes.
  • the frequency of the alternating voltage supplied by the inverter D is shifted into the vicinity of the resonant frequency of the series resonant circuit via the control circuit IC2, as a result of which the voltage across the resonant circuit capacitor C14 and the gas discharge lamps G1, G2 is increased, as a result of which these gas discharge lamps are ignited.
  • the electronic ballast shown in FIG. 1 goes into the actual operating phase, in which the frequency of the alternating voltage supplied by the inverter D is continuously set, for example, in such a way that a lamp current as constant as possible flows through the gas discharge lamps G1, G2 the gas discharge lamps have as constant a lamp voltage as possible.
  • the electronic ballast shown in FIG. 1 goes into the actual operating phase, in which the frequency of the alternating voltage supplied by the inverter D is continuously set, for example, in such a way that a lamp current as constant as possible flows through the gas discharge lamps G1, G2 the gas discharge lamps have as constant a lamp voltage as possible.
  • the 1 has a number of error detectors which determine certain circuit sizes of the electronic ballast, in particular the load circuit E, monitor and, upon detection of a specific fault, bring about a corresponding activation of the inverter D, for example in order to avoid the occurrence of an overvoltage on the gas discharge lamps G2 and G2, a rectification effect in the gas discharge lamps G1, G2 or capacitive operation of the load circuit E.
  • a circuit module which, at the heart, comprises the control circuit IC2 already mentioned and several external components as external circuitry for the control circuit IC2.
  • the main external components are six resistors R10, R13 - R16 and R21, R22 and two capacitors C7 and C17. As shown in Fig. 1, the individual external components are connected to respective input terminals of the control circuit IC2.
  • the external components connected to the control circuit IC2 serve primarily to detect certain circuit sizes of the electronic ballast, so that these can be evaluated in the control circuit IC2.
  • FIG. 2 shows an enlarged representation of the control circuit IC2 shown in FIG. 1 and the external wiring of the individual input connections of the control circuit IC2. Only the essential connections and external components are shown in FIG. 2.
  • the control circuit IC2 is advantageously designed as an application-specific integrated circuit (Application Specific Integrated Circuit, ASIC) and accommodated in a multi-pole SMD housing (Surface Mounted Device).
  • ASIC Application Specific Integrated Circuit
  • the control circuit IC2 is suitable both for the operation of a single lamp output circuit E and for the operation of a load circuit E designed for a tandem configuration shown in FIG. 1 with a plurality of gas discharge lamps.
  • the control circuit IC2 has a plurality of connections which have the following functions.
  • the reference potential, ie the ground potential, for the individual analog and digital function blocks of the control circuit IC2 is applied to the connection GND. From Fig. 1 it can be seen that the ground potential of the entire electronic ballast is grounded via a coupling capacitor C1.
  • the internally generated supply voltage for the individual analog and digital function blocks of the control circuit IC2 is provided at the connection VDD, which is connected to the ground potential via the coupling capacitor C7 (cf. FIG. 1).
  • the connection NP serves, as will be explained in more detail below, for the external setting and detection of the preheating method, ie for the selection between a cold start and warm start operation.
  • connection NP connected externally in such a way that a dynamic choice of the preheating method is possible.
  • the terminal VL1 detects the divided lamp voltage of the gas discharge lamps G1, G2 via the resistors R10 and R14, R15 shown in FIG. 1 and partly in FIG. 2 and thus serves primarily for monitoring the lamp voltage.
  • the connection ILC uses the resistors R13 and R16 shown in FIG. 1 and partly in FIG. 2 to monitor the output circuit or load circuit current (choke current) or to monitor the lamp current flowing through the gas discharge lamps G1, G2 after their ignition by using the shunt resistor R16 to detect a voltage proportional to it and to supply it to the control circuit via the connection ILC.
  • connection VL1 thus serves for voltage monitoring, while the connection ILC serves for current monitoring.
  • the two output connections OUTL and OUTH serve to control the low-lying or high-lying half-bridge switch T3 and T2 shown in FIG. 1.
  • control signals (TTL level) for switching the two inverter switches T2 and T3 on and off are provided at the output connections OUTL and OUTH.
  • the connection VCC of the control circuit IC2 is finally the central supply voltage connection of the control circuit IC2.
  • the supply voltage range can include 10-18V, for example.
  • the control circuit IC2 controls the inverter switches T2 and T3 in such a way that an alternating voltage of variable frequency with an operating frequency range of, for example, 40-80 kHz is generated on the output side by the inverter circuit D.
  • the control circuit IC2 forms the heart of the entire electronic ballast shown in FIG. 1 and accordingly comprises a large number of different functions.
  • the control circuit IC2 can be used to dynamically determine the preheating method for the connected gas discharge lamp (s) and to switch between a cold start and a warm start operation.
  • the control circuit IC2 ensures a defined preheating operation with a defined preheating time and a defined preheating current.
  • the control circuit IC2 likewise ensures a predefined ignition operation with a defined ignition time and a defined ignition voltage. Via the connections ILC or VL1 of the control circuit IC2, for example, the preheating current and the lamp operating current or the lamp voltage can be detected and regulated to a value that is as constant as possible.
  • control circuit IC2 monitors the capacitive operation of the load circuit E via the current connection ILC.
  • the occurrence of a constant light effect in a connected gas discharge lamp G1, G2 can also be recognized via the voltage connection VLI.
  • the occurrence of a Gas defect which leads to an overvoltage on the corresponding gas discharge lamp, is recognized and the electronic ballast is accordingly switched off in this case.
  • a special function of the control circuit IC2 is the detection of a lamp change, the lamp change detection in the tandem configuration shown in FIG. 1 being in particular independent of the changed lamp, ie both a change in the upper gas discharge lamp G1 and the lower gas discharge lamp G2 can be detected.
  • a (preferably digitally implemented) sequence control is implemented in the control circuit IC2, which ensures that the gas discharge lamp (s) connected to the electronic ballast are controlled in accordance with predetermined operating states, whereby from one operating state to a new operating state only when fulfilled at least one specific condition can be changed.
  • operating state-dependent monitoring of certain variables of the electronic ballast is possible, so that different error variables can be monitored and evaluated differently depending on the respective operating state.
  • an event-filtered error evaluation takes place in particular, ie with the help of digital event filters, for example, it is ensured that an error is only concluded if the corresponding error actually occurs several times in succession.
  • control circuit IC2 has further functions, all of which will be explained in more detail below with reference to the accompanying drawing.
  • Fig. 3 shows a block diagram of the internal structure of the control circuit IC2 described above.
  • a module 100 is coupled to the current connection ILC, which is used, among other things, for the previously described current detection and capacitive current detection of the load circuit.
  • the evaluation of the current sensed via the connection ILC is carried out in particular with the aid of a regulator formed by a comparator circuit.
  • this comparator circuit is also supplied and evaluated with the voltage signal received by the voltage connection VL1 of the control circuit IC2 and processed by a module 200.
  • the module 200 is used in particular for detecting the lamp voltage, for rectifying effect detection and for lamp change detection.
  • a further module 300 is coupled to the connection NP, which module is used to detect the warm or cold start operation when preheating the gas discharge lamp (s) to be controlled and to implement a dynamic preheating operation.
  • a voltage regulator module 400 which has an internal voltage regulator, is connected to the supply voltage connections VCC and VDD, which provides a regulated, very precise voltage for the voltage supply of all internal function blocks.
  • Another module 500 serves as a source for all required reference quantities, ie reference voltages and reference currents, in the control circuit IC2.
  • An oscillator 600 serves as an internal clock generator of the control circuit IC2, a time base generator 700 coupled thereto deriving internal time variables for the sequence control of the control circuit IC2, such as the preheating or ignition time, depending on the predetermined clock of the oscillator 600.
  • Another module 800 is used to implement the sequence control of the individual operating states of the entire electronic ballast and interacts closely with another module 900, which is used for measuring phase control.
  • the module 900 is used in particular for event-filtered evaluation of certain error quantities of the electronic ballast and for the measurement phase-dependent control of all switches of the individual function blocks of the control circuit IC2.
  • the sequence controller 800 evaluates the event-filtered status messages of the measurement phase controller 900 and controls the individual operating states of the electronic ballast or the control circuit IC2 depending on the time variables specified by the time base generator 700.
  • the control circuit IC2 has a further module 1000 for controlling the inverter. With the aid of this module 1000, frequency setting signals supplied by the measuring phase control 900 are converted into corresponding control signals for the upper inverter switch (via the output connection OUTH) or the lower inverter switch (via the output connection OUTL).
  • the control circuit IC2 can comprise both analog and digitally implemented function blocks.
  • the digital part of the control circuit IC2 designed as ASIC comprises the time base generator 700, the sequence control 800, the measurement phase control 900 and the inverter control 1000.
  • the control circuit IC2 can be equipped in such a way that the digital part corresponds to the analog part in terms of the area required by the control circuit IC2.
  • FIG. 4 shows a detailed circuit diagram of the current detection module 100 shown in FIG. 3.
  • FIG. 4 also shows the resistors R13 and R16 which are connected externally to the current connection ILC of the control circuit and which are also shown in FIG. 1.
  • a reference current Iref1 is added to the signal detected at the current connection ILC in order to ensure that the signal to be processed by the current detection module 100 is always in the operating voltage range of the control circuit.
  • an integrator circuit 105 is provided, which is used to integrate the input signal supplied to it.
  • the entire function block 105 is implemented in such a way that the integrator function can be used both for measuring the lamp current (via the ILC connection) in normal operation and for identifying rectification effects (via the VL1 connection).
  • the integrator circuit 105 can have sample and hold elements, which sample the input signal of the integrator alternately every period of the internal clock generator (cf. module 600 in FIG. 3). The charge thereby stored in the sample and hold elements is passed on to an integration amplifier of the integrator circuit 105. This process is repeated cyclically.
  • the integrator 105 can have an internal controllable switch which bridges the aforementioned sample and hold elements and is closed during the duration of the offset adjustment of the integrator 105. In this way, any signal, in particular the signal present at the input connection ILC, can be applied to the actual integration amplifier via the switch S105 or a reference voltage potential for rectifying effect detection from the voltage block 200 via the switch S107 during the initialization phase.
  • the actual integration amplifier of the integrator 105 has the task of integrating the current measurement signal at the ILC connection in a time-controlled manner.
  • the switch S105 is closed, while in the case of the rectification effect evaluation the reference potential for the rectification effect evaluation supplied via the switch S107 is applied to the integrator circuit 105.
  • the actual controller is a comparator 103, which carries out the required setpoint / actual value comparison and is connected to the output of integrators 105.
  • the arrangement of this comparator 103 shown in FIG. 4 makes it possible to use the comparator 103 very flexibly.
  • a switch S124 By actuating a switch S124 accordingly, different reference voltages or reference values can be connected or applied to the comparator 103, reference voltages Vref1-Vref6 being shown by way of example in FIG.
  • the reference potential Vref1 and Vref2 corresponds, for example, to a desired preheating voltage during a preheating operating state.
  • the reference voltage Vref1 or Vref2 is thus sent to the comparator with the help of the controllable switch S124 103 is applied so that the non-integrated measurement signal currently present at the ILC connector is compared with the reference value Vref1 or Vref2 respectively applied.
  • the reference potential Vref3 corresponds to the integration start value of the integration amplifier of the integrator 105, so that when this reference potential Vref3 is applied, the comparator 103 can detect the actual change in the integration result.
  • the reference potentials Vref4 or Vref6 can correspond to a positive or negative limit value for the lamp voltage of the connection VL1 supplied and integrated via the switch S107, in order to reliably determine the occurrence of a rectification effect by comparing these two limit values when the integration result is exceeded in the positive or negative direction to be able to recognize.
  • the further reference potential Vref5 is also used, which is added during the rectification effect detection and corresponds to the output or start value for the integration of the lamp voltage supplied via the switch S107.
  • the change in the corresponding integration variable that is actually present relative to the corresponding start value can thus be determined with the aid of the comparator 103.
  • the output signal of the comparator 103 is fed to the measuring phase controller 900 shown in FIG. 3, which evaluates it and evaluates it differently depending on the current measuring phase.
  • the measurement phase controller 900 provides for a corresponding adaptation of the output frequency of the inverter of the electronic ballast if the current measurement signal of the connection ILC monitored by the comparator 103 deviates from the predetermined target value Vref3.
  • the measurement phase control generates an event-filtered signal which indicates whether there is a rectification effect in a connected gas discharge lamp or not. This signal is evaluated by the sequence control block 800 shown in FIG. 3 and used to control the operating state of the entire electronic ballast.
  • the measurement signal present at the connection ILC can also be monitored and evaluated bypassing the integrator circuit 105, e.g. to detect a capacitive operation of the load circuit of the electronic ballast.
  • a detector can be provided for detecting a capacitive current flowing in the load circuit, which for example detects the phase angle of the load circuit, i.e. the phase difference between the load circuit voltage and the load circuit current, determined (capacitive current detection).
  • the result of this monitoring or evaluation can also be fed to the measuring phase controller 900.
  • FIG. 5a shows an enlarged illustration of the essential elements of the inverter D already shown in FIG. 1 and of the load circuit E.
  • FIG. 5a assumes that only one gas discharge lamp G1 is connected to the load circuit.
  • 5a shows the two inverter switches T2 and T3 connected in series.
  • the load circuit with its series resonance circuit is connected to the connection point between the two inverter switches T2 and T3, i.e. the resonance circuit coil L3 is connected in parallel with the resonance circuit capacitor C14 to the lower inverter switch T3.
  • the resonant circuit capacitor C14 is also connected in parallel to the gas discharge lamp G1.
  • Free-wheeling diodes V11 and V12 are connected in parallel to the individual inverter switches T2 and T3 and serve to protect the respective inverter switch.
  • 5b shows on the one hand the switch-on states of the two inverter switches T2 and T3 as well as the current profile of the current I L3 flowing through the choke L3 and the time profile of the voltage potential V L occurring at the connection point between the two inverter switches T2 and T3.
  • a current flows in the freewheeling diode of the inverter switch to be switched on and the inverter half bridge switches the resonant load circuit inductively, ie the voltage or potential V L leads the choke current I L3 .
  • the capacitive switching of the resonance load of the resonance load circuit is the capacitive switching of the resonance load of the resonance load circuit.
  • FIG. 5a shows the course of the individual currents I 1 -I 4 that occur during the time intervals t 1 -t 4 shown in FIG. 5b in the case of an inductive or capacitive inductor current I L3 .
  • the level of the current amplitude of the load circuit detected via the input ILC can now be monitored and compared with a fixed, predetermined reference value.
  • the magnitude of the current amplitude is advantageously detected at the time when the lower inverter switch T3 is switched on, since in this case the polarities of the measured values to be recorded are favorable for processing within the control circuit IC2 designed as an ASIC. If the detected current value is below the limit value specified by the corresponding reference potential, the presence of capacitive operation is inferred from the load circuit, and an output signal with a high level can be generated which is evaluated by the measurement phase control block 900 shown in FIG. 3 and finally by the inverter control block 1000, likewise shown in FIG. 3, is converted into control signals for the two inverter switches T2 and T3; that these are switched on and off alternately with an increased frequency in order to increase the working frequency and thus to counteract the capacitive operation.
  • FIG. 6 shows on the one hand the internal structure of the voltage detection block 200 and the external circuitry of the control circuit coupled to the connection VL1 of the voltage detection block 200.
  • a series resistor R10 on the one hand, has the connection VL1 and on the other hand, is coupled to a voltage divider consisting of resistors R14 and R15, the two voltage divider resistors R14 and R15 being connected in parallel to the gas discharge lamp G1 or to the gas discharge lamps G1 and G2 connected in tandem in FIG. 1.
  • FIG. 6 it is assumed in FIG. 6 that, in contrast to FIG. 1, only one gas discharge lamp G1 is actuated, to which the resonant circuit capacitor C14 is also connected in parallel.
  • the two resistors R14 and R15 have the task of dividing down the voltage applied to the gas discharge lamp G1, so that with the help of the resistor R10 acting on the connection point between the resistors R14 and R15, a measurement signal representative of the lamp voltage can be supplied to the voltage terminal VL1 of the voltage detection block 200 ,
  • the three external resistors R10, R14 and R15 are variable, so that - analogously to the power connection ILC (cf. resistors R13, R16) - via a connection of the control circuit completely independently of one another at different times, a total of three different control variables of the electronic ballast Can be set or controlled using one and the same controller.
  • the setpoints for the control of the three different control variables can be set or predefined depending on the lamp type or the electronic ballast type currently being used.
  • the following variables of the electronic ballast can be set with the help of the three external variable resistors R10, R14 and R15: the maximum lamp voltage positive / negative, the amplitude of the AC voltage component of the lamp voltage signal and the signal increase of the lamp voltage signal for rectification effect evaluation.
  • an internal reference current source is again provided, which applies an additional internal current Iref2 to the measurement signal present at the voltage connection VL1.
  • the reference current Iref2 is only activated, ie closed, using the controllable switch S207 during the evaluation of the rectification effect. All other evaluations connected to the VL1 connection relate to the signal present at connection VL1 without an additional reference current Iref2, ie without a DC offset. Accordingly, all other detectors on the VL1 connection are deactivated during the rectification effect evaluation, since they would otherwise give incorrect results.
  • the rectification effect detection is to be explained in more detail with the aid of the present control circuit.
  • gas discharge lamps due to the wear of the heating filament, have the effect at the end of the life of the gas discharge lamps that the lamp electrodes wear out unevenly over time, i.e. the removal of the emission layers on the lamp electrodes is different. Due to the different wear of the lamp electrodes, there are differences in the emissivity of the two lamp electrodes. The result of this is that a higher current flows from one lamp electrode to the other when the corresponding gas discharge lamp is operated than vice versa. The course of the lamp current over time therefore shows an increase in a half-wave.
  • the different removal of the two lamp electrodes thus creates asymmetries which not only lead to a stronger flickering of light at the end of the life of the gas discharge lamp, but even in extreme cases only permit the gas discharge lamp to be operated during one half-wave.
  • the gas discharge lamp acts like a rectifier, so that the effect described above is referred to as the "rectifying effect".
  • the rectification effect explained above also has the consequence that the more worn electrode, which has a higher work function than the other electrode, heats up more than the other electrode when the gas discharge lamp is started up.
  • the work function is generally the minimum energy required to detach an electron from a metal, in the present case from a lamp electrode.
  • the heating of the lamp electrode described above can become so strong, in particular in the case of lamps with a small diameter, that parts of the lamp glass bulb can melt.
  • each controlled lamp is monitored for the occurrence of a rectification effect, so that a reaction can be made accordingly when a rectification effect is detected.
  • the actual rectification effect detection does not take place in the voltage detection block 200 shown in FIG. 6, but in the current detection block 100, since the integrator circuit of the current detection block 100 and the downstream comparator 103 (cf. FIG. 4) are also used for the rectification effect detection , In this way, the number of components required for monitoring the electronic ballast or the gas discharge lamp (s) can be reduced.
  • the switch S207 shown in FIG. 6 is advantageously closed some time before the expected zero crossing of the lamp voltage signal present at the connection VL1, so that transient processes caused by the capacitor C201 cannot additionally falsify the measurement signal.
  • Switch S201 is opened again exactly at the calculated zero crossing of the lamp voltage.
  • the signal present at switch S107 shown in FIGS. 4 and 6 corresponds at this point in time to the AC voltage amplitude at terminal VL1, while the DC component of the signal present at switch S107 corresponds to the reference voltage Vref8 that is switched on.
  • the measurement signal of the connection VL1 prepared in this way is finally fed to the integrator circuit 105 shown in FIG. 4, as has already been explained above.
  • the switching state of the switch S107 is controlled by the measuring phase controller 900 shown in FIG. 3.
  • the individual switches shown in FIG. 4 are closed or opened by the measuring phase controller 900 in such a way that an averaged one is made with the aid of the comparator 103 via the upstream integrator circuit Evaluation of the current measurement signal present at connection ILC or of the voltage measurement signal present at connection VL1 is possible.
  • the comparator 103 can also be connected directly to the current measurement connection ILC, bypassing the integrator circuit, in order thus to evaluate or regulate the peak value of the current measurement signal at the connection ILC.
  • the measurement phase controller 900 specifies which of the measurement or control states described above is to be assumed.
  • the rectification effect detection principle implemented in the present control circuit IC2 provides that the lamp voltage detected via the voltage connection VL1 is integrated with the aid of the integrator circuit of the current detection block 100 shown in FIG. 4, and then the deviation from a predetermined desired value is evaluated.
  • the measurement signal corresponding to the lamp voltage is integrated over a full period or a multiple of a full period of the lamp voltage, and then the deviation of the integration result from the original integration start value is evaluated.
  • the comparator 103 is supplied with the integration start value by applying the corresponding reference potential Vref5.
  • the comparator 103 can also be given a positive limit value or a negative limit value for the rectification effect detection in the form of the further reference potentials Vref4 or Vref6.
  • the potential Vref5 can be, for example, 3.0V, while a value of 4.0V can be used as the positive reference potential Vref4 and a value of 2.0V can be used as the negative reference potential Vref6.
  • the output signal of the comparator shown in FIG. 4 is in turn fed to the measurement phase controller 900 which, after detection of a rectification effect, outputs a corresponding status message or error message to the sequence controller 800 shown in FIG. 3.
  • the measurement phase controller 900 carries out an event-filtered revision of this error message and ensures that an error message indicating the rectification effect is only output to the sequence controller 800 if the rectification effect occurs continuously over a long period of time. In principle, this applies not only to the error message indicating a rectification effect, but also to all error or output from the measuring phase controller 900 to the sequence controller 800.
  • the measuring phase controller 900 only outputs a rectification effect error message to the sequence controller 800 if a rectification effect is detected 32 times in succession every 255th period of the lamp voltage by the comparator 103 shown in FIG. 4. As soon as no rectification effect has been detected during a period of the lamp voltage, the counter of the measuring phase control 900 assigned to the rectification effect is reset to zero and the evaluation of the rectification effect error signal of the comparator 103 is started again.
  • the occurrence of a rectification effect is only taken into account in the operating state of the electronic ballast, since for example during the preheating phase the occurrence of a rectification effect should not result in the system being switched off.
  • the rectification effect detection takes place in particular in that clock pulses of a (high-frequency) reference clock are counted and compared with one another during the individual half-waves of the lamp voltage or the quantity dependent thereon, the clock pulses counted as a function of the duration of the respective half-wave are. If there is no rectification effect, the clock pulses counted during the positive and negative half-waves match. In contrast, if there is a rectification effect, the clock pulses counted during the positive and negative half-waves differ from one another.
  • 11a shows a circuit implementation of this exemplary embodiment with an up / down counter 107, which receives a UZERO signal as the actual input signal and further receives a high-frequency reference clock signal CLK, for example with the frequency 10 MHz, as well as a reset or reset signal as control signals ,
  • the signal UZERO assumes a positive and otherwise a negative voltage level during each positive half-wave of the lamp voltage present at the connection VL1 and thus detects the zero crossing of the lamp voltage.
  • the counter 107 is started at the zero crossing of the lamp voltage and counts either up or down during the subsequent half-wave of the lamp voltage. Reaches the measurement signal, ie the lamp voltage, after a Half-cycle again the zero crossing, the counting direction of the counter 107 is reversed. After a full period of the lamp voltage has elapsed, the current counter reading N of the counter 103 is connected to a comparator, which can be formed, for example, by the comparator 103 already described above. This comparator 103 compares the current counter reading N with the initialization value or the original counter reading of the counter 107. If there is no rectification effect, the counter reading N must have reached the output value N 0 again after the next zero crossing of the lamp voltage.
  • the comparator 103 advantageously compares the counter reading N with the initial value N 0 within certain tolerance limits, in order not to prematurely conclude that there is a rectification effect.
  • the output signal of the comparator 103 is fed via a D flip-flop 108 clocked by a latch signal to the measuring phase controller 900, which - as has been described above - evaluates this signal and in particular carries out an event-filtered evaluation, ie only then concludes that there is a rectification effect , if, for example, a rectification effect is reported by the comparator 103 32 times in succession every 255th period of the lamp voltage.
  • the zero crossing signal UZERO can originate, for example, from a further comparator 203, which monitors the voltage measuring signal present at the voltage connection VL1 with regard to its zero crossing.
  • the entire integrated measuring system of the control circuit IC2 is cyclically synchronized with respect to the zero point of the lamp voltage.
  • the synchronization advantageously takes place every second period of the output frequency.
  • An exception to this principle is the rectification effect evaluation. In this case, the synchronization is delayed by two further periods over a full period of the lamp voltage due to the integration carried out for the rectification effect evaluation.
  • the output signal of the zero crossing comparator 203 is also fed to the measuring phase control 900 and is of central importance for the control of all controllable switches of the entire control circuit, the actuation of which is controlled in each case to the zero crossing of the lamp voltage.
  • FIG. 11 b shows a representation of the signal profiles in the circuit shown in FIG. 11 a in the absence of a rectification effect and the states that occur in the process.
  • the zero crossing signal UZERO assumes the positive level during the positive half-wave of the lamp voltage U VL1 and the counter 107 has its counter reading N based on the initialization value N0 reduced according to the reference clock CLK until there is a new zero crossing of the lamp voltage U VL1 .
  • the counter reading N is then increased again.
  • the latch signal After a period of the lamp voltage U VL1 , the latch signal outputs the output value of the comparator 103 to the measuring phase controller 900 via the D flip-flop 108, and then the counter 107 is reset to the initial value N 0 using the reset signal.
  • the counter reading N of the counter 107 again corresponds to the output value N 0 , so that the comparator 103 reports no rectification effect.
  • 11c and 11d show courses of the counter reading N if there is a rectification effect, the counter reading N being greater than N 0 according to FIG. 11c or smaller than N 0 according to FIG. 11d after a complete period of the lamp voltage U VL1 , and thus the comparator 103 recognizes and reports the rectification effect by comparing N with N 0 .
  • the comparison of the comparator N advantageously takes place within predetermined tolerance limits, which are defined by threshold values N S1 and N S2 according to FIG. 11d, ie the comparator 103 only outputs an output signal corresponding to the rectification effect if the following condition is not fulfilled: N S2 ⁇ N ⁇ N S1 .
  • the threshold values are advantageously selected asymmetrically in such a way that the distance between N S1 and N 0 is greater than the distance between N 0 and N S2 (in particular twice as large), since the control behavior of the electronic ballast occurs when the rectification effect shown in FIG. 11d occurs always tries to compensate for the associated decrease in current by changing the frequency.
  • the sensitivity for the rectification effect detection at counter readings N which are below the output value N 0 after a full period of the lamp voltage U VL1 is increased and the threshold value N S2 is shifted closer to the output value N 0 .
  • a further function block for overvoltage detection of the lamp voltage can be connected to the voltage connection VL1 (cf. the arrow shown in FIG. 6), the output signal of this function block also being able to be fed to the measuring phase control 900 and, for example, again event-filtered (cf. the rectification effect evaluation explained above). leads to a corresponding error message to the sequencer 800.
  • the voltage detection block 200 shown in FIG. 6 comprises a further function block which is provided for the detection of a lamp change.
  • This functional block comprises a sampling circuit 201, a switch S206 and a comparator 202.
  • This lamp change detection circuit enables a change in both the upper gas discharge lamp G1 and the lower gas discharge lamp G2 shown in FIG. 1 to be detected.
  • any gas discharge lamp G1, G2 connected to the electronic ballast As soon as a lamp change has been recognized, this is communicated via the measuring phase controller 900 shown in FIG. 3 to the sequence controller 800 also shown schematically in FIG. 3, so that it can automatically restart the system after notification of a lamp change.
  • a lamp change is particularly suitable if a lamp error, such as a gas defect, has been determined and reported by the control circuit. In this case, the installer will try to replace the faulty lamp. Initially, however, the fitter does not know which of the gas discharge lamps G1, G2 connected to the electronic ballast is faulty. He will therefore replace one of these connected gas discharge lamps.
  • the sequence control 800 shown in FIG. 3 will restart the system. If a lamp fault is still detected or all the connected gas discharge lamps cannot be ignited, the control circuit switches back to an error or lamp change detection state without the connected gas discharge lamps being able to be operated continuously. For the fitter, this means that the gas discharge lamp he has replaced was either not faulty or there is another faulty gas discharge lamp. In this case, the fitter has to replace another gas discharge lamp connected to the electronic ballast.
  • a lamp change is recognized in that a supply voltage of a certain frequency is applied to the load circuit by the inverter and the transient response of the load circuit is evaluated in this regard.
  • the transient response of the load circuit is in turn assessed on the basis of the measurement signal present at the voltage connection VL1 and proportional to the lamp voltage, this measurement signal being sampled several times and thus the characteristic curve of the lamp voltage resulting from the applied supply voltage being assessed.
  • the supply voltage applied to the load circuit in lamp change detection mode has, in particular, a relatively low frequency of, for example, 40 Hz.
  • only one of the two inverter switches T2, T3 (cf. FIG. 1) is switched on or off alternately with the aforementioned frequency in the lamp change detection mode, while the other inverter switch remains permanently open during the lamp change mode.
  • it is the upper inverter switch T2 that is permanently open, while the lower inverter switch T3 is alternately switched on and off with the low repetition frequency of approximately 40 Hz.
  • the function of the lamp change detection circuit shown in Fig. 6 is as follows.
  • the lower inverter switch T3 of the inverter D shown in FIG. 1 is switched on and off with a low repetition frequency of approximately 40 Hz, while the upper inverter switch T2 remains permanently switched off. Because of the input and Switching off the inverter switch T3 results in a certain transient response in the load circuit of the electronic ballast, which depends in particular on the gas discharge lamps connected to the electronic ballast. This transient response of the load circuit is reflected in the measurement signal detected via the input connection VL1, which is evaluated by the lamp change detection circuit.
  • the sampling circuit 201 stores the current voltage value of the measurement signal present at the connection VL1 at certain times T 1 -T 3 .
  • the third measurement at time T 3 is not absolutely necessary, but it does increase the reliability of the measurement against interference. The measurement process described above takes place after the inverter switch T3 has been opened and before it has been closed again.
  • the result is temporarily stored in the downstream digital part (not shown in FIG. 6).
  • the lamp change detection circuit is then reinitialized, ie a specific reference voltage Vref11 is switched on via switch S206 and a new sample value of the voltage signal at terminal VL1 is buffered in the sampling circuit 201.
  • the comparator 202 thus carries out a double relative evaluation of the sample values stored in the sampling circuit 201, that is to say the difference between the sample value stored at time T 1 and the sample value stored at time T 2 and the difference between that at time T 1 recorded sample value and the sample value stored at time T 3 .
  • This evaluation of the relative relationships between the individual sample values is advantageous compared to the evaluation of absolute measured variables, since additional components would be required to evaluate absolute measured variables.
  • FIG. 7a shows a time diagram of the profile of the voltage U VL1 present at the connection VL1, the switching state of the inverter switch T3 and the switching state of the switch S206 shown in FIG. 6. Furthermore, the individual sampling times T 1 , T 2 and T 3 are indicated in FIG. 7a.
  • the evaluation of the comparison result provided by the comparator 202 between the samples at times T 1 and T 2 or T 1 and T 3 takes place in the measuring phase controller 900.
  • the transient process that is to say on the basis of the sample values at times T 1 - T 3 formed voltage characteristic
  • 7b shows an example of the course of the characteristic curve of the voltage signal U VL1 present at the connection VL1 for three different cases.
  • the characteristic curve a corresponds to the characteristic curve that arises when the upper gas discharge lamp G1 shown in FIG. 1 changes.
  • the characteristic curve b corresponds to the characteristic curve when changing the lower gas discharge lamp G2 during the lamp change detection operation.
  • the third characteristic curve c shown in FIG. 7b corresponds to the characteristic curve in normal operation without a lamp change, ie in the event that all lamps are connected.
  • control circuit IC2 will monitor the transient behavior with regard to the occurrence of the characteristic curves a or b when a lamp fault occurs in an error state. As soon as the voltage present at connection VL1 runs according to one of these characteristics, this means that one of the connected gas discharge lamps has been removed from its version for troubleshooting.
  • the control circuit IC2 or sequence control 800 then changes into the actual lamp change detection state, in which, as in the fault state, only the lower inverter switch T3 is opened and closed, for example at 40 Hz, while the upper inverter switch T2 is permanently open. In this state, the control circuit IC2 waits for the appearance of the characteristic curve c, d. H. that a replacement lamp has been used instead of the removed lamp and now all lamps are reconnected. The system then restarts or restarts. This process will be explained again later with reference to FIG. 9.
  • FIG. 8a and 8b show two variants of the circuit 300 shown in FIG. 3 for detecting a warm / cold start operation. Both variants have in common that the voltage potential present at the connection NP of the control circuit is always evaluated and a comparison is made with a predetermined reference voltage Vref12 to determine whether a warm or cold start should be carried out. This comparison is made with the help a comparator 301 performed, the positive measurement input is connected to the terminal NP. On the output side, the comparator 301 is connected to a state hold circuit 302, which can be implemented, for example, by a D flip-flop. This state hold circuit 302 has the effect that the output signal of the comparator 301 is only switched through and evaluated to the sequence control 800 if a corresponding enable signal EN is present.
  • This enable signal EN only briefly assumes a high level when the entire system is restarted or restarted, for example by actuating a corresponding mains switch. At no later point in time does a signal change at the NP port result in a state change at the output port of the state hold circuit 302.
  • FIG. 8b shows a variant of the circuit explained above, which enables a dynamic switchover between a warm and cold start operation.
  • the circuit shown in Fig. 8b corresponds essentially to the circuit shown in Fig. 8a, with the exception, however, that a switch S301 is provided internally at the input terminal NP, via which the supply voltage potential VDD can be applied to the input terminal NP, while externally an RC element consisting of the resistor R22 and capacitor C17 already shown in FIGS. 1 and 2 is connected to the connection NP.
  • the voltage potential present at the input connection NP is monitored by the comparator 301.
  • the operation of the circuit shown in Fig. 8b is as follows.
  • the switch S301 is closed so that the capacitor C17 is charged by the supply voltage potential VDD applied to the input terminal NP. If the system is switched off (e.g. due to a fault) or the system supply is switched from mains to emergency power operation, switch S301 is opened and capacitor C17 discharges with the time constant defined by the RC element.
  • the RC element is advantageously designed such that the capacitor C17 can hold the charge so long that the voltage applied to the input connection NP is greater than the reference voltage Vref12 applied to the comparator 301 for up to 400 ms.
  • the enable signal EN of the state hold circuit 302 assumes a high level, so that the comparison result of the comparator 301 is switched through. If at this point in time the voltage potential present at the input connection NP is still greater than the reference voltage Vref12, the sequence control 800 ensures the start-up of the connected gas discharge lamps without preheating operation and thus carries out a cold start. On the other hand, if the voltage potential present at the input connection NP is less than the reference potential Vref12, the connected gas discharge lamps are preheated and a warm start is carried out.
  • the voltage potential present at the input terminal NP of the control circuit depends on the on-time of the switch S301, which is equivalent to the operating time of the electronic ballast. This variable is decisive for the state of charge of the capacitor C17. Furthermore, the voltage potential at the input connection NP depends on the switch-off time of the switch S301 or the duration of the emergency power operation of the electronic ballast and the time constant of the RC element. These variables are decisive for the discharge process of the capacitor C17.
  • the circuit shown in FIG. 8b therefore performs a cold or warm start depending on the duration of the switch-off time and on the time constant of the RC element.
  • the switch-off time period can be specified which is just sufficient for a cold start operation of the connected lamps.
  • the RC element only has to be dimensioned such that, after charging the capacitor C17 and opening the switch S301, the voltage potential applied to the input terminal NP is greater than the reference potential just after the aforementioned switch-off period Vref12 of the comparator 301.
  • the maximum permissible time between switching to emergency power operation and restarting or restarting the electronic ballast without preheating the lamp electrodes is set to 400 ms. Accordingly, the resistor R22 and the capacitor C17 are to be dimensioned in such a way that the aforementioned period of 400 ms can be observed.
  • any other energy storage circuit can be used which stores energy depending on the supply voltage potential present at the input terminal NP and discharges with a certain time constant after the supply voltage potential has been disconnected ,
  • This energy storage circuit can thus contain any delay elements, as long as there is a defined and known temporal behavior of the delay element or the energy storage circuit.
  • the function blocks 400 and 500 shown in FIG. 3 will be explained in more detail below.
  • the voltage regulator function block 400 generates an internally regulated, very precise supply voltage VDD for all internal function blocks, which at the same time represents the source for all required reference voltages.
  • this internal supply voltage VDD is applied to the outside via the connection VDD and filtered via the external capacitor C7 with good high-frequency properties. Due to the provision of the internal supply voltage VDD, a single low-voltage level can be used for all functional parts of the entire electronic ballast, which is particularly advantageous for cost reasons.
  • the reference voltage generator 500 serves for the central generation of all reference quantities for the control circuit IC2, i.e. to generate all reference potentials and reference currents.
  • the oscillator 600 shown in FIG. 3 represents the central clock source for the entire control circuit IC2.
  • the oscillator 600 is constructed in such a way that no external components are required.
  • the basic clock of the oscillator is set with the help of micro fuses to the desired value of, for example, 10 MHz with an accuracy of z. B. 4-bit matched.
  • the frequency of the clock generator can be reduced to approximately 1/20 of the nominal clock rate, ie to approximately 550 kHz, via a digital input of the oscillator 600. As will be explained in more detail below, this reduced clock rate is used for certain operating states, in particular for the fault and Lamp change detection state needed in which the supply energy must be reduced.
  • the time base generator 700 likewise shown in FIG.
  • the sequence control function block 800 receives, for example, all the time reference quantities from the time base generator 700. All the time quantities generated by the time base generator 700 are a multiple of the basic clock of the oscillator 600. The time reference quantities generated by the time base generator 700 can include, for example, the individual preheating times or the ignition time. As will be explained in more detail below, these temporal reference variables are of particular importance for the temporal operating state control of the control circuit IC2, which is carried out by the sequence control function block 800.
  • sequence controller 800 The function of the sequence controller 800 will be explained in more detail below with reference to FIG. 9.
  • the sequence control function block 800 controls the operation of the electronic ballast, for example in accordance with the state diagram shown in FIG. 9. 9, each possible operating state is illustrated by a circle, while the individual arrows represent possible changes in state which occur when a condition associated with the two operating states is met. These conditions are in each case linked to specific states of certain state or monitoring variables of the electronic ballast or the lamp (s), these monitoring variables being processed internally by the sequence control 800 in the form of variables which depend on whether the monitoring variable assumes the corresponding state or not, for example assumes the value "1" when the assigned state is taken or "0" when the state is not taken.
  • the individual variables monitored by the sequence controller 800 can include, for example, time-based variables or error variables.
  • the course of a commissioning time, a preheating time, an ignition time or a delay time for the rectification effect detection can be monitored.
  • the error quantities for example, the occurrence of a capacitive current in the load circuit (via the current detection block 100), the presence of an overvoltage at the connected gas discharge lamp, the occurrence of a rectification effect or asymmetrical lamp operation, the absence of a lamp or the occurrence of a synchronization error with regard to the zero crossing the Lamp voltage (each via the voltage detection block 200) are monitored.
  • the output signal of the function block 300 can be monitored, with the aid of which a distinction can be made between a warm and a cold start operation. Any other monitoring parameters of the electronic ballast are of course also conceivable.
  • the individual error quantities are detected by the blocks 100-300 shown in FIG. 3, but processing is first carried out by the measuring phase control function block 900 before the individual error quantities are actually evaluated by the sequence control 800.
  • the measurement phase control contains a digital event filter assigned to the corresponding error size for each monitored error size.
  • this digital event filter performs the function of a counter which counts the uninterrupted occurrence of the corresponding error.
  • An error message is only passed on to the sequence control 800 by the corresponding event filter when the corresponding error has occurred n times in succession, where n corresponds to the filter depth of the corresponding digital event filter and can be different for each error size.
  • the sequence controller 800 does not react prematurely to the occurrence of a specific error, and an operating state change as a result of a specific error message is only carried out when it can be assumed with a relatively high degree of certainty that the corresponding error actually exists.
  • a special feature in this regard is the digital event filter for the rectification effect detection, since the rectification effect is a gradual, that is, slowly occurring, error.
  • the event filter assigned to the rectification effect is therefore dimensioned in such a way that a rectification effect only occurs and a corresponding error message is output to the sequential control unit 800 if the measuring phase control 900 reports a rectification effect 32 times in succession every 255th period of the lamp voltage.
  • a filter depth of 64 for the detection of an overvoltage a filter depth of 3 and for the detection of a synchronization error as well as for the lamp change detection each one Filter depth of 7 can be provided.
  • other filter depth values are also conceivable.
  • the corresponding error message from the measurement phase control 900 to the sequence control 800 after passing through the correspondingly assigned event filter is meant.
  • the initial state of the operating state control shown in FIG. 9 is the so-called. Reset state (state I).
  • the system is in state I whenever the electronic ballast has been started or restarted, which is synonymous with the occurrence of the enable signal EN explained with reference to FIG. 8.
  • the sequence controller 800 can comprise a hysteresis comparator, which monitors the external supply voltage signal VCC within certain limits and generates the enable signal EN if the supply voltage signal VC is within the required supply voltage range. In this way, the comparator also monitors the switching on and off of the entire system.
  • the enable signal EN can thus occur asynchronously to all other signals depending on the switching on and off of the overall system, with after the appearance of the enable signal EN, i.e.
  • the individual function blocks of the control circuit IC2 are compared. This adjustment is carried out by reading in the respective values for the individual micro fuses. These micro fuses are small fuses that are used, for example, to balance the individual internal power sources. Furthermore, as has been explained with reference to FIG. 8, when the enable signal EN occurs, the output signal of the function block 300 shown in FIG. 3 is read in, so that it is determined at this point in time whether the connected gas discharge lamps with a cold or warm start in To be put into operation. Overall, in state I the control circuit IC2 is thus initialized.
  • the sequential control system 800 automatically changes to a commissioning state (state II). Exceptionally, the transition from state I to state II is not linked to certain conditions and occurs automatically each time the electronic ballast is restarted or restarted. In state II, the harmonic filter starts up or the load circuit of the electronic ballast settles. Furthermore, the coupling capacitor of the load circuit is precharged in state II. In this phase, all error detectors are deactivated, ie there is no evaluation of the error variables mentioned above.
  • a preheating condition III is started from condition II if e.g. a start-up time assigned to state II, which denotes the normal operating time of state II, has expired and no cold start operation has been reported by function block 300 shown in FIG. 3. If, on the other hand, the start-up time has not yet expired, the system remains in state II, which is shown in FIG. 9 by an arrow starting from state II and returning to state II. If a cold start operation was detected by the function block 300 and the start-up time has already expired, the sequence control 800 changes directly from the state II to an ignition state IV, which corresponds to the previously explained warm start operation.
  • the inverter half bridge is driven in such a way that it oscillates at the upper limit in terms of frequency and generates, for example, an output frequency of approximately 80 kHz.
  • the preheating control, the overvoltage detection and the capacitive current detection can be activated.
  • the working frequency of the inverter of the electronic ballast can be changed depending on the value of the lamp current detected and the states of the overvoltage and capacitive current detection.
  • the controlled variable "lamp current” attempts to initially reduce the output frequency of the inverter, since the detected lamp current is significantly too small compared to the specified setpoint value because the ignition has not yet taken place. This control process is continued until the overvoltage detection or capacitive current detection prevents or counteracts the continuous reduction of the inverter frequency.
  • overvoltage detection will first become dominant as an influencing factor.
  • the lamp voltage is now regulated, as it were.
  • the ignition state IV can only be left in the direction of the previously mentioned operating state V after the specified ignition time has elapsed. This change of state is in particular independent of whether control in the ignition state IV is still based on the ignition voltage or is already based on the lamp current.
  • the mean or effective value of the lamp current is regulated, i.e. the output frequency of the inverter depends on the detected lamp current.
  • Overvoltage, capacitive current and synchronization error detection is activated during this operating state V, the control circuit also carrying out a new setpoint / actual value comparison every second period of the inverter output frequency during this state.
  • the rectification effect detection can also be activated.
  • the operating state V is not limited in time, i.e. is in principle an endless loop and can only be exited when one of the activated error detectors responds. All error detectors of the control circuit are advantageously activated during the operating state V.
  • the fault state VII shown in FIG. 9 is started up.
  • This fault condition VII is therefore the central point of contact for all serious operational disturbances.
  • the Fault state VII is jumped on directly from preheating state III if an overvoltage or a capacitive current operation has been detected during these preheating states.
  • the fault state VII is started from the operating state V if a capacitive current operation, an overvoltage fault, a synchronization fault and / or the occurrence of a rectification effect etc. with respect to the connected gas discharge lamps has been detected during this state.
  • the start-up of the fault state VII can, for example, be associated with a corresponding signaling of the respective fault for the user.
  • Fault status VII is only exited by the sequential control system if, after restarting the system, start-up status II is restarted via reset status I and the gas discharge lamps are started up again.
  • error state VII can be left if it is detected in this state that not all of the lamps connected to the electronic ballast have intact lamp filaments. This is equivalent to leaving the fault state VII in the direction of the lamp change detection state VIII already mentioned as soon as one of the connected gas discharge lamps is removed from its socket.
  • the operating current consumption of the control circuit is reduced to a minimum possible value during the fault state VII.
  • the electronic ballast is operated as in the lamp change detection state, i. H. the lower inverter switch T3 is opened and closed at a low frequency of, for example, 40 Hz, while the upper inverter switch is permanently opened.
  • the control circuit IC2 waits in the fault state VII for the occurrence of the voltage characteristic curves a or b (cf. FIG. 7a) at the voltage measurement connection VL1, which corresponds to the removal of one of the connected gas discharge lamps G1, G2 , In this case, the control circuit IC2 changes to the lamp change detection state VIII.
  • the control circuit can reliably detect both a change or a removal of the upper gas discharge lamp G1 and the lower gas discharge lamp G2 (see FIG. 1) and automatically restart the system after detecting a lamp change. While it is checked in error state VII whether a of the gas discharge lamps has been removed, monitoring is carried out in lamp change detection state VIII to determine whether all gas discharge lamps have been inserted. As soon as it has been recognized that all gas discharge lamps have been inserted, ie all lamp filaments connected to the electronic ballast are intact, the system automatically switches back to commissioning state II and the gas discharge lamps are put into operation again according to the functional circuit shown in FIG. 9. All other fault detectors are also deactivated during lamp change detection state VIII, with the exception of lamp change detection.
  • the inverter control function block 1000 serves to generate control signals for the upper and lower inverter switches T2, T3 (cf. FIG. 1) which are output via the output connections OUTH or OUTL of the control circuit. Depending on these control signals, the two inverter switches are either switched on or opened. As a rule, the inverter control 1000 generates alternating control pulses for the control connections OUTH and OUTL of the two inverter switches T2 and T3 and can furthermore have an internal dead time counter function in order to ensure a sufficient dead time between the activation of the two inverter switches. In lamp change detection state VIII (see FIG. 9), the inverter control 1000 ensures that the upper inverter switch T2 remains permanently open via the upper output connection OUTH, while only the lower inverter switch T3 alternately opens and closes with a relatively low frequency via the lower output connection OUTL becomes.
  • the inverter control 1000 provides in particular for an asymmetrical duty cycle of the inverter switches, but this asymmetry is only 2.1% for an output frequency of the inverter of 43 kHz, for example, and only 4% for an output frequency of 80 kHz, and is therefore hardly significant.
  • the generation of asymmetrical output signals for the two inverter switches leads to an increase in the frequency resolution of the inverter, ie smaller frequency steps of the inverter can be set using the control circuit.
  • the generation of an asymmetrical duty cycle also has the effect that the so-called.
  • "Walmen" of the connected gas discharge lamps can be changed. This heating is an effect of "running layers” that occurs especially at low temperatures shortly after the system is started, which is due to an uneven light distribution in the corresponding gas discharge lamp. These "running layers” consist of light / dark zones that run along the lamp tube at a certain speed. As is known, for example, from EP-B1-0490 329, this running effect can be accelerated by superimposing a small direct current in such a way that it no longer has a disruptive effect.
  • the generation of an asymmetrical duty cycle by the present control circuit of the electronic ballast can also prevent the occurrence of the so-called. Counteracting "Walmens".
  • an asymmetrical duty cycle for the two inverter switches is generated during individual half-periods, although the duty cycle is averaged over an entire period. Since only asymmetrical output signals are to be generated in the operating state V shown in FIG. 9, the inverter control 1000 evaluates, for example, a corresponding control signal which only releases the asymmetrical operation (for example by assuming a high level) if the system is in the operating state V is located.

Landscapes

  • Circuit Arrangements For Discharge Lamps (AREA)
  • Investigating, Analyzing Materials By Fluorescence Or Luminescence (AREA)
  • Discharge Lamp (AREA)

Claims (24)

  1. Procédé pour la détection de l'effet redresseur se produisant dans une lampe à décharge,
    dans lequel on saisit et on intègre la tension de lampe appliquée à une lampe à décharge (G1,G2) à surveiller ou une grandeur dépendante de celle-ci,
       caractérisé en ce que,
    la grandeur saisie est intégrée sur une pleine période ou un multiple de la pleine période de la grandeur saisie et en ce que l'on conclut à la présence d'un effet redresseur dans le cas où, en tant que condition d'effet redresseur, le résultat d'intégration s'écarte d'une valeur nominale déterminée,
    moyennant quoi, l'on ne conclut à la présence de l'effet redresseur que lorsque la condition d'effet redresseur a été satisfaite à plusieurs reprises, de façon consécutive, par tranches régulières.
  2. Procédé selon la revendication 1,
       caractérisé en ce que,
    l'on ne conclut à l'effet redresseur que lorsque le résultat d'intégration dépasse une valeur limite supérieure pré-établie (Vref4) ou descend au-dessous d'une valeur limite inférieure pré-étable (Vref6).
  3. Procédé selon la revendication 1 ou 2,
       caractérisé en ce que,
    la valeur saisie est surveillée et intégrée par un circuit de surveillance (IC2) conçu comme circuit intégré, moyennant quoi pour le traitement de la grandeur saisie, celle-ci est élevée dans la plage de tension de travail du circuit de surveillance (IC2).
  4. Procédé pour la détection de l'effet redresseur se produisant dans une lampe à décharge,
    moyennant quoi on saisit la tension de lampe appliquée à une lampe à décharge à surveiller (G1,G2) ou une grandeur dépendant de celle-ci (Uvl1),
       caractérisé en ce que, l'on ne conclut à la présence d'un effet redresseur que, lorsque comme condition d'effet redresseur la différence entre la durée temporelle de la demi-onde positive et la durée temporelle de la demi-onde négative de la grandeur saisie (Uvl1), dépasse une valeur de seuil déterminée (Ns1,Ns2).
  5. Procédé selon la revendication 4,
       caractérisé en ce que,
    l'on mesure la durée de la demi-onde positive ou négative de la grandeur saisie (Uvl1) de sorte qu'entre les passages par zéro de la grandeur saisie (Uvl1) on compte les impulsions de synchronisation de référence, et
    en ce que l'on conclut à la présence d'un effet redresseur lorsque la différence entre les impulsions de synchronisation de référence de la demi-onde positive et les impulsions de synchronisation de référence de la demi-onde négative de la grandeur saisie (Uvl1) dépasse la valeur de seuil déterminée (Ns1,Ns2).
  6. Procédé selon la revendication 5,
       caractérisé en ce que,
    la comparaison entre les impulsions de synchronisation de référence de la demi-onde positive et de la demi-onde négative de la grandeur saisie (Uvl1) s'effectue de telle sorte qu'un compteur (107) compte dans une direction déterminée en partant d'un état de compteur de départ déterminé pendant une demi-onde de la grandeur saisie (UVL1) et il compte dans une direction opposée pendant la demi-onde consécutive de la grandeur saisie (Uvl1), et en ce que l'on conclut à la présence d'un effet redresseur lorsque la différence entre l'état de compteur (107) après une période de la grandeur saisie (Uvl1) et l'état de compteur de départ (107) dépasse la valeur de seuil déterminée (Ns1,Ns2).
  7. Procédé selon la revendication 6,
       caractérisé en ce que,
    l'on conclut à la présence d'un effet redresseur lorsque la différence entre l'état de compteur du compteur (107) après une période de la grandeur saisie (Uvl1) et l'état de compteur de départ du compteur (107) est supérieure à une valeur de seuil supérieure déterminée (Ns1) ou inférieure à une valeur de seuil inférieure déterminée Ns2),
    moyennant quoi l'écart entre la valeur de seuil supérieure (Ns1) et l'état de compteur de départ est choisi pour être supérieur à l'écart entre l'état de compteur de compteur de départ et la valeur de seuil inférieure (Ns2).
  8. Procédé selon l'une des revendications 4 à 7,
       caractérisé en ce que,
    l'on ne conclut à la présence d'un effet redresseur que lorsque la condition d'effet redresseur a été satisfaite à plusieurs reprises, de façon consécutive, par tranches régulières.
  9. Procédé selon l'une des revendications 1 à 3 ou la revendication 8,
       caractérisé en ce que,
    l'on ne conclut à la présence de l'effet redresseur que lorsque la condition d'effet redresseur apparaît de façon ininterrompue n1-fois consécutivement chaque n2-ième période de la grandeur saisie (Uvl1).
  10. Procédé selon la revendication 9,
       caractérisé en ce que,
    s'applique : n1 = 32 et n2 = 255.
  11. Procédé selon l'une des revendications précédentes,
       caractérisé en ce que,
    la lampe de décharge (G1,G2) est pilotée par un ballast électronique, et
    en ce que pendant une phase de préchauffe pour la préchauffe des boudins de la lampe à décharge (G1,G2) ou pendant une phase d'allumage pour l'allumage de la lampe à décharge (G1,G2), on n'évalue pas la condition d'effet redresseur ou la tension de lampe ou la grandeur en dépendant (Uvl1).
  12. Ballast électronique pour le fonctionnement d'une lampe à décharge,
    avec une source de tension alternative (D),
    avec un circuit de charge (E) connecté à la source de tension alternative (D) d'au moins une lampe à décharge (G1,G2), et
    avec des moyens de détection de l'effet redresseur (IC2) qui saisissent et intègrent une grandeur du circuit de charge (E) qui correspond à ou est dépendant de la tension de la lampe à décharge (G1,G2),
       caractérisé en ce que,
    les moyens de détection de l'effet redresseur (IC2) intègrent la grandeur saisie sur une pleine période ou un multiple de cette pleine période de cette grandeur et concluent à la présence de l'effet redresseur dans la lampe à décharge (G1,G2) lorsque, en tant que condition de l'effet redresseur, le résultat d'intégration s'écarte d'une valeur nominale déterminée,
    moyennant quoi, ils ne concluent à la présence d'un effet redresseur que lorsque la condition d'effet redresseur a été satisfaite à plusieurs fois, de façon consécutive.
  13. Ballast électronique selon la revendication 12,
       caractérisé en ce que,
    les moyens de détection de l'effet redresseur (IC2) présentent des moyens d'intégration (102) pour intégrer la grandeur saisie, et en ce que les moyens de détection de l'effet redresseur (IC2) présentent des moyens de comparateur (103) auxquels sont amenés d'une part, le signal de sortie des moyens d'intégration (102) et d'autre part, une valeur limite supérieure ou inférieure (Vref4, Vref6), moyennant quoi la valeur limite supérieure et inférieure (Vref4, Vref6) définissent le résultat d'intégration.
  14. Ballast électronique selon la revendication 12 ou 13,
       caractérisé en ce que,
    les moyens de détection de l'effet redresseur (IC2) sont conçus sous forme de circuit intégré spécifique à l'application et présentent des moyens d'alignement de crête de signal (S207, Iref2) pour élever le signal de la grandeur saisie dans la plage de la tension de travail du circuit intégré spécifique à l'application (IC2).
  15. Ballast électronique selon la revendication 13 et 14,
       caractérisé en ce que,
    les moyens intégrés (105) sont élevés à la valeur de tension sur laquelle est aligné le signal de la grandeur saisie à l'aide des moyens d'alignement de crête de signal (S207,Iref2).
  16. Ballast électronique pour le fonctionnement d'au moins une lampe à décharge avec une source de tension alternative (D), et
    avec un circuit de charge (E) raccordé à la source de tension alternative (D), qui contient au moins une lampe à décharge (G1,G2), et
    avec des moyens de détection de l'effet redresseur (IC2) qui saisissent une grandeur (Uvl1) du circuit de charge (E) qui correspond à la tension de lampe de la lampe à décharge (G1,G2) ou est dépendante de celle-ci,
       caractérisé en ce que,
    les moyens de détection de l'effet redresseur (IC2) comparent la durée temporelle d'une demi-onde positive avec la durée temporelle d'une demi-onde négative de la grandeur saisie (Uv11) et concluent à la présence de l'effet redresseur dans la lampe à décharge (G1,G2) lorsque, en tant que condition de l'effet redresseur, la différence entre la durée temporelle de la demi-onde positive et la durée temporelle de la demi-onde négative de la grandeur saisie (Uvl1) dépasse une valeur de seuil déterminée (Ns1,Ns2).
  17. Ballast électronique selon la revendication 16,
       caractérisé en ce que les moyens de détection de l'effet redresseur (IC2) comprennent un compteur qui, en partant d'un état de compteur de départ pendant une demi-onde de la grandeur saisie (Uv11) selon un signal de synchronisation de référence (CLK) modifie son état de compteur dans une direction déterminée et pendant la demi-onde consécutive modifie son état de compteur selon le signal de synchronisation de référence (CLK) dans la direction opposée, et
       en ce que les moyens de détection de l'effet redresseur (IC2) comprennent des moyens de comparateur (103) qui comparent l'état de compteur du compteur (107) après une période de la grandeur saisie (Uvl1) avec l'état de compteur de départ et génèrent un signal de sortie indiquant l'effet redresseur lorsque la différence entre l'état de compteur du compteur (107) à l'expiration de la période de la grandeur saisie (Uvl1) et l'état de compteur de sortie dépasse la valeur seuil déterminée (Ns1,Ns2).
  18. Ballast électronique selon la revendication 17,
       caractérisé en ce que,
    les moyens de comparateur (103) génèrent le signal de sortie indiquant l'effet redresseur lorsque la différence entre l'état de compteur du compteur (107) à l'expiration de la période de la grandeur saisie (Uvl1) et l'état de compteur de sortie est supérieure à une valeur seuil supérieure déterminée (Ns1) ou inférieure à une valeur seuil inférieure déterminée (Ns2),
    moyennant quoi l'écart entre la valeur de seuil supérieure (Ns1) et l'état de compteur de sortie est choisi de façon à être supérieur à l'écart entre l'état de compteur de sortie et la valeur de seuil inférieure (Ns2).
  19. Ballast électronique selon l'une des revendications 16 à 18,
       caractérisé en ce que,
    les moyens de détection de l'effet redresseur (IC2) ne concluent plus à la présence de l'effet redresseur que lorsque la condition de l'effet redresseur a été satisfaite plusieurs fois de façon consécutive.
  20. Ballast électronique selon l'une des revendications 12 à 19,
       caractérisé en ce que,
    les moyens de détection de l'effet redresseur (IC2) présentent des moyens (203) pour déterminer le passage par zéro de la grandeur saisie (Uvl1).
  21. Ballast électronique selon l'une des revendications 12 à 20,
       caractérisé en ce que,
    les moyens de détection de l'effet redresseur (IC2) pilotent le service de la lampe à décharge (G1,G2) en fonction de l'état de service,
    moyennant quoi les moyens de détection de l'effet redresseur (IC2) dans un état de préchauffe pilotent la préchauffe des boudins de lampe de la lampe à décharge (G1,G2) et dans un état d'allumage, pilotent l'allumage de la lampe à décharge (G1,G2) et amènent la lampe à décharge (G1,G2) après un allumage satisfaisant, dans un état de service, et
    moyennant quoi les moyens de détection de l'effet redresseur (IC2) n'évaluent la condition de l'effet redresseur ou la grandeur saisie (Uvl1) que dans l'état de service.
  22. Ballast électronique selon la revendication 21,
       caractérisé en ce que,
    les moyens de détection de l'effet redresseur (IC2), après détection de l'effet redresseur d'une lampe à décharge (G1,G2), raccordée au ballast électronique, passent à un état de défaut que les moyens de détection de l'effet redresseur (IC2) ne quittent que lorsqu'une lampe à décharge (G1,G2) raccordée au ballast électronique a été remplacée ou que le ballast électronique a été de nouveau mis en marche.
  23. Ballast électronique selon la revendication 22,
       caractérisé en ce que,
    les moyens de détection de l'effet redresseur (IC2) comprennent des moyens de saisie de changement de lampe (200) pour saisir un remplacement d'une lampe à décharge (G1,G2) raccordée au ballast électronique.
  24. Ballast électronique selon l'une des revendications 12 à 15 ou 19 et l'une des revendications 13, 17 ou 18,
       caractérisé en ce que,
    les moyens de détection de l'effet redresseur (IC2) comprennent des moyens de filtre (90) qui reçoivent un signal de sortie des moyens de comparateur (103) et ne génèrent un signal de sortie indiquant l'effet redresseur que lorsque les moyens de comparateur (103) annoncent plusieurs fois, de façon consécutive, que la condition de redressement a été satisfaite.
EP98956934A 1997-12-23 1998-11-19 Procede et dispositif permettant de detecter l'effet redresseur apparaissant dans une lampe a decharge Expired - Lifetime EP1066739B1 (fr)

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DE19757635 1997-12-23
DE19757635 1997-12-23
DE19829434 1998-07-01
DE19829434 1998-07-01
PCT/EP1998/007428 WO1999034647A1 (fr) 1997-12-23 1998-11-19 Procede et dispositif permettant de detecter l'effet redresseur apparaissant dans une lampe a decharge

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AU1339599A (en) 1999-07-19
WO1999034647A1 (fr) 1999-07-08
US6400095B1 (en) 2002-06-04
NZ505209A (en) 2002-12-20
NO325778B1 (no) 2008-07-14
DE59803245D1 (de) 2002-04-04
EP1066739A1 (fr) 2001-01-10
AU738151B2 (en) 2001-09-13
ATE213901T1 (de) 2002-03-15
DE19882031D2 (de) 2000-10-12
NO20003259L (no) 2000-08-21
NO20003259D0 (no) 2000-06-22

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