CN1512660A - 具有声音输出装置的电子装置 - Google Patents
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Abstract
本发明提供一种具有声音输出装置的电子装置，该声音输出装置具有需要有偏置电压的前置放大器及输出放大器，可以独立地接通关闭输出放大器，同时降低其接通时的电冲击声。具有：前置放大器；输入该前置放大器的输出、能够分别被开关的至少一个输出放大器；生成提供给前置放大器的第1偏置电压的第1偏置电路；包含有电阻及电容器，通过进行动作而生成对应提供给输出放大器的接通信号缓缓增加的第2偏置电压的第2偏置电路。另外，在第2偏置电路中设置有加快偏置电压的上升的加速电路。
Description
技术领域
本发明涉及可降低起动时的电冲击声的具有声音输出装置的电子装置。
背景技术
在具有声音输出装置的电子装置中，为了防止(或降低)对耳朵产生不愉快的电冲击声(所谓砰声)，在起动时，以一定的时间常数使其输出放大电路等的偏压电路缓慢升压。
图12为表示以往的具有声音输出装置的电子装置的构成例的图。在该图中，在声音信号处理IC200中，设置有前置放大器10和输出放大器20、20A，对由信号输入端子Pin所输入的输入信号Vin实施信号处理，由信号输出端子Pout、PoutA将输出信号Vout输出。通过耦合电容器Cc将信号输出端子Pout的输出信号Vout提供给扬声器Sp。另外，信号输出端子PoutA的输出信号比如可用于耳机。
前置放大器10具有运算放大器11、在其输入输出端子之间连接的电阻13、和输入电阻12，将第1偏置电压Vb1提供给运算放大器11的另一输入端子。该前置放大器10发挥阻抗匹配及缓冲等功能。输出放大器20具有运算放大器21、在其输入输出端子之间连接的电阻23、输入电阻22、输入信号开关24，将偏置电压Vb1提供给运算放大器21的另一输入端子。输出放大器20A也和输出放大器20相同。
第1偏置电路30将在电源电压Vdd与地电位之间串联连接的电阻31、32的连接点的偏置电压Vb1提供给前置放大器10及输出放大器20、20A、及其它必要的部分，外接电容器33通过电容器连接端子Pc1与电阻32并联连接。
当图12的声音信号处理IC200被施加了电源电压Vdd时，偏置电压Vb1从零电压缓缓上升，经过一段时间达到规定电压。这样，即使在前置放大器10、输出放大器20等处于可以动作的状态的情况下，耦合电容器Cc的输出方的直流电压的变化也可被抑制在很小，从而降低电冲击声。这样，通过由公共设置的偏压源分别将偏置电压提供给需要有偏置电压的多个放大器等，可以简化整体的电路结构。
另外，如这样通过由公共的偏压源将偏置电压提供给多个电路单元而构成的声音输出装置，正在被广泛地使用(参照专利文献特开平8一18342号公报、专利文献特开平5-136634号公报)。
但是，作为电子装置，如果以移动电话为例，则如图12所示，比如具有：将输出放大器20的输出信号输出的扬声器用的信号输出端子Pout、将输出放大器20A的输出信号输出的耳机用的信号输出端子PoutA、将前置放大器10的输出信号输出的外部输出用的信号输出端子PoutB等多个输出。在移动电话中，由于将电池作为电源来使用，因而希望尽可能降低电能消耗、力图延长电池电源的寿命。因此构成为只使在当时所使用的输出放大电路进行动作，使不使用的输出放大电路停止动作，从开关信号输入端子Pon、PonA将开关控制信号Vpon输入到每个输出放大电路。这样，在移动电话的使用中被接通的输出放大电路，在接通时就会产生电冲击声。
发明内容
因此，本发明的目的在于，提供一种具有声音输出装置的电子装置，该声音输出装置包括需要有偏置电压的前置放大器及至少一个输出放大器，可以分别独立地开关输出放大器，并且可降低其接通时的电冲击声。
另外，本发明的目的在于，提供一种具有声音输出装置的电子装置，该声音输出装置能够分别地开关需要有偏置电压的输出放大器，同时能够提高偏置电压的上升速度、并可降低接通时的电冲击声。
本发明之1的具有声音输出装置的电子装置的特征在于，具有：需要有第1偏置电压的前置放大器；可被分别开关的、需要有第2偏置电压的、输入所述前置放大器的输出的至少一个输出放大器；生成提供给所述前置放大器的第1偏置电压的第1偏置电路；包含电阻及电容器，在动作时生成对应提供给所述输出放大器的接通信号而缓慢增加的所述第2偏置电压的第2偏置电路。
本发明之2的具有声音输出装置的电子装置的特征是，具有：可被分别开关的、需要有偏置电压的、输入前置放大器的输出的至少一个输出放大器；包含电阻及电容器，在动作时生成对应提供给所述输出放大器的接通信号而缓慢增加的所述偏置电压的偏置电路；对应所述接通信号，随着时间的经过，进一步增加由所述偏置电路所生成的偏置电压大小的偏置调整电路。
本发明之3的具有声音输出装置的电子装置的特征是，在本发明之2的具有声音输出装置的电子装置中，所述偏置调整电路具有：将恒定电流提供给所述偏置电路的输出点的恒定电流电路；和对应所述接通信号而开始动作，使所述恒定电流电路进行动作直到所述偏置电压达到规定电压为止的电压比较电路。
本发明之4的具有声音输出装置的电子装置的特征是，在本发明之2的具有声音输出装置的电子装置中，所述偏置调整电路具有：连接在所述偏置电路的输出点与电源电压之间，通过一个或多个开关可以变更电阻值的电阻电路网；对应所述接通信号而开始动作、生成控制所述开关的开关控制信号，以使所述电阻电路网的电阻值从大的值按顺序变更为小的值，然后从小的值按顺序变更为大的值的开关控制电路。
本发明之5的具有声音输出装置的电子装置的特征是，在本发明之4的具有声音输出装置的电子装置中，所述开关控制电路具有：计数器，其具有能够输入所述接通信号和时钟信号的结构，在接收到所述接通信号后对所述时钟信号进行计数，并输出规定的计数信号；和根据所述计数信号生成所述开关控制信号的逻辑电路。
本发明之6的具有声音输出装置的电子装置的特征是，在本发明之4的具有声音输出装置的电子装置中，所述开关控制电路具有：将所述偏置电压分别与不同的比较电压进行比较，并输出比较结果的多个比较器；和根据这些多个比较器的比较输出，生成所述开关控制信号的逻辑电路。
本发明之7的具有声音输出装置的电子装置的特征是，在本发明之4的具有声音输出装置的电子装置中，所述开关控制电路具有：计数器，其具有可输入所述接通信号和时钟信号的结构，在接收到所述接通信号后对所述时钟信号进行计数，输出在包含最初的开关控制信号的前半期间所使用的规定的计数信号；将所述偏置电压分别与不同的比较电压进行比较，并输出在包含最后的开关控制信号的后半期间所使用的比较结果的多个比较器；和输入所述计数信号和所述多个比较器的比较输出，在包含最初的开关控制信号的前半期间，根据所述计数信号生成所述开关控制信号，在包含最后的开关控制信号的后半期间，根据所述比较输出生成所述开关控制信号的逻辑电路。
附图说明
图1为表示本发明的具有声音输出装置的电子装置的第1实施例的电路结构图。
图2为表示图1的接通时的特性图。
图3为表示本发明的具有声音输出装置的电子装置的第2实施例的设置了偏置加速电路的构成图。
图4为表示在本发明的第3实施例的偏置加速电路50A中采用恒定电流电路的构成图。
图5为表示图4的接通时的特性图。
图6为表示在本发明的第4实施例的偏置加速电路50B中采用梯型电阻电路网和时间控制该电阻值的电路的构成图。
图7为表示图6的接通时的动作说明及特性的图。
图8为表示在本发明的第5实施例的偏置加速电路50C中采用梯型电阻电路网和电压控制该电阻值的电路的构成图。
图9为表示图8的接通时的特性图。
图10为表示在本发明的第6实施例的偏置加速电路50D中采用梯型电阻电路网和时间及电压控制该电阻值的电路的构成图。
图11为表示图10的接通时的特性图。
图12为表示以往的具有声音输出装置的电子装置的构成例的图。
图中：100、200-声音信号处理IC，10-前置放大器，20、20A-输出放大器，11、21-运算放大器，12、13、22、23-电阻，24-输入信号开关，30-第1偏置电路，40、40A-第2偏置电路，31、32、41、42-电阻，33、43-电容器，44-PMOS，45-反相电路，50、50A～50D-偏置加速电路，51、52、64～66-PMOS，53-NMOS，54-恒定电流源，55、71～76-比较器，61～63-加速电阻，67、78-计数器，68、77-逻辑电路，Vin-输入信号，Vout-输出信号，Cc-耦合电容器，Sp-扬声器，Vpon-开关控制信号，Vb1-第1偏置电压，Vb2-第1偏置电压，CLK-时钟。
具体实施方式
下面，参照附图，对本发明的具有声音输出装置的电子装置的实施例进行说明。另外，在本发明中，「声音」是指声、音响。
图1为表示本发明的具有声音输出装置的电子装置的第1实施例的构成图，图2为表示接通时的特性图。
在图1中，其电路结构与图12中的不同点在于：设置有第2偏置电路40，将来自该第2偏置电路40的第2偏置电压Vb2提供给输出放大器20。其它的构成与图12相同，对于对应的构成部分付有相同的参照符号。
由第1偏置电路30生成的第1偏置电压Vb1，被提供给前置放大器10。前置放大器10的输出被提供给扬声器用的输出放大器20、耳机用的输出放大器20A及信号输出端子PoutB。
在本发明中，新设置的第2偏置电路40在电源电压Vdd和地之间串联连接有P型MOS晶体管(PMOS)44、电阻41和电阻42。将电阻41和电阻42的连接点与电容器连接端子Pc2连接，通过该电容器连接端子Pc2将外接电容器43与电阻42并联连接。将在电阻41和电阻42的连接点所生成的第2偏置电压Vb2提供给输出放大器20的运算放大器21。另外，也可以将电容器33、43设置在声音信号处理IC100的内部。
通过反相电路45，将开关控制信号Vpon施加到PMOS44的栅极，在将电源电压Vdd提供给输出放大器20的运算放大器21进行动作时，PMOS44导通(开关接通)。
决定电阻41和电阻42的电阻值，以使在对电源电压Vdd进行分压，得到规定的偏置电压Vb2的同时，能够将消耗电力限制在允许值的范围内。另外，在决定电容器43的电容容量时，除了要考虑到要将在PMOS44导通后的偏置电压Vb2的上升速度定为哪种程度之外，还要考虑到在电源电压Vdd内有噪声重叠的情况下，作为在偏置电压Vb2中产生的变化的比率的电源电压变化除去比PSRR。
当将电源电压Vdd施加到图1的声音信号处理IC100上时，第1偏置电路30的偏置电压Vb1从零电压缓缓上升，经过一定的时间达到规定的电压。通过偏置电压Vb1上升，确定了前置放大器10内的运算放大器11的偏置电压，生成输入信号Yin被前置放大的声音信号，该声音信号被提供给输出放大器20和输出放大器20A。
在该状态下，当开关控制信号Vpon为高(H)电平时，首先，将电源施加到输出放大器20，开始动作(接通)。同时，将开关控制信号Vpon提供给第2偏置电路40，PMOS44导通，偏置电压Vb2开始上升。
在图2中，表示了输出放大器20的接通时的特性。在时间t1，当开关控制信号Vpon从低(L)电平变为H电平时，偏置电压Vb2根据由电阻41、42及电容器43的值所决定的时间常数缓缓上升。由于输出放大器20的输出信号Vout和偏置电压Vb2同样增加，所以作为耦合电容器Cc输入端的X点的电压Vx和偏置电压Vb2同样缓缓增加。另一方面，作为耦合电容器Cc输出端的Y点的电压Vy成为对应电压Vx的变化量的值。
这样，由于电压Vy缓缓变化，因而由扬声器Sp所产生的电冲击声就被限制在小的值。将其与为了进行参考而用虚线表示的以往的电压Vy变化的特性进行比较，可看出显著地变小了。
输出放大器20的输入信号开关24，在输出放大器20被接通之前形成开路，在偏置电压Vb2上升到规定值后形成闭路。这样，来自前置放大器10的声音信号被放大输出。另外，输入信号开关24在输出放大器20的动作停止(断开)之前形成开路。
另外，在输出放大器20断开时，由运算放大器21的高阻抗及所设置的用于放电的阻抗电路，为了在再启动时不发生电冲击声，对被充电到耦合电容器Cc内的电荷进行放电。
另外，输出放大器20A的偏置电压，在图1中使用了第1偏置电路30的偏置电压Vb1。但也可以取代其，而进一步设置输出放大器20A用的结构与第2偏置电路40相同的专用偏置电路。
另外，在图1中，将开关信号输入端子Pon、PonA分别对应输出放大器20、20A来设置，但也可以构成共用这些开关信号输入端子的一个端子。在该情况下，其构成为：将所输入的开关信号在IC100的内部实施逻辑处理，根据该输入，分别开关控制各输出放大器20、20A。
这样，在包括需要有偏置电压的前置放大器10和一个或多个输出放大器20、20A的声音输出装置中，通过使其能够分别地开关输出放大器20，并且设置该输出放大器用的偏置电路40，来降低接通时的电冲击声。
图3为表示设置了本发明的具有声音输出装置的电子装置的第2实施例的偏置调整电路(以下称偏置加速电路)的构成图。图4为表示在本发明的第3实施例的偏压加速电路中采用了恒定电流电路的构成图。图5为表示图4中的接通时的特性图。
在图3中，在第2偏置电路40A中设置了偏置加速电路50，这一点与图1不同。另外，也可以取代在第2偏置电路40A中设置偏置加速电路50，而设置其它的电路。
偏置加速电路50对应开关控制信号Vpon的H电平，开始动作，对电容器43提供充电电流，以便在电冲击声被允许的范围内尽快使偏置电压Vb2上升。并在偏置电压Vb2达到规定值时停止动作。
决定偏置电压Vb2稳定时的大小的电阻41、42，为了减少电能消耗，而被设定为大的电阻值。另一方面，只要决定了电阻41、42的电阻值，为了设定偏置电压Vb2的所希望的上升特性、即时间常数(C×R)，必然要决定电容器43的容量。因此，在为了减少电能消耗而加大电阻41、42的电阻值的情况下，电容器43的容量就会被设定为小的值。
但是，为了改善电源电压变化除去比PSRR、即使在电源电压内有噪声重叠的情况下，也能减少在偏置电压Vb2中所产生的变化，也希望使电容器43具有尽可能大的容量。这直接关系到能否进行稳定的放大动作、生成质量好的输出信号。这一点，在电源容量有限制、将电池作为电源来使用的便携式电子装置中，为特别重要的问题。
通过设置本发明的偏置加速电路50，能够在规定期间内进行偏置电压Vb2的上升、并限制伴随着偏置电压Vb2的上升的电冲击声，同时在偏置电路40A中采用电阻值大的电阻41、42和容量大的电容器43，可以在减少电能消耗的同时，改善电源电压变化除去比PSRR。
在图4所示的本发明第3实施例中，在偏置加速电路50A中设置有漏极与偏置电压Vb2的输出点连接的电流镜电路的输出侧PMOS52、及栅极和漏极与该PMOS52的栅极连接的电流镜电路的输入侧PMOS51。通过N型MOS晶体管(以下称NMOS)53，PMOS51的漏极与恒定电流源54连接。
另外，设置将偏置电压Vb2和基准电压Vref1相比较，根据该比较输出控制NMOS53开关的比较器55。该比较器55根据开关控制信号Vpon的H电平开始动作。
也参照表示接通时的特性的图5，对图4的动作进行说明。当开关控制信号Vpon为H电平时，在输出放大器20被接通的同时，PMOS44导通，开始对电容器43充电。同时，比较器55也开始动作，根据该输出，NMOS53导通，对应恒定电流源54的电流的恒定电流通过输出侧的PMOS52开始对电容器43充电。该状态为图5的时间t1。
偏置电压Vb2根据恒定电流从时间t1随时间的迁移直线上升。当然，电流也流入电阻41、电阻42，但由于与流过输出侧的PMOS52的电流相比其很小，因而用直线来表示。电容器43被充电，当偏置电压Vb2达到基准电压Vref1时，比较器55的输出就反转为L电平，电流镜电路的动作结束，输出侧的PMOS52截止。
由于耦合电容器Cc的一端的X点的电压Vx和偏置电压Vb2同样进行变化，因而耦合电容器Cc的另外一端的Y点的电压Vy就成为对应电压Vx的变化率的值。该电压Vy与没有设置偏置加速电路50A时的特性(在图中用单点划线表示)相比较，在很短的时间其变化就结束。另外，虽然该电压Vy的大小有所增加，但与以往的特性(在图中用虚线表示)相比，只是被局限在非常小的值上。
这样，即使是加大了电容器43的容量，提高了电源电压变动除去比PSRR的偏置电路40A，也可以加快偏置电压Vb2的上升，并可以降低接通时的电冲击声。
图6表示在本发明的第4实施例的偏置加速电路50B中采用梯型的电阻电路网和时间控制该电阻值的电路的构成图。图7(a)(b)(c)为表示图6中接通时的动作说明及特性的图。
在图6中，在偏置加速电路50B中，在偏置电压Vb2的输出点和电源电压Vdd之间并联连接有PMOS64和加速电阻61(电阻值R1)、RMOS65和第2加速电阻62(电阻值R2)、RMOS66和第3加速电阻63(电阻值R3)。另外，具有：将时钟CLK输入，根据开关控制信号Vpon的H电平来计数时钟CLK，按顺序生成计数输出01～06的计数器67；和接收这些计数输出01～06，并输出使PMOS64～66导通或截止的栅极控制信号的逻辑电路68。
该逻辑电路68是由如图所示那样构成的与非门电路NAND1～NAND3及反相电路NOT1～NOT3所构成。其动作如图7(a)所示，在从开关控制信号Vpon成为H电平时的时间t1到计数输出01成为H电平时的第1期间T1，PMOS64～66全部截止，然后在直到计数输出02成为H电平前的第2期间T2，只有PMOS64导通，然后在直到计数输出03成为H电平前的第3期间T3，PMOS64、65导通，然后在直到计数输出04成为H电平前的第4期间T4，PMOS64、65、66全部导通，然后在直到计数输出05成为H电平前的第5期间T5，PMOS64、65导通，然后在直到计数输出06成为H电平前的第6期间T6，只有PMOS64导通，最后，在计数输出06成为H电平后的第7期间T7，PMOS64、65、66全部截止。
参照图7，对采用了该图6的梯型电阻的电阻电路网的偏置电路40A的动作进行说明。
在时间t1，当开关控制信号Vpon成为H电平时，计数器67开始时钟CLK的计数。在期间T1，只通过电阻41(电阻值为R0)对电容器43进行充电。由于电阻值R0很大，因而偏置电压Vb2的增加极其缓慢。
在期间T2，电阻41和电阻61成为并联(R0//R1，“//”表示并联关系)，在期间T3，电阻41、电阻61及电阻62成为并联(R0//R1//R2)，在期间T4，电阻41、电阻61、电阻62和电阻63成为并联(R0//R1//R2//R3)。从该期间T1到期间T4，对电容器43进行充电的并联电阻值逐渐变小，单位时间的偏置电压Vb2的增加率逐渐变大。
在期间T5，电阻41、电阻61和电阻62成为并联(R0//R1//R2)，在期间T6，电阻41和电阻61成为并联(R0//R1)。在期间T7只有电阻41(R0)。从该期间T5到期间T7，对电容器43进行充电的并联电阻值逐渐变大，单位时间的偏置电压Vb2的增加率逐渐变小。
在图7(b)中模式地表示了该经过时间(T1-T7)与偏置电压Vb2的关系。适当地设定各期间T1～T6的长度和各电阻41、电阻61～63的电阻值，使偏置电压Vb2的变化和时间同时平缓地变化。在该图中，各期间的偏置电压Vb2的变化，实际上为电阻和电容器的曲线的特性，为了简单用直线来表示。
在该实施例中，根据时钟CLK的计数的时间和电阻41、电阻61～63的电阻值，决定偏置电压Vb2的精度。因此，比如在电阻值与规定值(即，设计值)不同的情况下，如图7(b)中用单点划线所示那样，在期间T6的结束时，有从规定的偏置电压Vb2R偏离的情况。在该情况下，在期间T7中，通过电阻41(或电阻42)，对电容器43进行充电(或放电)直到达到由电阻41、42的分压比所决定的偏置电压Vb2R。
在采用该梯型电阻的电阻电路网的偏置电路40A中，Y点电压Vy如图7(c)所示，与以往的相比当然不用讲，即使与图4的恒定电流方式相比，变化也变得更平滑。因此，就可以更有效地控制电冲击声。并且，其所用的控制装置，能够用计数器和逻辑电路这样的简单电路来构成。
图8表示在本发明第5实施例的偏置加速电路50C中采用梯型的电阻电路网和电压控制该电阻值的电路的构成图。图9为表示图8中接通时的特性图。
在图8的偏置加速电路50C中，通过检测偏置电压Vb2的电压值，控制梯型的电阻电路网的电阻值。这一点与图7的偏置加速电路50B不同，除此之外相同。
在图8中，具有：将偏置电压Vb2分别与第1电压V1～第6电压V6相比较的第1比较器71～第6比较器76；和根据这些比较器71～76的比较结果，控制PMOS64～66的逻辑电路77。逻辑电路77具有与非门电路NAND1～NAND3。第1电压V1～第6电压V6被设定为：V1＜V2＜V3＜V4＜V5＜V6，第6电压V6被设定为与规定的偏置电压Vb2R相等(V6＝Vb2R)。
参照图9，对该图8的电压控制梯型电阻的电阻电路网的偏置电路40A的动作进行说明。
在时间t1，当开关控制信号Vpon成为H电平时，PMOS44导通，只通过电阻41对电容器43进行充电。由于电阻值R0很大，因而偏置电压Vb2的增加极其缓慢。当偏置电压Vb2达到第1电压V1时，比较器71的输出反转(L→H电平)，电阻61被并联连接到电阻41。以下相同，每当在偏置电压Vb2达到第2电压V2～第6电压V6时，比较器72～比较器76便进行反转(L→H电平、或H→L电平)。电阻电路网的电阻值的变更程序和图6中的相同。
在该实施例中，由于采用比较器71～76进行电压控制，所以电阻41、电阻61～63的电阻值的个体偏差等就不会对偏置电压Vb2的精度产生影响。在第6比较器76进行反转动作时，可以得到规定的偏置电压Vb2R。因此，就不需要单独通过电阻41、42所追加的充放电时间。另外，即使在不能得到时钟CLK的情况下，也可以推进电阻电路网的电阻值的变更程序。另外，其它的效果，与图6的第4实施例相同。
图10表示在本发明第6实施例的偏置加速电路50D中采用梯型的电阻电路网和对该电阻值实施时间控制及电压控制的电路的构成图。图11为表示图10中的在接通时的特性图。
在图10的偏置加速电路50D中，在包含最初的开关控制信号的前半期间中，采用用于时间控制的计数器的计数信号来进行梯型的电阻电路网的电阻值的变更程序，在包含最后的开关控制信号的后半期间中，采用检测偏置电压Vb2的电压值的比较器的比较输出来进行梯型的电阻电路网的电阻值的变更程序。在采用这种混合型控制方面，与图7的偏置加速电路50B、图8的偏置加速电路50C是不同的。在其它的方面相同。
在图10中，具有：将时钟CLK输入，根据开关控制信号Vpon的H电平来计数时钟，按顺序生成计数输出01～03的计数器78；将偏置电压Vb2和第4电压V4～第6电压V6分别比较的第4比较器74～第6比较器76；和根据这些计数输出01～03及比较器74～76的比较结果，控制PMOS64～66的逻辑电路77。逻辑电路77具有与非门电路NAND1～NAND3。计数输出01～03根据该顺序依次成为H电平，然后，将比较器74～76的比较输出按顺序输出。第4电压V4～第6电压V6被设定为：V4＜V5＜V6，第6电压V6被设定为与规定的偏置电压Vb2R相等(V6＝Vb2R)。
并且参照图11，也对该图10的时间控制及电压控制梯型电阻的电阻电路网的偏置电路40A的动作进行说明。
在时间t1，当开关控制信号Vpon成为H电平时，PMOS44导通，只通过电阻41对电容器43进行充电。在该期间T1，由于电阻值R0很大，因而偏置电压Vb2的增加极其缓慢。同时，计数器78开始时钟CLK的计数。
当生成计数输出01时，进入期间T2，当生成计数输出02时，进入期间T3，还有，当生成计数输出03时，进入期间T4。从该期间T1到期间T4，对电容器43充电的并联电阻值逐渐变小，单位时间的偏置电压Vb2的增加率逐渐变大。
然后，在期间T4进行电容器43的充电，当偏置电压Vb2达到V4时，比较器74的比较输出就反转为L电平，当偏置电压Vb2达到V5时，比较器75的比较输出就反转为L电平，最后，当偏置电压Vb2达到V6时，比较器76的比较输出就反转为L电平。在该状态下，就成为由电阻41、电阻42、电容器43决定了偏置电压Vb2的状态。
这样，在前半期间，采用计数器78的计数信号01～03进行梯型的电阻电路网的电阻值的变更程序，在后半期间中，采用比较器74～76的比较输出进行梯型的电阻电路网的电阻值的变更程序。但电阻电路网的电阻值的变更程序和图6、图8中的相同。
在该实施例中，在前半期间，采用计数器78的计数信号01～03进行时间控制，在后半期间，采用比较器74～76进行电压控制。这样，就可以减少用于进行电压控制的比较器。
另外，由于电阻61～63的电阻值的偏差等，如图11中单点划线所示，即使偏置电压Vb2的特性与预定的不同时，也可以通过在后半期间，在第4比较器74进行反转动作时吸收该偏差，在第6比较器76进行反转动作时得到规定的偏置电压Vb2R。因此，就不需要只通过电阻41、42追加的充放电时间。另外，也可以进一步缩短采用比较器进行电压控制的后半期间(比如仅期间T6)。
该实施例，在得到时钟信号的情况下，可以得到精度高的偏置电压Vb2，并由于可以简化必要的电路结构，因而具有高的实用效果。
另外，上面对于电阻电路网的梯型电阻的段数以用3段为例进行了说明，当然该段数仅为一个实例，可以参照偏置电压Vb2的必要的特性，设定为1以上的任意段数。
发明效果
根据本发明，在包括具备需要有偏置电压的前置放大器及至少一个输出放大器的声音输出装置的电子装置中，可以分别开关输出放大器，并且可以降低该输出放大器在接通时的电冲击声。
另外，根据本发明，可以分别开关需要有偏置电压的输出放大器，同时在偏置电路内或与偏置电路一起设置使偏置电压的大小随时间一起急速增加的偏置加速电路。这样，即可以加大偏置电路内包含的电容器的容量，提高电源电压变化除去比PSRR，也可以加速偏置电压的上升并降低在接通时的电冲击声。
Claims (7)
1.一种具有声音输出装置的电子装置，其特征在于，具有：
需要有第1偏置电压的前置放大器；
可被分别开关的、需要有第2偏置电压的、输入所述前置放大器的输出的至少一个输出放大器；
生成提供给所述前置放大器的第1偏置电压的第1偏置电路；
包含电阻及电容器，在动作时生成对应提供给所述输出放大器的接通信号而缓慢增加的所述第2偏置电压的第2偏置电路。
2.一种具有声音输出装置的电子装置，其特征在于，具有：
可被分别开关的、需要有偏置电压的、输入前置放大器的输出的至少一个输出放大器；
包含电阻及电容器，在动作时生成对应提供给所述输出放大器的接通信号而缓慢增加的所述偏置电压的偏置电路；
对应所述接通信号，随着时间的经过，进一步增加由所述偏置电路所生成的偏置电压大小的偏置调整电路。
3.根据权利要求2所述的具有声音输出装置的电子装置，其特征在于，所述偏置调整电路具有：
将恒定电流提供给所述偏置电路的输出点的恒定电流电路；和
对应所述接通信号而开始动作，使所述恒定电流电路进行动作直到所述偏置电压达到规定电压为止的电压比较电路。
4.根据权利要求2所述的具有声音输出装置的电子装置，其特征在于，所述偏置调整电路具有：
连接在所述偏置电路的输出点与电源电压之间，通过一个或多个开关可以变更电阻值的电阻电路网；
对应所述接通信号而开始动作、生成控制所述开关的开关控制信号，以使所述电阻电路网的电阻值从大的值按顺序变更为小的值，然后从小的值按顺序变更为大的值的开关控制电路。
5.根据权利要求4所述的具有声音输出装置的电子装置，其特征在于，所述开关控制电路具有：
具有能够输入所述接通信号和时钟信号的结构，在接收到所述接通信号后对所述时钟信号进行计数，并输出规定的计数信号的计数器；和
根据所述计数信号生成所述开关控制信号的逻辑电路。
6.根据权利要求4所述的具有声音输出装置的电子装置，其特征在于，所述开关控制电路具有：
将所述偏置电压分别与不同的比较电压进行比较，并输出比较结果的多个比较器；和
根据这些多个比较器的比较输出，生成所述开关控制信号的逻辑电路。
7.根据权利要求4所述的具有声音输出装置的电子装置，其特征在于，所述开关控制电路具有：
具有可输入所述接通信号和时钟信号的结构，在接收到所述接通信号后对所述时钟信号进行计数，输出在包含最初的开关控制信号的前半期间所使用的规定的计数信号的计数器；
将所述偏置电压分别与不同的比较电压进行比较，并输出在包含最后的开关控制信号的后半期间所使用的比较结果的多个比较器；和
输入所述计数信号和所述多个比较器的比较输出，在包含最初的开关控制信号的前半期间，根据所述计数信号生成所述开关控制信号，在包含最后的开关控制信号的后半期间，根据所述比较输出生成所述开关控制信号的逻辑电路。
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| CNB2003101102907A Expired - Fee Related CN100477492C (zh) | 2002-12-27 | 2003-12-26 | 具有声音输出装置的电子装置 |
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|---|---|
| US (1) | US7046082B2 (zh) |
| JP (1) | JP4160381B2 (zh) |
| CN (1) | CN100477492C (zh) |
| TW (1) | TW200419896A (zh) |
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2002
- 2002-12-27 JP JP2002379943A patent/JP4160381B2/ja not_active Expired - Fee Related
-
2003
- 2003-12-24 US US10/746,813 patent/US7046082B2/en not_active Expired - Lifetime
- 2003-12-25 TW TW092136830A patent/TW200419896A/zh unknown
- 2003-12-26 CN CNB2003101102907A patent/CN100477492C/zh not_active Expired - Fee Related
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1956523B (zh) * | 2005-10-27 | 2010-09-22 | 海尔集团公司 | 一种消除电视机关机噪音的装置及方法 |
Also Published As
| Publication number | Publication date |
|---|---|
| CN100477492C (zh) | 2009-04-08 |
| US20040161123A1 (en) | 2004-08-19 |
| JP2004214815A (ja) | 2004-07-29 |
| US7046082B2 (en) | 2006-05-16 |
| TW200419896A (en) | 2004-10-01 |
| JP4160381B2 (ja) | 2008-10-01 |
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