WO2024252558A1 - 直流電力変換装置及び制御方法 - Google Patents

直流電力変換装置及び制御方法 Download PDF

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Publication number
WO2024252558A1
WO2024252558A1 PCT/JP2023/021159 JP2023021159W WO2024252558A1 WO 2024252558 A1 WO2024252558 A1 WO 2024252558A1 JP 2023021159 W JP2023021159 W JP 2023021159W WO 2024252558 A1 WO2024252558 A1 WO 2024252558A1
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Prior art keywords
voltage
power
limit value
drive signal
phase difference
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PCT/JP2023/021159
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English (en)
French (fr)
Japanese (ja)
Inventor
裕司 岡田
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東芝三菱電機産業システム株式会社
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Priority to PCT/JP2023/021159 priority Critical patent/WO2024252558A1/ja
Priority to JP2025525524A priority patent/JPWO2024252558A1/ja
Publication of WO2024252558A1 publication Critical patent/WO2024252558A1/ja

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC

Definitions

  • An embodiment of the present invention relates to a DC power conversion device and a control method.
  • DAB dual active bridge
  • DC/AC conversion circuits full bridge circuits
  • the direction of power transmission and the amount of conversion can be controlled by adjusting the relationship between the phase of the drive signal for the full bridge circuit on the primary side and the phase of the drive signal for the full bridge circuit on the secondary side.
  • the object of the present invention is to provide a DC power conversion device and a control method that can reduce the effects of voltage fluctuations that occur between the input voltage and output voltage of a DAB type DC power conversion device.
  • the DC power conversion device of the embodiment performs power conversion between a first DC power and a second DC power by a DAB method for transferring power between a first DC power and a second DC power.
  • the DC power conversion device includes a first bridge circuit, a second bridge circuit, an inductance element, and a control device.
  • the first bridge circuit is driven by a first drive signal, and converts the first DC power into a first AC power and outputs it to a first AC terminal.
  • the second bridge circuit is driven by a second drive signal, and converts a second DC power of a second DC voltage into a second AC power and outputs it to a second AC terminal.
  • the inductance element is provided between the first bridge circuit and the second bridge circuit, and is connected to the first AC terminal and the second AC terminal, respectively.
  • the control device determines a phase difference between the first drive signal and the second drive signal used for phase shift control by the DAB system, generates the first drive signal and the second drive signal that drive the first bridge circuit and the second bridge circuit according to the phase difference, and drives the first bridge circuit and the second bridge circuit using the first drive signal and the second drive signal.
  • the control device determines an allowable range of the phase difference using the first DC voltage and the second DC voltage and limits the magnitude of the current flowing through the inductance element, it generates the first drive signal and the second drive signal with the phase difference limited within the allowable range.
  • FIG. 1 is a configuration diagram of a power conversion device according to an embodiment.
  • FIG. 4 is a diagram showing an equivalent circuit of an inductance element.
  • FIG. 2 is a diagram for explaining the operation of a DC/DC converter.
  • FIG. 2 is a block diagram of a control device for a power conversion device according to an embodiment.
  • FIG. 4 is a diagram for explaining an arithmetic expression used by the control device according to the embodiment.
  • 5A to 5C are diagrams for explaining current waveforms generated by control according to the embodiment.
  • FIG. 4 is a diagram for explaining an example of a current waveform.
  • FIG. 1 is a configuration diagram of a DC power conversion device 100 according to an embodiment.
  • the DC power conversion device 100 includes a DC/DC converter 102 forming a main circuit, and a control device 103 .
  • the DC power conversion apparatus 100 further includes voltage detectors 171 and 172 for detecting the operating state of the main circuit, and a current detector 141 .
  • the DC power conversion device 100 includes primary side DC terminals 102a and 102b and secondary side DC terminals 102c and 102d as terminals to be connected to an external bus or the like.
  • the DC/DC converter 102 performs power conversion (DC/DC conversion) between a primary side DC voltage Vdc1 across primary DC terminals 102a, 102b and a secondary side DC voltage Vdc2 across secondary side DC terminals 102c, 102d.
  • the DC/DC converter 102 is a DC/DC converter with a DAB configuration.
  • the DC/DC converter 102 includes a primary bridge circuit 110, a secondary bridge circuit 120, an inductance element 130, and smoothing capacitors 150 and 160.
  • the primary bridge circuit 110 and the secondary bridge circuit 120 are an example of a pair of bridge circuits.
  • the primary side bridge circuit 110 forms a single-phase full bridge. Specifically, the primary side bridge circuit 110 has semiconductor switching elements SW1 to SW4 connected between the high potential side power supply wiring PL1 and the low potential side power supply wiring NL1.
  • the power supply wiring PL1 and the power supply wiring NL1 are connected to the primary side DC terminals 102a and 102b, respectively.
  • a smoothing capacitor 150 for stabilizing the primary side DC voltage Vdc1 is connected between the power supply wiring PL1 and the power supply wiring NL1.
  • the semiconductor switching elements SW1 and SW2 are connected in series via a node N1a to form a first leg 111 connected between the power supply wiring PL1 and the power supply wiring NL1.
  • the node N1a is connected to an AC terminal 123a.
  • the semiconductor switching elements SW3 and SW4 are connected between the power supply wiring PL1 and the power supply wiring NL1 via a node N1b to form a second leg 112.
  • the node N1b is connected to an AC terminal 123b.
  • the secondary side bridge circuit 120 forms a single-phase full bridge.
  • the secondary side bridge circuit 120 has semiconductor switching elements SW5 to SW8 connected between the high potential side power supply wiring PL2 and the low potential side power supply wiring NL2.
  • the power supply wiring PL2 and the power supply wiring NL2 are connected to the secondary side DC terminals 102c and 102d, respectively.
  • a smoothing capacitor 160 for stabilizing the secondary side DC voltage Vdc2 is connected between the power supply wiring PL2 and the power supply wiring NL2.
  • semiconductor switching elements SW5 and SW6 are connected in series between power supply wiring PL2 and power supply wiring NL2 via node N2a connected to AC terminal 124a to form third leg 121.
  • semiconductor switching elements SW7 and SW8 are connected in series between power supply wiring PL2 and power supply wiring NL2 via node N2b connected to AC terminal 124b to form fourth leg 122.
  • semiconductor switching elements SW1, SW3, SW5, SW7 form the "upper arm”
  • semiconductor switching elements SW2, SW4, SW6, SW8 form the "lower arm.”
  • semiconductor switching elements SW1 to SW8 are collectively referred to as semiconductor switching elements SW.
  • the semiconductor switching element SW has a self-extinguishing switching element and a diode.
  • the switching element can be composed of any self-extinguishing element such as an IGBT (Insulated Gate Bipolar Transistor), a MOSFET (Metal Oxide Semiconductor Field Effect Transistor), or a GCT (Gate Commutated Turn-off) thyristor.
  • the diode is connected in inverse parallel to the switching element to form a free wheeling diode (FWD).
  • the inductance element 130 has primary side AC terminals 130a and 130b connected to the AC terminals 123a and 123b of the primary side bridge circuit 110, respectively, and secondary side AC terminals 130c and 130d connected to the AC terminals 124a and 124b of the secondary side bridge circuit 120, respectively.
  • the inductance element 130 is formed by a transformer 11 having a primary winding 11a connected between the primary side AC terminals 130a and 130b, and a secondary winding 11b connected between the secondary side AC terminals 130c and 130d.
  • FIG. 2 is a diagram showing an equivalent circuit of the inductance element 130.
  • the inductance element 130L can also be configured to include a reactor 11c connected between the primary AC terminal 130a and the secondary AC terminal 130c.
  • the inductance element 130L shown in FIG. 2 can be used as an equivalent circuit of the inductance element 130 described above.
  • the inductance element 130L is an unbalanced circuit provided in one of the circuits in FIG. 2, it may also be a balanced circuit provided in both circuits.
  • the voltage detector 171 detects the terminal voltage of the smoothing capacitor 150, i.e., the primary side DC voltage Vdc1, and outputs a signal indicating the detected value to the control device 103.
  • the voltage detector 172 detects the terminal voltage of the smoothing capacitor 160, i.e., the secondary side DC voltage Vdc2, and outputs a signal indicating the detected value to the control device 103.
  • the current detector 141 detects the AC current IL1 (hereinafter also referred to as the "primary AC current") flowing between the AC terminal 123a of the primary bridge circuit 110 and the primary AC terminal 130a of the inductance element 130, and outputs a signal indicating the detected value to the control device 103.
  • the primary AC current hereinafter also referred to as the "primary AC current”
  • the current detector 142 detects the AC current IL2 (hereinafter also referred to as the "secondary AC current") flowing between the AC terminal 124a of the secondary bridge circuit 120 and the secondary AC terminal 130c of the inductance element 130, and outputs a signal indicating the detected value to the control device 103.
  • the AC current IL2 hereinafter also referred to as the "secondary AC current”
  • the direction of the primary side AC current IL1 flowing from the primary side bridge circuit 110 to the inductance element 130 is regarded as the positive direction.
  • the direction of the secondary side AC current IL2 flowing from the secondary side bridge circuit 120 to the inductance element 130 is regarded as the positive direction.
  • the current detector may be either one of the current detector 141 and the current detector 142.
  • the current detector 141 may be provided on the primary side.
  • the control device 103 controls the power conversion in the DC/DC converter 102. Specifically, the control device 103 generates control signals (gate signals) GP1 to GP8 for controlling the on/off of the semiconductor switching elements SW1 to SW8 based on commands from a higher-level controller (not shown) and the output signals of the voltage detectors 171, 172 and the current detector 141.
  • control signals gate signals
  • GP1 to GP8 for controlling the on/off of the semiconductor switching elements SW1 to SW8 based on commands from a higher-level controller (not shown) and the output signals of the voltage detectors 171, 172 and the current detector 141.
  • control device 103 can be configured with a microprocessor including a CPU (Central Processing Unit) 103a, memory 103b, and an input/output (I/O) circuit 103c.
  • the input/output circuit 103a receives detection values from sensors disposed in the DC/DC converter 102, and outputs control signals to the components of the DC/DC converter 102.
  • the control signals include the gate signals GP1 to GP8 described above.
  • the control device 103 can realize the control functions described below by software processing in which the CPU 103a executes arithmetic processing according to a program stored in the memory 103b. Alternatively, the control device 103 can realize some or all of the control functions by hardware processing using dedicated electronic circuits.
  • the DC/DC converter 102 converts the DC power input from the primary side DC terminal 102a into AC power (single-phase AC power in the example of FIG. 1) by the primary side bridge circuit 110, and the AC power is transmitted to the secondary side bridge circuit 120 via the inductance element 130.
  • the secondary side bridge circuit 120 converts the AC power back into DC power and transmits it to the secondary side DC terminals 102c and 102d. In this case, power is transmitted from the primary side DC terminals 102a and 102b to the secondary side DC terminals 102c and 102d.
  • the DC/DC converter 102 can transmit power from the secondary side DC terminals 102c, 102d to the primary side DC terminals 102a, 102b due to the symmetry of the circuit.
  • the DC power input to the secondary side DC terminal 102c is converted to AC power (single-phase AC power in the example of FIG. 1) by the secondary side bridge circuit 120, and the AC power is transmitted to the primary side bridge circuit 110 via the inductance element 130.
  • the primary side bridge circuit 110 converts the AC power back to DC power and transmits it to the primary side DC terminals 102a, 102b.
  • the DC power conversion device 100 is capable of DC voltage conversion between the primary side and the secondary side, and the power transmission direction can be controlled to either power transmission from the primary side to the secondary side or power transmission from the secondary side to the primary side.
  • Fig. 3 is a diagram for explaining the operation of the DC/DC converter 102.
  • Fig. 3 shows the operation when the transformer 11 is applied as the inductance element 130.
  • the horizontal axis of Fig. 3 shows the switching phase, with the switching period Tsw of each semiconductor switching element SW being one period (2 ⁇ ).
  • the semiconductor switching elements SW1 and SW2 included in the same leg are turned on and off in a complementary manner, and similarly the semiconductor switching elements SW3 and SW4 are turned on and off in a complementary manner. Furthermore, the semiconductor switching elements SW1 and SW4 are turned on and off in the same phase, and the semiconductor switching elements SW2 and SW3 are turned on and off in the same phase.
  • the semiconductor switching elements SW1 to SW4 are periodically switched on and off depending on the state of the drive signal (gate pulse GP).
  • the above is the case where the duty (duty factor) of the drive signal is ( ⁇ /2), but there is no limitation to this and any desired duty may be used.
  • the semiconductor switching elements SW5 and SW6 included in the same leg are turned on and off in a complementary manner, and similarly the semiconductor switching elements SW7 and SW8 are turned on and off in a complementary manner. Furthermore, the semiconductor switching elements SW5 and SW8 are turned on and off in the same phase, and the semiconductor switching elements SW6 and SW7 are turned on and off in the same phase.
  • the semiconductor switching elements SW5 to SW8 are switched on and off periodically every ( ⁇ /2) of the switching period Tsw depending on the state of the drive signal (gate pulse GP).
  • phase difference ⁇ (0 ⁇ ) between the timing at which the semiconductor switching elements SW1 to SW4 in the primary bridge circuit 110 are switched on and off and the timing at which the semiconductor switching elements SW5 to SW8 in the secondary bridge circuit 120 are switched on and off.
  • an AC voltage Vtrpri (hereinafter also referred to as “primary side AC voltage”) is generated between the primary side AC terminals 130a and 130b of the inductance element 130 (both ends of the primary winding 11a), and an AC voltage Vtrsec (hereinafter also referred to as “secondary side AC voltage”) is generated between the secondary side AC terminals 130c and 130d of the inductance element 130 (both ends of the secondary winding 11b).
  • the current flowing through the secondary winding 11b is called the secondary side AC current IL2
  • the current flowing through the primary winding 11a is called the primary side AC current IL1.
  • IL1 -IL2
  • the primary side AC current IL1 and secondary side AC current IL2 are collectively referred to as the reactor current IL.
  • Each of the primary AC voltage Vtrpri and the secondary AC voltage Vtrsec is a square wave voltage having a voltage pulse width ⁇ that corresponds to the on-period length of the semiconductor switching elements SW1 to SW8 (0 ⁇ ).
  • the ratio of the on-period length of the semiconductor switching element SW to the switching period Tsw is defined as Duty.
  • Fig. 4A is a block diagram of the control device 103 of the DC power conversion device 100 according to the embodiment.
  • Fig. 4B is a diagram for explaining an arithmetic expression used by the control device 103 according to the embodiment.
  • Fig. 5 is a diagram for explaining a current waveform generated by the control according to the embodiment.
  • each block in each block diagram, including FIG. 4A, described below, are realized by at least one of software processing and hardware processing by the control device 103.
  • the control device 103 includes, for example, a voltage detection unit 301, a phase difference generation unit 302, a limit value adjustment unit 303, a limiter 304, a phase difference command generation unit 305, a current control unit 306, and a current detection unit 307.
  • the voltage detection unit 301 receives the output signals of the voltage detectors 171 and 172 ( Figure 1).
  • the voltage detection unit 301 samples the detection value of the primary side DC voltage Vdc1 by the voltage detector 171 at a predetermined sampling period Tsa, and outputs a primary side DC voltage detection value Vdc1_det based on the sampled value.
  • the voltage detection unit 301 samples the detection value of the secondary side DC voltage Vdc2 by the voltage detector 172 at a sampling period Tsa, and outputs a secondary side DC voltage detection value Vdc2_det based on the sampled value.
  • the phase difference generating unit 302 includes, for example, a voltage reference generating unit 3021, a subtractor 3022, a voltage control unit 3023, a phase difference conversion gain calculating unit 3024, a gain adjusting unit 3025, and a phase calculating unit 3026.
  • the voltage reference generating unit 3021 receives the primary side DC voltage detection value Vdc1_det from the voltage detection unit 301, and generates a voltage reference based on the primary side DC voltage detection value Vdc1_det. For example, the voltage reference generating unit 3021 performs smoothing processing on the primary side DC voltage detection value Vdc1_det, and outputs the resulting primary side DC voltage reference Vdc1_ref.
  • the subtractor 3022 calculates the difference between the primary side DC voltage reference Vdc1_ref provided by the voltage reference generating unit 3021 and the secondary side DC voltage detection value Vdc2_det provided by the voltage detection unit 301 as a voltage command.
  • the voltage control unit 3023 performs a PI calculation on the output (voltage command) of the subtractor 3022 to generate a power command Pref. For example, based on the difference between the primary side DC voltage reference Vdc1_ref provided by the voltage reference generation unit 3021 and the secondary side DC voltage detection value Vdc2_det provided by the voltage detection unit 301, the voltage control unit 3023 generates a power command Pref such that the difference becomes 0. This power command Pref corresponds to the transmission power between the primary side and secondary side.
  • the phase difference conversion gain calculation unit 3024 calculates the phase difference conversion gain based on the primary side DC voltage reference Vdc1_ref and the secondary side DC voltage detection value Vdc2_det.
  • the gain adjustment unit 3025 uses the phase difference conversion gain to standardize the power command generated by the voltage control unit 3023 for the phase difference conversion gain. More specifically, the gain adjustment unit 3025 outputs the result (quotient) of dividing the power command by the phase difference conversion gain as the phase adjustment amount.
  • the phase calculation unit 3026 adjusts the reference phase using the phase adjustment amount generated by the gain adjustment unit 3025. For example, the phase calculation unit 3026 subtracts the phase adjustment amount from a reference value (e.g., "1") and calculates the square root of the result as the first reference phase. Furthermore, the phase calculation unit 3026 subtracts the first reference phase from the reference value (e.g., "1") and calculates a second reference phase from the result.
  • a reference value e.g., "1”
  • the phase difference generating unit 302 outputs the second reference phase as the calculation result.
  • the phase difference generating unit 302 generates a command value that generates a phase difference between the primary side AC voltage Vtrpri and the secondary side AC voltage Vtrsec. Since the AC currents IL1 and IL2 change according to this phase difference ⁇ , the power transmitted between the primary side and the secondary side also changes. Therefore, by providing a phase difference ⁇ that is set according to the power command value, the transmission power between the primary side and the secondary side can be controlled according to the power command value.
  • the transmission power P converted by the DC/DC converter 102 is expressed by the following equation (A) using the switching frequency fsw of the semiconductor switching element SW, the inductance component L of the transformer 11, and the phase difference ⁇ .
  • phase difference command value ⁇ ref which is the command value for the phase difference ⁇
  • the phase difference command value Pref can be calculated from the power command value Pref according to the following formula (C).
  • ⁇ ref ( ⁇ /2)-( ⁇ /2) ⁇ (1-(8L ⁇ fsw ⁇ Pref)/(Vdc1 ⁇ Vdc2))...(C)
  • the current detection unit 307 receives, for example, the output signal of the current detector 141 ( Figure 1).
  • the current detection unit 307 samples the output signal of the current detector 141 at a sampling period Tsa, and outputs a current detection value IL1_det based on the sampled value.
  • the limit value adjustment unit 303 receives the primary side DC voltage reference Vdc1_ref, the secondary side DC voltage detection value Vdc2_det, and the current detection value IL1_det, and generates a limit value ⁇ _LMT.
  • the limit value adjustment unit 303 includes, for example, limit value calculation units 3031 and 3032 and a limit value determination unit 3033 .
  • the limit value calculator 3031 calculates the first limit value ⁇ (t2) based on the calculation formula (1) shown in FIG. 4B.
  • the limit value calculator 3032 calculates the second limit value ⁇ (t3) based on the calculation formula (2) shown in FIG. 4B. The details of the equations (1) and (2) will be described later.
  • the limit value determination unit 3033 determines the limit value ⁇ _LMT based on the magnitudes of the first limit value ⁇ (t2) and the second limit value ⁇ (t3). For example, the limit value determination unit 3033 selects the smaller one of the first limit value ⁇ (t2) and the second limit value ⁇ (t3).
  • the limiter 304 limits the magnitude of the second reference phase so that it is equal to or less than the limit value ⁇ _LMT.
  • the phase difference command generator 305 divides the output value from the limiter 304 by 2 to calculate the phase difference command value ⁇ ref (phase shift command ⁇ ref).
  • the current control unit 306 uses the phase difference command value ⁇ ref to perform phase shift control using the DAB method, provides a phase difference according to the phase shift command ⁇ ref, and generates gate pulses GP1-GP8 for driving the DC/DC converter 102, which are supplied to the primary side bridge circuit 110 and the secondary side bridge circuit 120.
  • the DC/DC converter 102 operates the primary bridge circuit 110 and the secondary bridge circuit 120 using gate pulses GP1-GP8.
  • the reactor current waveform will be a repetition of a similar waveform shape, as shown in Figure 3 above.
  • Figure 5 shows one cycle of this.
  • the parameters characterizing the reactor current waveform shown in FIG. 5 are defined as follows:
  • the primary side DC voltage detection value Vdc1_det and the secondary side DC voltage detection value Vdc2_det are treated as voltages applied to the primary winding and secondary winding of the transformer, and are simply denoted as V1 and V2.
  • the voltage V2 on the secondary side of the transformer is converted to the voltage V1 on the primary side using a coefficient kn based on the turns ratio, and this is denoted as V2'.
  • t0, t1, t2, and t3 on the horizontal axis indicate the timing at which the control modes are started. Each control mode is started at each of these timings.
  • the order of the control modes is Mode1-1, Mode1-2, Mode2, and Mode3.
  • i(t0) Reactor current at time t0
  • i(t1) Reactor current at time t1
  • i(t2) Reactor current at time t2
  • i(t3) Reactor current at time t3
  • the period is indicated as T, and the duration of each control mode is indicated as T1 and T2.
  • T Period T1: Duration of Mode1 (combined range of Mode1-1 and Mode1-2) T2: Duration of Mode 2
  • the angle corresponding to the duration T1 of Mode 1 is indicated by ⁇ .
  • the angle corresponding to the duration T2 of Mode 2 is (2D ⁇ - ⁇ ). Note that (2D ⁇ ) is the angle corresponding to the pulse width of gate pulses GP1-GP8, whose Duty (Duty Factor) is D.
  • ⁇ IL1 Amount of change in reactor current during Mode 1
  • ⁇ IL2 Amount of change in reactor current during Mode 2
  • ⁇ IL2 can take positive or negative values depending on the magnitude of V1 and V2'. For example, if V2' is greater than V1, the value of ⁇ IL2 becomes negative, and power is sent from the secondary side to the primary side. The current waveform in this state will be as shown in Figure 5. On the other hand, if V2' is smaller than V1, the value of ⁇ IL2 becomes positive, and power is sent from the primary side to the secondary side. The current waveform in this state will differ from the waveform shown in Figure 5, and the current will increase during Mode 2 from time t2 to t3.
  • i(t2) and i(t3) can be reorganized as follows.
  • t1 T1 ⁇ i(t3)/(i(t2)+i(t3))
  • i(t1) 0
  • i(t2) ((2 ⁇ - ⁇ )V1+ ⁇ V2')/(2 ⁇ L)
  • the peak value of the current flowing through the transformer windings can be determined based on the primary DC voltage Vdc1, the secondary DC voltage Vdc2, the inductance of the transformer, the turns ratio of the transformer, and the phase difference ⁇ .
  • the peak value of the current flowing through the transformer windings varies depending on the primary DC voltage Vdc1, the secondary DC voltage Vdc2, and the phase difference ⁇ .
  • FIG. 6 is a diagram for explaining an example of a current waveform. For example, when a phase difference ⁇ is set such that the current flowing through the transformer winding has an amplitude of a waveform as shown by the dotted line in FIG. 6, a state occurs in which Mode 2 continues until time t4 corresponding to that phase difference ⁇ .
  • the phase difference ⁇ is limited at time t2 before the situation occurs in which the current shown by the dotted line in Figure 6 flows, so the control of Mode 1 does not continue beyond the phase difference ⁇ at time t2, and switches from Mode 1 to Mode 2 at time t2.
  • the peak value of the current flowing through the transformer winding is limited to a current value equivalent to i(t2) shown in Figure 5.
  • phase difference command value ⁇ ref used for such control is calculated using information on the current primary side DC voltage Vdc1 and secondary side DC voltage Vdc2. This makes it possible to set a limit value for the phase difference command value ⁇ ref in the phase shift control method based on the upper limit of the current flowing through the transformer windings.
  • the DC power conversion device 100 performs DAB type power conversion control for transferring power between the first DC power and the second DC power.
  • the first bridge circuit 110 of the DC power conversion device 100 is driven by gate pulses GP1-4 (first drive signal) and converts a first DC power of a first DC voltage into a first AC power and outputs it to a first AC terminal.
  • the second bridge circuit 120 is driven by gate pulses GP5-8 (second drive signal) and converts a second DC power of a second DC voltage into a second AC power and outputs it to a second AC terminal.
  • the inductance element 130 is provided between the first bridge circuit 110 and the second bridge circuit 120, and is connected to the first AC terminal and the second AC terminal, respectively.
  • the control device 103 determines a phase difference between the first drive signal and the second drive signal used for phase shift control using the DAB system, generates the first drive signal and the second drive signal that drive the first bridge circuit 110 and the second bridge circuit 120 respectively in accordance with the phase difference, and drives the first bridge circuit 110 and the second bridge circuit 120 using the first drive signal and the second drive signal.
  • the control device 103 determines an allowable range of the phase difference using the first DC voltage and the second DC voltage, and when limiting the magnitude of the current flowing through the inductance element 130, generates the first drive signal and the second drive signal with the phase difference limited within the allowable range. This allows the DC power conversion device 100 to reduce the influence of voltage fluctuations occurring between the input voltage and output voltage of a DAB type DC power conversion device.
  • the control device 103 may determine the allowable range based on the magnitude of the first DC voltage, the second DC voltage, and the current flowing through the inductance element 130 .
  • the inductance element 130 may be configured to include a transformer.
  • control device 103 may determine a limit value that limits the magnitude of the phase difference using the first DC voltage, the second DC voltage, the inductance of the inductance element 130 (transformer), and the turns ratio of the transformer.
  • control device 103 may estimate the magnitude of the current flowing through the inductance element 130 using the first DC voltage, the second DC voltage, the inductance of the inductance element (transformer), the turns ratio of the transformer, and the magnitude of the phase difference.
  • the phase difference generation unit 302 outputs the second reference phase as a calculation result.
  • the limit value adjustment unit 303 calculates the first limit value ⁇ (t2) and the second limit value ⁇ (t3), and determines the limit value ⁇ _LMT based on the magnitudes of the first limit value ⁇ (t2) and the second limit value ⁇ (t3).
  • the limiter 304 passes the generated second reference phase when the generated second reference phase is not greater than the limit value ⁇ _LMT, and limits the magnitude of the second reference phase to be equal to or less than the limit value ⁇ _LMT when the generated second reference phase is greater than the limit value ⁇ _LMT.
  • the current control unit 306 may use the phase difference command value ⁇ ref to perform phase shift control by the DAB method.
  • the first limit value calculation unit 3031 of the limit value adjustment unit 303 calculates a first limit value ⁇ (t2) for phase shift control.
  • the first limit value calculation unit 3032 calculates a second limit value ⁇ (t3) for the phase shift control.
  • the limit value determination unit 3033 may determine the limit value ⁇ _LMT based on the magnitudes of the first limit value ⁇ (t2) and the second limit value ⁇ (t3).
  • the duty of the drive signal (gate pulse) shown in Fig. 3 is exemplified as 0.5.
  • the duty may be set to a value other than 0.5.
  • an equation including the duty value (D) may be used as an arithmetic equation for determining the limit value of the phase difference command value ⁇ ref.
  • the value of the duty (D) may be a predetermined value (constant) or a variable whose value is set according to the state of control. It is preferable to use the most recent value of the duty (D) when determining the limit value of the phase difference command value ⁇ ref.
  • a representative value of either the detected value of AC current IL1 or the detected value of AC current IL2 may be used to calculate the limit value of the phase difference command value ⁇ ref.
  • the representative value the larger of the detected value of AC current IL1 or the detected value of AC current IL2, or the average value of these two values may be used.
  • the DC power conversion device performs power conversion between the first DC power and the second DC power by a DAB method for transferring power between the first DC power and the second DC power.
  • the DC power conversion device includes a first bridge circuit, a second bridge circuit, an inductance element, and a control device.
  • the first bridge circuit is driven by a first drive signal, and converts the first DC power into a first AC power and outputs it to a first AC terminal.
  • the second bridge circuit is driven by a second drive signal, and converts the second DC power of a second DC voltage into a second AC power and outputs it to a second AC terminal.
  • the inductance element is provided between the first bridge circuit and the second bridge circuit, and is connected to the first AC terminal and the second AC terminal, respectively.
  • the control device determines a phase difference between the first drive signal and the second drive signal used for phase shift control by the DAB system, generates the first drive signal and the second drive signal that drive the first bridge circuit and the second bridge circuit according to the phase difference, and drives the first bridge circuit and the second bridge circuit using the first drive signal and the second drive signal.
  • the control device determines an allowable range of the phase difference using the first DC voltage and the second DC voltage and limits the magnitude of the current flowing through the inductance element, the control device can reduce the influence of voltage fluctuations occurring between the input voltage and the output voltage of the DAB DC power conversion device by generating the first drive signal and the second drive signal with the phase difference limited within the allowable range.
  • a part or all of the functional units of the control device 103 in the DC power conversion device 100 of the embodiment described above may have software functional units that are realized, for example, by a computer processor (hardware processor) executing a program (computer program, software component) stored in a storage unit (memory, etc.) of the computer.
  • a part or all of the functional units of the control device 103 may be realized by hardware such as an LSI (Large Scale Integration), an ASIC (Application Specific Integrated Circuit), or an FPGA (Field-Programmable Gate Array), or may be realized by a combination of software functional units and hardware.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
PCT/JP2023/021159 2023-06-07 2023-06-07 直流電力変換装置及び制御方法 WO2024252558A1 (ja)

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Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2020225854A1 (ja) * 2019-05-07 2020-11-12 三菱電機株式会社 電力変換装置
JP2021083253A (ja) * 2019-11-21 2021-05-27 富士電機株式会社 電力変換装置、制御方法、および制御プログラム
JP2023007117A (ja) * 2021-07-01 2023-01-18 株式会社豊田中央研究所 無接点電力伝送回路
JP2023018738A (ja) * 2021-07-28 2023-02-09 三菱電機株式会社 電力変換装置

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2020225854A1 (ja) * 2019-05-07 2020-11-12 三菱電機株式会社 電力変換装置
JP2021083253A (ja) * 2019-11-21 2021-05-27 富士電機株式会社 電力変換装置、制御方法、および制御プログラム
JP2023007117A (ja) * 2021-07-01 2023-01-18 株式会社豊田中央研究所 無接点電力伝送回路
JP2023018738A (ja) * 2021-07-28 2023-02-09 三菱電機株式会社 電力変換装置

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