WO2015041111A1 - 電力変換装置 - Google Patents
電力変換装置 Download PDFInfo
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- WO2015041111A1 WO2015041111A1 PCT/JP2014/073891 JP2014073891W WO2015041111A1 WO 2015041111 A1 WO2015041111 A1 WO 2015041111A1 JP 2014073891 W JP2014073891 W JP 2014073891W WO 2015041111 A1 WO2015041111 A1 WO 2015041111A1
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- power
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- pulsating
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
- H02M1/15—Arrangements for reducing ripples from dc input or output using active elements
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
- H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
- H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
- H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
- H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
- H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
- H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M5/4585—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only having a rectifier with controlled elements
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
- H02M1/007—Plural converter units in cascade
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention relates to a power converter having a power buffer circuit.
- a full-wave rectifier circuit In order to obtain a DC voltage from a single-phase AC voltage input from a single-phase AC power supply, it is common to use a full-wave rectifier circuit. However, the output of the full-wave rectifier circuit has a power pulsation having a frequency twice that of the single-phase AC voltage. Therefore, in order to reduce this power pulsation, a power buffer circuit that buffers power between the output side of the full-wave rectifier circuit and the load is required. For power buffering, for example, a capacitive element called a smoothing capacitor is required.
- Non-Patent Document 1 discloses a technique in which a buffer capacitor is connected to a smoothing capacitor via a current reversible chopper to absorb pulsating power. With this technique, the total capacitance required for smoothing is greatly reduced by reducing the capacitance of the smoothing capacitor and allowing the voltage ripple on the buffer side.
- Non-Patent Document 2 discloses a technique of reducing the smoothing capacitor of Non-Patent Document 1 and connecting a buffer capacitor to a DC link via a switching element.
- a direct conversion circuit is shown that generates a voltage source with such a technique and generates a high frequency link along with a power supply voltage.
- Non-Patent Document 3 further discloses a technique for making the input waveform sinusoidal and increasing the efficiency.
- Patent Documents 1 and 2 filed by the applicant of the present application are listed as documents disclosing the technology related to the present application.
- Non-Patent Document 1 In the power conversion using the technique shown in Non-Patent Document 1, it is not necessary to control the voltage of the buffer capacitor to be constant. Therefore, regardless of whether it is a direct conversion type or an indirect conversion type, In comparison, the required capacitance can be set small.
- the amplitude of pulsating power is as large as the constant component of power. Therefore, the allowable ripple current value required for the buffer capacitor is also high.
- it is desirable to use an electrolytic capacitor as a buffer capacitor because of downsizing of the device and cost constraints. Therefore, even if it is a buffer capacitor, by using an electrolytic capacitor, it is possible to select a capacitance that is larger than the actual required capacitance and is equivalent to a normal smoothing capacitor from the viewpoint of satisfying the allowable ripple current value. I had to do it.
- Non-Patent Document 4 shows a single-phase three-phase direct conversion circuit that does not have an active power buffer circuit. Here, the relationship between input current and output power ripple is shown. And in order to make an input waveform into a sine wave shape, the necessity of giving the pulsation electric power which has a frequency twice a power supply frequency with respect to output electric power is shown.
- the speed ripple accompanying the pulsation of the load torque is expected to be suppressed to about 10% by the moment of inertia of the motor. Nevertheless, since the pulsation torque increases as the power capacity increases, the stress of the compressor support system also increases. Therefore, it is clear that there is an upper limit to the power capacity that can be adopted.
- the power buffered by the power buffer circuit is made smaller than the pulsating power, thereby reducing the capacitance and power capacity of the power buffer circuit. With the goal. This also contributes to expanding the range of power capacity when the load pulsates.
- the power conversion device includes a DC link (7) including a first power supply line (LH) and a second power supply line (LL); a single-phase AC voltage (Vin) is input and pulsating power is applied to the DC link.
- Converter (3) that outputs (Pin); inverter (5) that inputs power from the DC link and outputs AC current (Iu, Iv, Iw); and charging power (Pl) that is input from the DC link
- a power buffer circuit (4) for outputting discharge power (Pc) to the DC link.
- the fluctuation amount (Pc ⁇ Pl) of the discharging power with respect to the charging power is an AC component (Pin ⁇ ) of the pulsating power. Smaller than).
- a second mode of the power conversion device is the first mode, wherein the input power (Pdc) input to the inverter (5) is the pulsating power from the DC link (7).
- a value obtained by subtracting the charging power from the sum of the discharging power (Pin + Pc ⁇ Pl) is taken.
- the charging power (Pl) is a constant (k) times the pulsating power (Pin) (however, the constant is positive and smaller than 1 ⁇ 2).
- a third aspect of the power conversion device is the second aspect, wherein the converter (3) is obtained by full-wave rectifying the single-phase AC voltage (Vm ⁇ sin ( ⁇ t)).
- the rectified voltage (Vrec) is applied to the DC link (7) with the first power supply line (LH) having a higher potential than the second power supply line (LL); at least the pulsating power exceeds the predetermined value
- a value obtained by subtracting the constant from 1 (1-k) is a first current that is a current (Im ⁇
- the power buffer circuit (4) includes a capacitor (C4) and a first switch connected in series on the first power line side with respect to the capacitor between the first power line and the second power line.
- a discharge current (ic) which is a current (Pc / Vc) obtained by dividing the discharge power (Pc) by the voltage across the capacitor (Vc);
- the 4th aspect of the power converter device concerning this invention is the 2nd aspect, Comprising:
- the said converter (3) is a rectified voltage (Vrec) obtained by carrying out full wave rectification of the said single phase alternating voltage (Vin). ) Is applied to the DC link (7) with the first power line (LH) at a higher potential than the second power line (LL).
- the power buffer circuit (4) includes a capacitor (C4) and a first switch connected in series on the first power line side with respect to the capacitor between the first power line and the second power line.
- a discharge circuit (4a) including (Sc, D42) and a charging circuit (4b) for charging the capacitor.
- the rectification duty (drec) which is the duty at which the converter conducts with the DC link (7), is the square of the sine value of the predetermined voltage (Vdc) and the phase ( ⁇ t) of the single-phase AC voltage (sin 2 ( ⁇ t)). (Vdc / Vm ⁇
- the discharge duty (dc) which is the duty that the capacitor discharges, is a value obtained by dividing the product of the predetermined voltage and the square of the cosine value of the phase (cos 2 ( ⁇ t)) by the voltage across the capacitor (Vc) ( Vdc / Vc ⁇ cos 2 ( ⁇ t)).
- a fifth aspect of the power converter according to the present invention is any one of the second to fourth aspects, wherein the constant (k) does not depend on the alternating current (Iu, Iv, Iw). .
- a sixth aspect of the power conversion device is any one of the second to fourth aspects, wherein the constant (k) is the magnitude of the alternating current (Iu, Iv, Iw). Inversely proportional.
- the predetermined value is set smaller than the maximum rated power of the pulsating power.
- a fluctuation amount (Pc ⁇ Pl) of the discharging power with respect to the charging power is an alternating current of the pulsating power. It is equal to the component (Pin ⁇ ).
- a variation (Pc ⁇ Pl) of the discharging power with respect to the charging power does not depend on the pulsating power.
- the variation of the discharge power with respect to the charge power is the power buffered by the power buffer circuit, which is smaller than the AC component of the pulsating power. Therefore, the power capacity of the power buffer circuit can be reduced as compared with the conventional case.
- the power buffered by the power buffer circuit is twice the constant multiple of the AC component of the pulsating power. Since the constant is smaller than 1/2, the power to be buffered in the first mode is smaller than that in the conventional power buffer circuit, and the second mode contributes to the realization of the first mode.
- the period during which the inverter flows the zero-phase current can be shortened, and the period during which the voltage applied to the DC link voltage can be increased.
- the sum of the product of the rectification duty and the rectification voltage and the product of the discharge duty and the voltage at both ends corresponds to the average value of the DC voltage used by the inverter.
- the said sum corresponds with a predetermined voltage, This does not depend on the phase of a single phase alternating voltage, and can be made into a fixed value.
- the ripple current of the capacitor can be reduced in the light load region, and the life of the power converter can be extended.
- FIG. 2 is a circuit diagram showing an equivalent circuit of the circuit shown in FIG. 1.
- movement of the direct power converter device concerning this Embodiment The graph which shows operation
- FIG. 1 is a block diagram showing a configuration of a direct power converter to which the control method shown in the present embodiment is applied.
- the direct power converter includes a converter 3, a power buffer circuit 4, an inverter 5, and a DC link 7.
- the converter 3 is connected to the single-phase AC power source 1 through the filter 2, for example.
- the filter 2 includes a reactor L2 and a capacitor C2.
- Reactor L ⁇ b> 2 is provided between one of the two output ends of single-phase AC power supply 1 and converter 3.
- the capacitor C2 is provided between the two output terminals of the single-phase AC power source 1.
- the filter 2 removes the high frequency component of the current.
- the filter 2 may be omitted. For the sake of simplicity, the following description will be made ignoring the function of the filter 2.
- DC link 7 has DC power supply lines LH and LL.
- the converter 3 employs a diode bridge, for example, and includes diodes D31 to D34.
- the diodes D31 to D34 constitute a bridge circuit, and the single-phase AC voltage Vin, which is an input voltage input from the single-phase AC power supply 1, is converted into a rectified voltage Vrec by single-phase full-wave rectification, and this is converted to the DC power supply line LH. , LL.
- a higher potential than the DC power supply line LL is applied to the DC power supply line LH.
- An input current Iin flows into the converter 3 from the single-phase AC power source 1.
- the power buffer circuit 4 has a discharge circuit 4 a and a charging circuit 4 b, and exchanges power with the DC link 7.
- the discharge circuit 4a includes a capacitor C4, and the charging circuit 4b boosts the rectified voltage Vrec to charge the capacitor C4.
- the discharge circuit 4a further includes a transistor (here, insulated gate bipolar transistor: hereinafter abbreviated as “IGBT”) Sc connected in reverse parallel to the diode D42.
- the transistor Sc is connected in series between the DC power supply lines LH and LL on the DC power supply line LH side with respect to the capacitor C4.
- the anti-parallel connection means that the forward directions are opposite to each other and are connected in parallel.
- the forward direction of the transistor Sc is a direction from the DC power supply line LL to the DC power supply line LH
- the forward direction of the diode D42 is a direction from the DC power supply line LH to the DC power supply line LL.
- the transistor Sc and the diode D42 can be collectively understood as one switch element (first switch).
- the capacitor C4 is discharged by the conduction of the first switch, and power is given to the DC link 7.
- the charging circuit 4b includes, for example, a diode D40, a reactor L4, and a transistor (IGBT here) Sl.
- the diode D40 includes a cathode and an anode, and the cathode is connected between the first switch and the capacitor C4.
- Such a configuration is known as a so-called boost chopper.
- Reactor L4 is connected between DC power supply line LH and the anode of diode D40.
- Transistor S1 is connected between DC power supply line LL and the anode of diode D40.
- a diode D41 is connected in reverse parallel to the transistor S1, and both can be grasped as one switch element (second switch). Specifically, the forward direction of the transistor S1 is a direction from the DC power supply line LH to the DC power supply line LL, and the forward direction of the diode D40 is a direction from the DC power supply line LL to the DC power supply line LH.
- the capacitor C4 is charged by the charging circuit 4b, and a both-end voltage Vc higher than the rectified voltage Vrec is generated. Specifically, energy is accumulated in the reactor L4 by flowing current from the DC power supply line LH to the DC power supply line LL via the second switch, and then the energy is transferred to the diode D40 by turning off the second switch. And stored in the capacitor C4.
- the both-end voltage Vc is higher than the rectified voltage Vrec, basically no current flows through the diode D42. Therefore, the conduction / non-conduction of the first switch depends exclusively on that of the transistor Sc. Therefore, hereinafter, the first switch including not only the transistor Sc but also the diode D42 may be referred to as a switch Sc.
- the second switch in which not only the transistor Sl but also the diode D41 is combined may be referred to as a switch Sl.
- the inverter 5 converts the DC voltage between the DC power supply lines LH and LL into an AC voltage and outputs it to the output terminals Pu, Pv and Pw.
- the inverter 5 includes six switching elements Sup, Svp, Swp, Sun, Svn, and Swn.
- the switching elements Sup, Svp, Swp are respectively connected between the output terminals Pu, Pv, Pw and the DC power supply line LH, and the switching elements Sun, Svn, Swn are respectively connected to the output terminals Pu, Pv, Pw and the DC power supply line LL. Connected between.
- the inverter 5 constitutes a so-called voltage source inverter and includes six diodes Dup, Dvp, Dwp, Dun, Dvn, Dwn.
- the diodes Dup, Dvp, Dwp, Dun, Dvn, and Dwn are all arranged with the cathode facing the DC power supply line LH and the anode facing the DC power supply line LL.
- the diode Dup is connected in parallel with the switching element Sup between the output terminal Pu and the DC power supply line LH.
- the diodes Dvp, Dwp, Dun, Dvn, Dwn are connected in parallel with the switching elements Svp, Swp, Sun, Svn, Swn, respectively.
- AC currents Iu, Iv, and Iw are output from the output terminals Pu, Pv, and Pw, respectively, and constitute a three-phase AC current.
- IGBTs are employed for the switching elements Sup, Svp, Swp, Sun, Svn, and Swn.
- the inductive load 6 is a rotating machine, for example, and is illustrated by an equivalent circuit indicating that it is an inductive load.
- the reactor Lu and the resistor Ru are connected in series with each other, and one end of the series body is connected to the output end Pu.
- reactors Lv and Lw and resistors Rv and Rw are connected to each other.
- the instantaneous input power Pin has an AC component ( ⁇ 1/2) ⁇ Vm ⁇ Im ⁇ cos (2 ⁇ t) indicated by the second term on the right side of the equation (1) (hereinafter also referred to as “AC component Pin ⁇ ”). Therefore, in the following, the instantaneous input power Pin may be referred to as pulsating power Pin.
- the power conversion device shown in FIG. 1 can be grasped as follows.
- the DC link 7 includes DC power supply lines LH and LL:
- the converter 3 receives a single-phase AC voltage Vin and outputs a pulsating power Pin:
- the power buffer circuit 4 inputs the charging power Pl from the DC link 7 and outputs the discharging power Pc to the DC link 7:
- FIG. 2 is a block diagram schematically showing the power balance in the direct power conversion apparatus shown in FIG.
- both the charging power Pl and the discharging power Pc have the same value as the AC component Pin ⁇ and the power supply phase
- the power buffer circuit 4 and the DC power supply lines LH and LL are exchanged with each other in a mutually exclusive period. For this reason, the power to be buffered by the power buffer circuit 4 is equal to the absolute value of the AC component Pin ⁇ , and a power capacity greater than this is required for the power buffer circuit 4.
- the difference in power exchanged between the power buffer circuit 4 and the DC power supply lines LH and LL only needs to satisfy Expression (2).
- the absolute value of the power (Pc ⁇ Pl) that is the fluctuation amount of the discharge power Pc with respect to the charge power Pl is smaller than the absolute value of the alternating current component Pin ⁇ , the power capacity of the power buffer circuit 4 is increased as compared with the conventional case. Can be reduced.
- the buffering power Pbuf can be selected smaller than the techniques shown in Non-Patent Documents 2 and 3. This leads to the following advantages for the power buffer circuit 4.
- Symbols H1 and H2 indicate capacitor capacities used when a single-phase power factor correction circuit is employed. Symbols H1 and H2 are data when air conditioners having air conditioning capacities of 6 kW and 11.2 kW, respectively, are employed.
- the power factor correction circuit here can be grasped as a configuration in which the switch Sc is short-circuit removed from the power buffer circuit 4 and the connection point between the reactor L4 and the converter 3 is not directly connected to the inverter 5.
- the series connection of the diode D40 and the reactor L4 is interposed between the converter 3 and the inverter 5 in the DC power supply line LH, and the capacitor C4 is connected between the DC power supply lines LH and LL and the inverter 5 Will be connected in parallel.
- the charging power Pl is a constant k times the pulsating power Pin
- the discharging power Pc is a power obtained by adding the charging power Pl to a constant k times ( ⁇ 2) times the AC component Pin ⁇ .
- the charging power Pl is the power k ⁇ Pin distributed from the pulsating power Pin to the power buffer circuit 4 via the DC link 7 with the constant k as a distribution rate. Therefore, hereinafter, the constant k is also referred to as a buffer distribution ratio k.
- Such charging power Pl and discharging power Pc are different from Patent Document 1 and Non-Patent Document 2 in which these are exchanged between the power buffer circuit 4 and the DC link 7 in an exclusive period in the power supply phase, respectively. No exclusive period is set in the power phase.
- discharge main period a period in which Pc> Pl (that is, Pbuf> 0) (hereinafter also referred to as “discharge main period”), discharging is mainly performed rather than charging, and a period in which Pc ⁇ Pl (that is, Pbuf ⁇ 0) is satisfied (hereinafter, “ In the “charging main period”, charging is mainly performed rather than discharging.
- the period of (n + 1/4) ⁇ ⁇ ⁇ t ⁇ (n + 3/4) ⁇ is the charge main period
- the period of ⁇ is the discharge main period (n is an integer: the same applies hereinafter).
- the power capacity required for the charging circuit 4b can be described quantitatively rather than the description in the previous section.
- Equation (6) The average value per cycle of the power supply frequency input to the conventional power factor correction circuit, that is, the power input to the reactor, is obtained by Equation (6) in view of Equation (1).
- the charging power Pl is input thereto. Therefore, in view of the equation (4), the average value per cycle of the power supply frequency input to the power buffer circuit 4, that is, the power input to the charging circuit 4b is obtained by the equation (7).
- the power capacity required for the charging circuit 4b is k times that of the power factor correction circuit.
- the power capacity required for the charging circuit 4b becomes smaller than 1/2 times that of the power factor correction circuit.
- the current irec output from the converter 3 is equal to the sum of the current irec1 and the current il.
- the peak value of the current il is k ⁇ Im. Therefore, in view of the fact that the peak value of the current input to the conventional power factor correction circuit is Im, it can be seen that the power capacity required for the reactor L4 is reduced as compared with the conventional case.
- FIG. 4 shows an equivalent circuit of the circuit shown in FIG.
- the equivalent circuit is introduced in Patent Document 1, for example.
- the current irec1 is equivalently represented as a current irec1 passing through the switch Srec when it is turned on.
- the discharge current ic is equivalently expressed as a current ic passing through the switch Sc when it is conductive.
- the switch Sz also conducts current that flows to the inductive load 6 via the inverter 5. Is equivalently expressed as a zero-phase current iz that flows through this.
- a reactor L4, a diode D40, and a switch Sl that constitute the charging circuit 4b are shown, and a current il that flows through the reactor L4 is added.
- the duty drec, dc, dz can be regarded as a current distribution ratio of the direct current Idc with respect to each current irec1, ic, iz.
- the duty drec is a duty that sets a period during which the converter 3 is connected to the DC link 7 and a current can flow to the inverter 5, it may be hereinafter referred to as a rectification duty drec.
- the duty dc is a duty for discharging the capacitor C4, hereinafter, it may be referred to as a discharge duty dc.
- the duty dz is a duty through which the zero-phase current iz always flows regardless of the output voltage in the inverter 5, it may be hereinafter referred to as a zero duty dz.
- the rectification duty drec and the discharge duty dc are set by the following equations (15) and (16), respectively.
- Equation (11) is adopted from the request to make it.
- the converter 3 when the converter 3 employs a diode bridge, the converter 3 cannot be actively switched at the rectification duty drec expressed by the equation (15). Therefore, the inverter 5 and the switch Sc are switched according to the zero duty dz and the discharge duty dc determined by the expressions (14), (15), and (16), respectively, and thereby the current irec1 expressed by the expression (10). Can be obtained.
- the inverter 5 cannot use the DC voltage in the DC link 7 during the period in which the zero-phase current iz flows. Therefore, a virtual DC voltage (hereinafter referred to as “virtual DC voltage”) Vdc during a period in which the inverter 5 can convert power among the DC voltages between the DC power supply lines LH and LL can be considered as follows. .
- the virtual DC voltage Vdc is grasped as a voltage generated at both ends of the inverter 5 and a current source Idc representing the load (which flows the DC current Idc).
- the voltage utilization rate R can be increased as the zero duty dz is reduced, and the lower limit of the zero duty dz is zero. Therefore, the duties drec and dc when the virtual DC voltage Vdc is maximized for each buffer distribution ratio k are obtained when the zero duty dz is zero.
- Expression (19) is obtained from Expressions (14), (15), and (16).
- the voltage Vc at both ends can be regarded as almost constant even by charging / discharging in the power buffer circuit 4 (for example, the fluctuation is about 5% as described above). Therefore, from equation (19), the DC current Idc when the virtual DC voltage Vdc is maximized is determined for each buffer distribution ratio k. Thus, from equations (15) and (16), the duties drec and dc when the virtual DC voltage Vdc is maximized are determined for each buffer distribution ratio k. Note that the virtual DC voltage Vdc at this time is determined by equations (18) and (19).
- the DC current Idc when the virtual DC voltage Vdc is maximized takes the minimum value in view of the equation (18). This is desirable from the viewpoint of reducing the power rating of the switching elements Sup, Svp, Swp, Sun, Svn, Swn and the diodes Dup, Dvp, Dwp, Dun, Dvn, Dwn employed in the inverter 5.
- duty drec, dc, dz is set in the first stage, virtual DC voltage Vdc and its first component drec ⁇ Vrec and second component dc ⁇ Vc and DC are set in the second stage.
- the current Idc, the current irec output from the converter 3 in the third stage (which is equal to the absolute value of the input current Iin) and the current irec1, il, ic, and the power Pin, Pc, Pbuf and Prec are shown respectively. Both graphs employ a phase ⁇ t in units of “degrees” on the horizontal axis.
- the first component drec ⁇ Vrec of the virtual DC voltage Vdc is a voltage that appears in the first term of the equation (17), and indicates the contribution of the converter 3 to the virtual DC voltage Vdc.
- the second component dc ⁇ Vc of the virtual DC voltage Vdc is a voltage that appears in the second term of the equation (17), and indicates the contribution of the capacitor C4 to the virtual DC voltage Vdc.
- the virtual DC voltage Vdc can be set to a constant value.
- the upper limit of the virtual DC voltage Vdc when it becomes constant will be described.
- dz ⁇ 0 when the phase ⁇ t is 30 to 150 degrees and 210 to 330 degrees.
- phase ⁇ t giving the maximum value of the virtual DC voltage Vdc gives the minimum value of the denominator on the right side of the equation (21). Therefore, the phase ⁇ t when the value of the expression (22) indicating the derivative of the denominator becomes zero may be obtained.
- each duty can be fixed according to the equations (14), (15), and (16), and the virtual DC voltage Vdc can be made constant.
- x Vc / (2 ⁇ Vm) in equation (21)
- the maximum value 1 can be obtained as the voltage utilization rate R by setting the both-end voltage Vc to twice the peak value Vm.
- the rectification duty drec can be expressed as, for example, a value obtained by dividing the product of the square of the sine value of the phase ⁇ t and the virtual DC voltage Vdc by the rectification voltage Vrec.
- the discharge duty dc can be expressed, for example, as a value obtained by dividing the product of the square of the cosine value of the phase ⁇ t and the virtual DC voltage Vdc by the both-ends voltage Vc.
- the virtual DC voltage Vdc can be arbitrarily set to a constant value unrelated to the phase ⁇ t, for example, while setting the rectification duty drec and the discharge duty dc to values unrelated to the buffer distribution ratio k.
- the input current Iin is expressed by Im ⁇ sin ( ⁇ t), that is, a sinusoidal waveform
- the current il satisfies the following formula (26) depending on the DC current Idc.
- equation (28) is obtained, which is the same as equation (21).
- Vc 1.5 Vm
- Vdc 0.96 Vm
- control for realizing the equation (18) can be performed by performing the control for matching the AC component of the equation (31) with the second term on the rightmost side of the equation (32).
- FIG. 11 An example of a configuration for performing the above control is shown in FIG. 11 as a block diagram.
- the said structure is provided in the structure shown as the control part 10 in FIG. 1, for example.
- the inductive load 6 is a rotating machine
- the rotational angular velocity ⁇ m the field magnetic flux ⁇ a of the rotating machine
- the d-axis inductance Ld and q-axis inductance Lq of the rotating machine the q-axis current command value Iq *
- the q-axis voltage command value Vq * and the d-axis voltage command value Vd * are obtained.
- Voltage command values Vu *, Vv *, and Vw * for controlling the inverter 5 are generated from the q-axis voltage command value Vq * and the d-axis voltage command value Vd *.
- the speed detector 9 detects AC currents Iu, Iv, Iw flowing through the inductive load 6, and from these, the rotational angular velocity ⁇ m, the q-axis current Iq, and the d-axis current Id are controlled. 10 is given.
- control unit 10 performs switching elements Sup, Svp, Swp, Sun, Svn of the inverter 5 by arithmetic processing (not shown) based on the voltage command values Vu *, Vv *, Vw * (see, for example, Patent Document 1).
- Swn respectively, control signals SSup, SSvp, SSwp, SSun, SSvn, SSwn (see FIG. 1) are obtained.
- the control unit 10 also generates signals SSc and SS1 for controlling the operations of the switches Sc and Sl, respectively, and these are generated based on the duties drec, dc, dz, and dl (see, for example, Patent Document 1). .
- the processing unit 71 includes a DC power calculation unit 711, a pulsation component extraction unit 712, a pulsation component calculation unit 713, a subtracter 714, an adder 715, and a PI processing unit 716.
- the DC power calculation unit 711 receives the q-axis voltage command value Vq * and the d-axis voltage command value Vd *, the q-axis current Iq and the d-axis current Id, and inputs the input power Pdc based on the above equation (31). Is calculated and given to the pulsation component extraction unit 712.
- the pulsation component extraction unit 712 extracts and outputs the AC component of Expression (31).
- the pulsation component extraction unit 712 is realized by, for example, a high-pass (high-pass transmission) filter HPF.
- the pulsation component calculation unit 713 receives the peak values Vm and Im, the power source angular velocity ⁇ , and the buffer distribution ratio k, and obtains the second term on the rightmost side of Equation (32).
- the peak values Vm, Im and the power source angular velocity ⁇ can be input to the pulsation component calculator 713 as information obtained from the single-phase AC power source 1 (see FIG. 1).
- the desired processing is to match the alternating current component of Equation (31) with the second term on the rightmost side of Equation (32), so the output of the pulsation component extraction unit 712 and the pulsation component calculation unit Control may be performed so as to reduce the difference from the output of 713. Accordingly, the difference is obtained by the subtracter 714, and a value obtained by subjecting the difference to integral proportional control by the PI processing unit 716 is output to the adder 715.
- the adder 715 performs processing for correcting the current command value Ia * in the normal processing with the output of the PI processing unit 716. Specifically, first, as a normal process for obtaining the current command value Ia *, a subtractor 701 obtains a deviation between the rotational angular velocity ⁇ m and the command value ⁇ m *. The deviation is subjected to integral proportional control in the PI processing unit 702, and a current command value Ia * is obtained once. The adder 715 performs processing for increasing the current command value Ia * by the output from the PI processing unit 716.
- the above-described known technique is applied to the current command value Ia * corrected by the processing unit 71 in this way to generate the q-axis voltage command value Vq * and the d-axis voltage command value Vd *.
- Such control is control in which feedback is performed on the q-axis voltage command value Vq * and the d-axis voltage command value Vd *, the q-axis current Iq, and the d-axis current Id, and the difference output from the subtracter 714 Is converged to 0. That is, by such control, the alternating current component of Equation (31) and the second term on the rightmost side of Equation (32) can be matched.
- the buffer distribution ratio k can be set regardless of the load. Such a setting is desirable from the viewpoint that the ripple current of the capacitor C4 can be reduced in the light load region and the life of the power converter can be extended.
- the buffer distribution ratio k may be set smaller as the load increases.
- the buffer distribution ratio k inversely proportional to the current command value Ia * obtained from the adder 715 can be set, or the reciprocal of the sum of the squares of the q-axis current Iq and the d-axis current Id.
- the buffer distribution ratio k may be set in proportion to. Such setting of the buffer distribution ratio k can be realized using a known technique.
- the direct power converter performs an operation in which the buffer distribution ratio k increases in inverse proportion to the current flowing through the inductive load 6.
- Such an operation is desirable in the following situation, for example.
- a load having a large inertia such as an electric motor that drives a compressor. If the inertia is large, the vibration of the electric motor and the compressor due to the torque fluctuation is suppressed. However, the effect of inertia on torque fluctuation is reduced at low speeds. Therefore, in a region where the electric current flowing through the inverter is small, that is, a low speed region of the electric motor as a load, the buffer distribution ratio k can be increased, thereby suppressing the torque fluctuation of the motor.
- the buffer distribution ratio k may be halved when the load is below a predetermined threshold.
- the fact that the buffer distribution ratio k is 1 ⁇ 2 means that the buffering power Pbuf (which corresponds to the power Pc ⁇ Pl which is the fluctuation amount: see (b-1)) is equal to the AC component Pin ⁇ of the pulsating power. means.
- the predetermined value can be set to 0. In this case, if the pulsating power Pin is 0, the power Pc-Pl is also 0. In this case, if the pulsating power Pin is positive, the power Pc ⁇ Pl is controlled to be smaller than the pulsating power Pin.
- this threshold value By setting this threshold value to a value corresponding to a predetermined value smaller than the maximum rated power Pin (max) of the pulsating power Pin, even when the pulsating power Pin takes the maximum rated power Pin (max), the power buffer Ring can be done.
- the buffering power Pbuf may be set to a constant value without depending on the pulsating power Pin.
- the filter 2 can be provided between the converter 3 and the power buffer circuit 4 even when any of the techniques described above is employed.
- FIG. 12 is a circuit diagram showing only the vicinity when the filter 2 is provided between the converter 3 and the power buffer circuit 4 as the modification.
- the diode D0 When adopting such a configuration, it is desirable to provide a diode D0 between the filter 2 and the discharge circuit 4a in the DC power supply line LH.
- the anode of the diode D0 is disposed on the filter 2 side, and the cathode is disposed on the discharge circuit 4a side.
- the diode D0 can prevent the voltage across the capacitor C2 from being affected by the voltage Vc across the capacitor C4 due to the switching of the switch Sc.
Abstract
Description
図1は、本実施の形態で示される制御方法が適用される直接形電力変換装置の構成を示すブロック図である。当該直接形電力変換装置は、コンバータ3と、電力バッファ回路4と、インバータ5と、直流リンク7とを備えている。
(b-1)電力低減の基本的な考え方.
コンバータ3に入力する瞬時入力電力Pinは、入力力率を1として、次式(1)で表される。但し、単相交流電圧Vinの波高値Vm及び電源角速度ω、入力電流Iinの波高値Im、時間tを導入した。電源角速度ωと時間tとの積ωtは単相交流電圧Vinの位相を表すことになる。また交流波形は、当該交流波形の位相ωtの正弦値と波高値の積として把握した。
コンバータ3は単相交流電圧Vinを入力し、脈動電力Pinを出力する:
電力バッファ回路4は、充電電力Plを直流リンク7から入力し、放電電力Pcを直流リンク7へ出力する:
インバータ5は直流リンク7から、脈動電力Pinと放電電力Pcとの和から充電電力Plを引いた入力電力Pdc(=Pin+Pc-Pl)を入力し、交流電流Iu,Iv,Iwを出力する。
この節では、バッファリング電力Pbufを低減することで、コンデンサC4に電解コンデンサを採用することができ、放電回路4aが安価に実現されることを説明する。
この節では、バッファリング電力Pbufを低減することで、充電回路4bが安価に実現されることを説明する。
さて、本節以降では、上述の充電電力Pl及び放電電力Pcの一例として、これらをそれぞれ式(4)(5)で定める。
本節では、コンバータ3が出力する電流irecのうち、コンバータ3からインバータ5へと流れる電流irec1を、バッファ分配率kに依存して設定する技術を説明する。
本節では、デューティdrec,dc,dzを、バッファ分配率kに依存せずに設定する技術を説明する。本節ではデューティdrec,dcを、それぞれ式(23),(24)で設定する。零デューティdzは式(23),(24),(14)から定まる。
上記の(b-5),(b-6)のいずれの技術を採用する場合であっても、デューティdrec,dc,dzの設定のみならず、直流電流Idcを式(18)に基づいて設定する必要がある。そこで、当節では直流電流Idcに採用される式(18)を実現するための一例を挙げる。
(c-1)バッファ分配率kの選定.
バッファ分配率kは負荷の大小によらずに設定できる。このような設定は軽負荷域においてコンデンサC4のリプル電流を低減でき、電力変換装置の寿命を長くすることができるという観点で望ましい。
上記で示されたいずれの技術を採用する場合であっても、フィルタ2をコンバータ3と電力バッファ回路4との間に設けることもできる。
Claims (9)
- 第1電源線(LH)及び第2電源線(LL)を含む直流リンク(7)と;
単相交流電圧(Vin)を入力して前記直流リンクに脈動電力(Pin)を出力するコンバータ(3)と;
前記直流リンクから電力を入力し、交流電流(Iu,Iv,Iw)を出力するインバータ(5)と;
前記直流リンクから充電電力(Pl)を入力し、前記直流リンクへと放電電力(Pc)を出力する電力バッファ回路(4)と
を備え、
少なくとも前記脈動電力が所定値を越えるときに、前記放電電力の前記充電電力に対する変動分(Pc-Pl)は、前記脈動電力の交流成分(Pin^)よりも小さい、電力変換装置。 - 前記インバータ(5)に入力する入力電力(Pdc)は、前記直流リンク(7)から、前記脈動電力と前記放電電力との和から前記充電電力を引いた値(Pin+Pc-Pl)を採り、
少なくとも前記脈動電力が前記所定値を越えるときに、
前記充電電力(Pl)は、前記脈動電力(Pin)の定数(k)倍(但し前記定数は正であって1/2よりも小さい)の値(k・Pin)を採り、前記放電電力(Pc)は、前記脈動電力の交流成分(Pin^)の前記定数倍の(-2)倍に前記充電電力を加えた値(2k・Pin^+Pl)を採る、請求項1記載の電力変換装置。 - 前記コンバータ(3)は、
前記単相交流電圧(Vm・sin(ωt))を全波整流して得られる整流電圧(Vrec)を、前記第1電源線(LH)を前記第2電源線(LL)よりも高電位として前記直流リンク(7)に印加し;
少なくとも前記脈動電力が前記所定値を越えるときに、前記脈動電力(Pin)を前記整流電圧(Vrec)で除した電流(Im・|sin(ωt)|)である第1電流に、1から前記定数を引いた値(1-k)を乗じた電流((1-k)・Im・|sin(ωt)|)を前記直流リンクに流し、
前記電力バッファ回路(4)は、
コンデンサ(C4)と、前記第1電源線と前記第2電源線との間で前記コンデンサに対して前記第1電源線側で直列に接続された第1スイッチ(Sc,D42)とを含む放電回路(4a)と、
前記コンデンサを充電する充電回路(4b)と
を含み、
前記電力バッファ回路(4)は、少なくとも前記脈動電力が前記所定値を越えるときに、前記第1電流の前記定数倍である充電電流(il=k・Im・|sin(ωt)|)を入力し;前記放電電力(Pc)を前記コンデンサの両端電圧(Vc)で除した電流(Pc/Vc)である放電電流(ic)を出力する、請求項2記載の電力変換装置。 - 前記コンバータ(3)は、前記単相交流電圧(Vin)を全波整流して得られる整流電圧(Vrec)を、前記第1電源線(LH)を前記第2電源線(LL)よりも高電位として前記直流リンク(7)に印加し、
前記電力バッファ回路(4)は、
コンデンサ(C4)と、前記第1電源線と前記第2電源線との間で前記コンデンサに対して前記第1電源線側で直列に接続された第1スイッチ(Sc,D42)とを含む放電回路(4a)と、
前記コンデンサを充電する充電回路(4b)と
を含み、
前記コンバータが前記直流リンク(7)と導通するデューティである整流デューティ(drec)は、所定電圧(Vdc)と前記単相交流電圧の位相(ωt)の正弦値の二乗(sin2(ωt))との積を前記整流電圧(Vrec)で除した値(Vdc/Vm・|sin(ωt)|)を採り、
前記コンデンサが放電するデューティである放電デューティ(dc)は、前記所定電圧と前記位相の余弦値の二乗(cos2(ωt))との積を前記コンデンサの両端電圧(Vc)で除した値(Vdc/Vc・cos2(ωt))を採る、請求項2記載の電力変換装置。 - 前記定数(k)は前記交流電流(Iu,Iv,Iw)に依存しない、請求項2乃至請求項4のいずれか一つに記載の電力変換装置。
- 前記定数(k)は前記交流電流(Iu,Iv,Iw)の大きさと反比例する、請求項2乃至請求項4のいずれか一つに記載の電力変換装置。
- 前記所定値は前記脈動電力の最大定格電力よりも小さく設定される、請求項1乃至請求項6のいずれか一つに記載の電力変換装置。
- 前記脈動電力が所定値以下であるときに、前記放電電力の前記充電電力に対する変動分(Pc-Pl)は、前記脈動電力の交流成分(Pin^)と等しい、請求項1乃至請求項7のいずれか一つに記載の電力変換装置。
- 前記脈動電力が所定値を越えるときに、前記放電電力の前記充電電力に対する変動分(Pc-Pl)は、前記脈動電力に依存しない、請求項1乃至請求項8のいずれか一つに記載の電力変換装置。
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US15/022,287 US9780683B2 (en) | 2013-09-19 | 2014-09-10 | Power converter with a power buffer circuit whose buffered power is smaller than an AC component of a pulsating power |
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Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN108450057A (zh) * | 2015-12-28 | 2018-08-24 | 大金工业株式会社 | 功率转换装置的控制装置 |
US10951152B2 (en) | 2018-03-29 | 2021-03-16 | Daikin Industries, Ltd. | Power conversion apparatus |
Families Citing this family (34)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP5664733B1 (ja) * | 2013-09-24 | 2015-02-04 | ダイキン工業株式会社 | 直接形電力変換装置の制御方法 |
JP2015228778A (ja) * | 2014-06-03 | 2015-12-17 | 株式会社日立製作所 | 電力変換装置 |
JP5930108B2 (ja) | 2014-09-25 | 2016-06-08 | ダイキン工業株式会社 | 電力変換装置 |
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US9923451B2 (en) * | 2016-04-11 | 2018-03-20 | Futurewei Technologies, Inc. | Method and apparatus for filtering a rectified voltage signal |
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US10277115B2 (en) | 2016-04-15 | 2019-04-30 | Emerson Climate Technologies, Inc. | Filtering systems and methods for voltage control |
CN105958836B (zh) * | 2016-06-30 | 2019-03-08 | 陕西科技大学 | 一种带开关续流电容的交直交变频器及其控制方法 |
JP6265297B1 (ja) | 2016-09-30 | 2018-01-24 | ダイキン工業株式会社 | 直接形電力変換器用の制御装置 |
CN106401963B (zh) * | 2016-11-22 | 2019-05-24 | 广东美芝制冷设备有限公司 | 旋转式压缩机以及具有其的制冷系统 |
CN106382229B (zh) * | 2016-11-22 | 2019-05-24 | 广东美芝制冷设备有限公司 | 旋转式压缩机及制冷循环装置 |
CN106803721B (zh) * | 2017-02-17 | 2018-12-14 | 江苏大学 | 永磁同步电机驱动系统无电解电容功率变换器及控制方法 |
TWI635380B (zh) * | 2017-04-26 | 2018-09-11 | 泰達國際控股有限公司 | 適用於功率因數校正電路之相位補償方法 |
US10170976B2 (en) | 2017-04-26 | 2019-01-01 | Delta Electronics (Thailand) Public Company, Limited | Phase compensation method for power factor correction circuit |
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WO2022070867A1 (ja) | 2020-09-30 | 2022-04-07 | ダイキン工業株式会社 | 電力変換装置 |
JP2022072026A (ja) * | 2020-10-29 | 2022-05-17 | ナブテスコ株式会社 | Ac-acコンバータ |
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US20220321016A1 (en) * | 2021-03-29 | 2022-10-06 | University Of Maryland, College Park | Multi-port power converters and power conversion systems, and methods for design and operation thereof |
WO2023105761A1 (ja) * | 2021-12-10 | 2023-06-15 | 三菱電機株式会社 | 電力変換装置、電動機駆動装置及び冷凍サイクル適用機器 |
Citations (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2006166654A (ja) * | 2004-12-09 | 2006-06-22 | Daikin Ind Ltd | 多相電流供給回路、駆動装置、圧縮機、及び空気調和機 |
JP2011193678A (ja) | 2010-03-16 | 2011-09-29 | Nagaoka Univ Of Technology | 単相/三相直接変換装置及びその制御方法 |
JP2012135184A (ja) | 2010-12-24 | 2012-07-12 | Daikin Ind Ltd | 制御信号生成装置、直接形電力変換装置並びに、その制御方法、その運転方法及びその設計方法 |
Family Cites Families (10)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP3112386B2 (ja) * | 1994-11-25 | 2000-11-27 | 三菱電機株式会社 | 無効電力発生装置 |
US6313602B1 (en) * | 1999-04-30 | 2001-11-06 | Texas Instruments Incorporated | Modified space vector pulse width modulation technique to reduce DC bus ripple effect in voltage source inverters |
US8503207B2 (en) * | 2010-09-29 | 2013-08-06 | Rockwell Automation Technologies, Inc. | Discontinuous pulse width drive modulation method and apparatus for reduction of common-mode voltage in power conversion systems |
US9362839B2 (en) * | 2011-02-09 | 2016-06-07 | Rockwell Automation Technologies, Inc. | Power converter with common mode voltage reduction |
EP2899865B1 (en) * | 2012-09-21 | 2019-01-02 | Daikin Industries, Ltd. | Method for controlling direct power conversion device |
JP5626435B2 (ja) * | 2012-09-27 | 2014-11-19 | ダイキン工業株式会社 | 直接形交流電力変換装置 |
WO2014057883A1 (ja) * | 2012-10-10 | 2014-04-17 | ダイキン工業株式会社 | 直接形電力変換装置および直接形電力変換装置の制御方法 |
JP6065262B2 (ja) * | 2012-10-12 | 2017-01-25 | 富士電機株式会社 | 電源装置 |
JP5664733B1 (ja) * | 2013-09-24 | 2015-02-04 | ダイキン工業株式会社 | 直接形電力変換装置の制御方法 |
JP5794273B2 (ja) * | 2013-10-07 | 2015-10-14 | ダイキン工業株式会社 | 直接形電力変換装置の制御方法 |
-
2014
- 2014-09-05 JP JP2014181287A patent/JP5804167B2/ja active Active
- 2014-09-10 MY MYPI2016700884A patent/MY174263A/en unknown
- 2014-09-10 CN CN201480051309.1A patent/CN105556817B/zh active Active
- 2014-09-10 US US15/022,287 patent/US9780683B2/en active Active
- 2014-09-10 AU AU2014322275A patent/AU2014322275B2/en active Active
- 2014-09-10 WO PCT/JP2014/073891 patent/WO2015041111A1/ja active Application Filing
- 2014-09-10 ES ES14846241T patent/ES2886801T3/es active Active
- 2014-09-10 SG SG11201602139SA patent/SG11201602139SA/en unknown
- 2014-09-10 EP EP14846241.9A patent/EP3048718B1/en active Active
Patent Citations (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2006166654A (ja) * | 2004-12-09 | 2006-06-22 | Daikin Ind Ltd | 多相電流供給回路、駆動装置、圧縮機、及び空気調和機 |
JP2011193678A (ja) | 2010-03-16 | 2011-09-29 | Nagaoka Univ Of Technology | 単相/三相直接変換装置及びその制御方法 |
JP2012135184A (ja) | 2010-12-24 | 2012-07-12 | Daikin Ind Ltd | 制御信号生成装置、直接形電力変換装置並びに、その制御方法、その運転方法及びその設計方法 |
Non-Patent Citations (4)
Title |
---|
HAGA; TAKAHASHI; OHISHI: "Unity Power Factor Operation Control Method For Single-phase to Three-phase Matrix Converter", THE INSTITUTE OF ELECTRICAL ENGINEERS OF JAPAN TRANSACTIONS D, vol. 124, no. 5, 2004, pages 510 - 516 |
IRIE; YAMASHITA; TAKEMOTO: "Ripple Compensation for a Single-Phase Rectifier by 2-Quadrant Chopper and Auxiliary Capacitor", THE INSTITUTE OF ELECTRICAL ENGINEERS OF JAPAN TRANSACTIONS D, vol. 112, no. 7, 1992, pages 623 - 629 |
OHNUMA; ITOH: "Circuit Configuration and Control Strategy of single-to-three Phase Power Converter with Active Buffer and Charge Circuit", THE 2010 ANNUAL MEETING OF THE INSTITUTE OF ELECTRICAL ENGINEERS OF JAPAN, 2010, pages 4 - 057 |
OHNUMA; ITOH: "Comparison between a Boost Chopper and an Active Buffer as a Single to Three Phase Converter", THE 2011 ANNUAL MEETING OF THE INSTITUTE OF ELECTRICAL ENGINEERS OF JAPAN, 2011, pages 4 - 042 |
Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN108450057A (zh) * | 2015-12-28 | 2018-08-24 | 大金工业株式会社 | 功率转换装置的控制装置 |
CN108450057B (zh) * | 2015-12-28 | 2019-08-06 | 大金工业株式会社 | 功率转换装置的控制装置 |
US10951152B2 (en) | 2018-03-29 | 2021-03-16 | Daikin Industries, Ltd. | Power conversion apparatus |
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CN105556817A (zh) | 2016-05-04 |
AU2014322275B2 (en) | 2017-06-29 |
EP3048718A4 (en) | 2017-05-17 |
CN105556817B (zh) | 2018-01-19 |
US20160294300A1 (en) | 2016-10-06 |
JP5804167B2 (ja) | 2015-11-04 |
JP2015084637A (ja) | 2015-04-30 |
EP3048718A1 (en) | 2016-07-27 |
AU2014322275A1 (en) | 2016-04-28 |
ES2886801T3 (es) | 2021-12-20 |
US9780683B2 (en) | 2017-10-03 |
EP3048718B1 (en) | 2021-08-04 |
SG11201602139SA (en) | 2016-04-28 |
BR112016005958A2 (pt) | 2017-08-01 |
MY174263A (en) | 2020-04-01 |
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