WO2013007623A2 - Verfahren zur ansteuerung einer mehrphasigen maschine - Google Patents
Verfahren zur ansteuerung einer mehrphasigen maschine Download PDFInfo
- Publication number
- WO2013007623A2 WO2013007623A2 PCT/EP2012/063222 EP2012063222W WO2013007623A2 WO 2013007623 A2 WO2013007623 A2 WO 2013007623A2 EP 2012063222 W EP2012063222 W EP 2012063222W WO 2013007623 A2 WO2013007623 A2 WO 2013007623A2
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- WIPO (PCT)
- Prior art keywords
- phase
- current
- drive
- phases
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Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
- H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
- H02M7/53873—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current with digital control
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
- H02M7/53878—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current by time shifting switching signals of one diagonal pair of the bridge with respect to the other diagonal pair
Definitions
- the invention relates to a method for controlling a multi-phase machine.
- Electric rotary field drives are known. Different types of modulation are used. Widely used in polyphase drives is the use of pulse width modulation (PWM). A control of such rotary field drives is carried out depending on the respective requirements by one of the following methods:
- start-stop systems serve to stop and restart an internal combustion engine for the purpose of reducing fuel consumption and exhaust emissions.
- a start-stop system developed by the applicant works on the basis of conventional starters. In this case, the respective starter is controlled by an electronic control unit and engages by means of a pinion in a ring gear provided on the flywheel.
- boost converter For vehicles with voltages greater than 14 V and 42 V, for example, it is already known to use a boost converter. This makes it possible to allow a current output of the generator before reaching an open circuit voltage of 42 V.
- a device and a method for controlling a generator with associated voltage converter are known, wherein the voltage converter operates as a boost converter. Said control takes place in at least two subregions, which are defined as speed ranges or as voltage ranges, in different ways.
- a first, subordinate control device is used to control the voltage operating as a boost converter transducer.
- a second control device serves as a regulator for the excitation current flowing through the field winding of the generator. Both control devices communicate with each other and exchange information.
- the subordinate control for the step-up converter is conventionally realized by means of a center-centered PWM control (center-aligned drive) in which the drive ratio is continuously increased. This variation of the drive ratio is accompanied by a high DC link current.
- the presence of a high intermediate circuit current is critical because the DC link capacitor is exposed to high ambient temperatures and the ambient temperatures mentioned and the DC link current determine the service life of the DC link capacitor.
- a reduction of the DC link current opens up the possibility of using smaller capacity DC link capacitors, which leads to cost advantages.
- Another advantage is the possibility of increasing the maximum permitted ambient temperatures by reducing the internal power loss of the DC link capacitor.
- a method with the features specified in claim 1 has the advantage that the intermediate circuit currents occurring are minimized. It offers a drive strategy especially for electric generators in the
- a drive connected to a battery multiphase machine which has a provided with an intermediate circuit capacitor DC link and per phase has a high-side switch and a low-side switch, wherein the individual phases associated switches of a control unit are supplied with control signals, wherein the control unit for reducing the DC link current control signals for the individual phases associated switches such that sinusoidal phase currents are given, at any time of each An horrzyklusses at least one phase current is switched on and for each drive cycle a fixed ge - Pulstes control pattern is present, in which the control widths of the phases associated with the drive signals are constant.
- FIG. 2 shows diagrams for illustrating a known center-aligned drive pattern and occurring currents
- FIG. 3 shows an enlarged detail of the diagrams shown in FIG. 2,
- FIG. 4 shows diagrams for illustrating a five-phase sine system
- FIG. 5 shows diagrams for illustrating a first improved control pattern and the intermediate circuit current occurring in the process
- FIG. 6 shows diagrams for illustrating a second improved control pattern and the intermediate circuit current occurring in the process
- Figure 7 shows a Anberichtmuster according to a first embodiment of the
- FIG. 8 shows a drive pattern according to a second exemplary embodiment of the invention
- FIG. 9 shows a drive pattern according to a third exemplary embodiment of the invention
- Phase currents are shown as a function of the driving time
- FIG. 1 diagrams in which the courses of DC link, battery and
- FIG. 12 shows diagrams for illustrating the DC link current during a speed ramp-up when using a known center-aligned drive pattern
- FIG. 13 Diagrams for illustrating the DC link current during a speed ramp-up when using a drive pattern according to the invention.
- the invention relates to a method for controlling a multiphase machine connected to a battery, which has a DC link capacitor provided with a DC link and per phase a high-side switch and a low-side switch, wherein the individual phases associated switch from a control unit with control signals be charged.
- This method is not bound to a specific number of phases of the machine, but will be explained in more detail below using a five-phase machine.
- Drudenfußverscnies is understood as an interconnection type in which the total of five phase windings of the circuit are electrically connected to each other such that the shape of the circuit diagram yields a pentagram.
- the machine shown has a total of five phase terminals A1, A2, A3, A4, A5 and a total of five phase windings 1, 2, 3, 4, 5, wherein each of these phase windings is connected between two of said phase terminals. Furthermore, the machine shown has a power electronics LE connected to the phase terminals and a battery B. The battery B has a positive terminal B + and a negative terminal B-. Between the battery B and the power electronics LE is a DC link ZK, which contains a DC link capacitor C_ZK.
- Power electronics LE includes five branches Ph1, Ph2, Ph3, Ph4 and Ph5, each of which has a series connection of two switches, with each of these switches having a diode connected in anti-parallel. This arrangement results in the use of conventional field effect transistors as switches, since these include an inverse diode. In principle, however, the use of other switching elements, such as IGBTs possible.
- the branch Ph1 of the power electronics LE which contains the switches HS1 and LS1, is connected at a connection point between the two switches HS1 and LS1 to the phase connection A1 of the stator of the machine.
- the switch HS1 of the branch Ph1 is a highside switch. Anti-parallel to the switch HS1, a diode is connected.
- the switch LS1 of the branch Ph1 is a low-side switch. Anti-parallel to the switch LS1, a diode is connected.
- the switches HS1 and LS1 are controlled by a control unit S with control signals S1 and S2.
- the branch Ph2 of the power electronics LE which contains the switches HS2 and LS2, is connected at a connection point between the two switches HS2 and LS2 to the phase connection A2 of the stator of the machine.
- HS2 of branch Ph2 is a highside switch. Anti-parallel to the switch HS2, a diode is connected.
- Switch LS2 of branch Ph2 is a low side switch. Anti-parallel to the switch LS2, a diode is connected.
- the switches HS2 and LS2 are controlled by the control unit S with control signals S3 and S4.
- the branch Ph3 of the power electronics LE which includes the switches HS3 and LS3, is connected at a connection point between the two switches HS3 and LS3 to the phase terminal A3 of the stator of the machine.
- Switch HS3 of branch Ph3 is a highside switch. Anti-parallel to the switch HS3, a diode is connected.
- Switch LS3 of branch Ph3 is a low-side switch. Anti-parallel to the switch LS3, a diode is connected.
- the switches HS3 and LS3 are controlled by the control unit S with control signals S5 and S6.
- the branch Ph4 of the power electronics LE which includes the switches HS4 and LS4, is connected at a connection point between the switches HS4 and LS4 to the phase terminal A4 of the stator of the machine.
- Switch HS4 of branch Ph4 is a highside switch. Anti-parallel to the switch HS4, a diode is connected.
- the switch LS4 of the branch Ph4 is a low-side switch. At- Tiparallel to the switch LS4 is a diode connected.
- the switches HS4 and LS4 are controlled by the control unit S with control signals S7 and S8.
- the branch Ph5 of the power electronics LE which includes the switches HS5 and LS5, is connected to the phase terminal A5 of the stator of the machine at a connection point between the two switches HS5 and LS5.
- Switch HS5 of branch Ph5 is a highside switch. Antiparallel to the switch HS5 is a diode connected.
- Switch LS5 of branch Ph5 is a low side switch. Antiparallel to the switch LS5 is a diode connected.
- the switches HS5 and LS5 are controlled by the control unit S with control signals S9 and S10.
- l_ZK l_Bat - l_Gen.
- the generator current I_Gen results from a superposition of the phase currents I_1 to I_5 for those phases whose high-side switch is turned on at the respective instant.
- FIG. 2 a the control signals for the switches, in the FIG. 2 b the DC link current I_ZK, in FIG. 2 c the voltage V_B + applied to the positive pole of the battery, in FIG. 2 d the battery current I_Bat and in FIG. 2 e the phase currents I_X to I_Y shown.
- FIG. 2d shows the battery current I_Bat and FIG. 2E shows the phase currents I_X to I_Y, which make a contribution to the DC link current or not depending on the position of the respectively associated highside switch.
- FIG. 3 shows an enlarged detail of the diagrams shown in FIG. 3a, in turn, the control signals for the switches, in FIG. 3b the DC link current I_Zk, in FIG. 3C the voltage V_B + applied to the positive pole of the battery, in FIG. 3d the battery current I_Bat and in FIG. 3e the phase currents I_X to l_Y shown.
- the intermediate circuit current I_ZK is formed by a superimposition of the battery current I_Bat with the respective active phase current (s) and that in the case of a through-connection of the high-side switches associated with the phase connections X, U and W, a high intermediate level circulating current, which in the present example is about-420 A, while the battery current is about 80A and the effective phase current is about 200A.
- the arithmetic mean of the capacitor current is zero in the case of neglecting the intrinsic losses.
- the RMS value increases sharply when the currents are heavily added up; H. Due to this large increase of the RMS value, the thermal load of the DC link capacitor is high, Such a high thermal load, as occurs when using a center-aligned drive, is avoided in a method according to the invention.
- FIG. 4a shows a diagram to illustrate a five-phase sinusoidal system, as used in DE 10 201 1076676, in which diagram the phase sequence is changed in comparison to the diagrams shown in FIGS. 2 and 3.
- the associated phase currents are denoted by U, V, W, X and Y.
- An upper limit is denoted by G_o and a lower limit by G_u. These limit values are illustrated by dashed lines in FIG. 4a.
- the upper limit G_o is slightly smaller than the maximum positive target voltage value.
- the other limit value G_u is slightly larger than the minimum negative target voltage value.
- G_o U_Soll_amplitude * cos (360 (4 * PZ))
- G_u -G_o, where PZ is the phase number of the machine.
- the control unit provides in successive drive cycles pulse-shaped control signals for the switches whose pulse widths and pulse starts are each varied within a drive cycle such that the DC link current is reduced.
- angular intervals or fiattop windows ai, a10 are marked in which voltage presets exist in the sense that either the nominal voltage value assigned to a current phase is greater than the upper limit value G_o or less than the lower limit value G_u. If the nominal voltage value assigned to a current phase is greater than the upper limit value G_o, then the associated highside switch is controlled through in the associated angular interval. If, on the other hand, the nominal voltage value assigned to a current phase is smaller than the lower limit value G_u, then the associated low-side switch is controlled in the associated angular interval, as will be explained below with reference to FIG.
- the sinusoidal signals correspond to the nominal voltage specifications.
- FIGS. 4a and 4b It can be seen from FIGS. 4a and 4b that
- FIG. 5 shows diagrams for illustrating a control pattern in accordance with the invention described in DE 10 201 1076 676 and the DC link current occurring in the process. The control pattern is shown in FIG.
- phase currents are avoided by appropriately shifting the associated drive pulses within a drive period. This shift can be done arbitrarily without limiting the effect of a sine commutation within a drive period. Consequently, the effective DC link current can be further reduced if the control of the phases whose two switches are not turned on in the current Fiattoprate, relative to each other are shifted so that overlaps of positive or negative
- Phase currents are avoided and / or that positive and negative phase currents compensate each other at least partially.
- FIG. 6 shows diagrams for illustrating a drive pattern according to the development described above, according to which a superimposition of positive and negative phase currents takes place in such a way that the intermediate phase is reduced circle, the occurring DC link current and associated instantaneous current values.
- the drive pattern and the DC link current are shown in FIG. 6a and the associated instantaneous current values are shown in FIG. 6b.
- the DC link current can be reduced by up to 40% compared to a conventional center-aligned drive.
- sinusoidal setpoint current or setpoint voltage specifications are used.
- the drive duration or the battery current is varied so that the pulses of the pulse pattern move towards each other until, in the example described above, ideally the drive pulses for the phases X and Y abut each other exactly flush.
- the resulting pulse pattern and the associated DC link current are illustrated in FIG. 7, which shows a pulse pattern according to a first exemplary embodiment of the invention. From a comparison of FIGS. 6 and 7, it can be seen that, in the case of a control according to FIG. 6, an effective DC link current of approximately 100 A occurs with the same phase current, while in the case of a drive according to FIG. 7 an effective DC link current of approximately 40 A occurs occurs. Since the pulse pattern still ensures freewheeling phases, for example, a Hochsetzsteller compassion compassion with minimal DC link current is possible.
- the pulse pattern according to FIG. 7 is characterized in that the drive pulses for the phases U and W are arranged "below” the drive pulse for the phase Y and that the drive pulse for the phase X is exactly flush with the drive pulse for the phase Y
- the phase V is continuous turned on. After every 18 degrees, the pulse arrangement is changed.
- the drive pulses for the phases U and W are arranged after 18 angular degrees "below” the drive pulse for the phase X. Thereafter, a changeover to a low-side flattop with a corresponding change of the drive pulses similar to FIG.
- FIG. 8 shows, as a second exemplary embodiment of the invention, an alternative drive pattern which likewise leads to a reduction of the DC link current.
- the effective phase and battery current are approximately in the ratio 3: 4.
- Such a pulse pattern can be advantageously used when lower battery currents are requested in a boost converter operation.
- no flattop method is used, since all five phases are switched within a drive cycle here.
- the phase V drive window is located exactly on the edges of the drive pulses for phase X and phase Y.
- FIG. 9 shows as a third embodiment of the invention a drive pattern for a three-phase machine in which the resulting intermediate circuit current is reduced .
- This control pattern is characterized in that within a An horrzyklusses no time gaps occur or that within each An horrzyklusses always a phase current is switched through, that the sum of the predetermined sinusoidal phase currents is equal to the battery current and that for the duration of a An horrzyklusseses a fixed , unmodified control pattern is used.
- FIG. 10 shows diagrams in which the courses of DC link, battery and phase currents are shown as a function of the drive duration.
- the currents are shown, as in the case of known center-aligned drive occur, and in the figure 10b, the currents mentioned, as they are in the case of a drive pattern according to the figure 7. It can be seen that in both cases the height of the intermediate circuit current depends on the control width. It can be seen from FIG. 10b that there is a minimum DC link current at a control duration of 0.6 and that, in this case, a halving of the DC link current can be achieved in comparison with a center-aligned triggering.
- FIG. 11 shows diagrams in which, in the case of an engine start, the progress of DC link, battery and phase currents is dependent on the
- FIG. 12 illustrates a simulation of a speed-up of an electric machine in the case of a known center-aligned drive, wherein this speed ramp-up takes place linearly from 0 rpm to 1000 rpm in 0.3 s. It can be seen that in this case an effective DC link current is established whose average value is 164 A.
- FIG. 13 illustrates a simulation of a speed-up of an electric machine in the case of a drive strategy according to the invention, wherein here too the speed ramp-up takes place linearly from 0 rpm to 1000 rpm in 0.3 s. It can be seen that, when using a control pattern according to the invention, an effective DC link current is established, its mean value being at
- pulse patterns For electrical machines whose phase number is greater than 5, results in a higher number of pulse patterns according to the invention, which lead to reduced Zwenk cycles. These pulse patterns are determined in advance and permanently stored in the sequence control of the respective system. A regulation of the generator current via a gradation using the individual pulse pattern, the exciter current of the machine, the commutation angle, a pulsed battery current on a higher time level with buffering in the battery or a combination of these measures.
- a method for controlling a multiphase machine according to the invention is advantageously suitable for reducing the effective intermediate circuit current, in particular in a boost converter mode, but can also be used in motor operation of the machine.
- a simple calculation of the switching pulses of the switches assigned to the phases can take place independently of the current rotational speed and independently of the current phase position.
- a method according to the invention is applicable to machines having an arbitrary number of phases, but in particular to machines whose phase number is greater than 3.
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- Control Of Ac Motors In General (AREA)
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Abstract
Description
Claims
Priority Applications (4)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US14/131,647 US9312802B2 (en) | 2011-07-08 | 2012-07-06 | Method for controlling a multiphase machine |
CN201280034017.8A CN103650322A (zh) | 2011-07-08 | 2012-07-06 | 用于操控多相电机的方法 |
BR112014000291A BR112014000291A2 (pt) | 2011-07-08 | 2012-07-06 | método para ativação de uma máquina de fases múltiplas |
JP2014517817A JP2014528229A (ja) | 2011-07-08 | 2012-07-06 | 多相機械を制御する方法 |
Applications Claiming Priority (6)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
DE102011078842.5 | 2011-07-08 | ||
DE102011078842 | 2011-07-08 | ||
EPPCT/EP2012/062324 | 2012-06-26 | ||
PCT/EP2012/062324 WO2013007512A2 (de) | 2011-07-08 | 2012-06-26 | Verfahren zur ansteuerung einer mehrphasigen maschine |
DE102012211802.0 | 2012-07-06 | ||
DE102012211802A DE102012211802A1 (de) | 2011-07-08 | 2012-07-06 | Verfahren zur Ansteuerung einer mehrphasigen Maschine |
Publications (3)
Publication Number | Publication Date |
---|---|
WO2013007623A2 true WO2013007623A2 (de) | 2013-01-17 |
WO2013007623A3 WO2013007623A3 (de) | 2013-10-10 |
WO2013007623A8 WO2013007623A8 (de) | 2014-07-17 |
Family
ID=46397244
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Application Number | Title | Priority Date | Filing Date |
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PCT/EP2012/062324 WO2013007512A2 (de) | 2011-07-08 | 2012-06-26 | Verfahren zur ansteuerung einer mehrphasigen maschine |
PCT/EP2012/063222 WO2013007623A2 (de) | 2011-07-08 | 2012-07-06 | Verfahren zur ansteuerung einer mehrphasigen maschine |
Family Applications Before (1)
Application Number | Title | Priority Date | Filing Date |
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PCT/EP2012/062324 WO2013007512A2 (de) | 2011-07-08 | 2012-06-26 | Verfahren zur ansteuerung einer mehrphasigen maschine |
Country Status (5)
Country | Link |
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JP (1) | JP2014528229A (de) |
CN (1) | CN103650322A (de) |
BR (1) | BR112014000291A2 (de) |
DE (1) | DE102012211802A1 (de) |
WO (2) | WO2013007512A2 (de) |
Families Citing this family (1)
Publication number | Priority date | Publication date | Assignee | Title |
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FR3076124B1 (fr) * | 2017-12-22 | 2019-11-22 | Valeo Equipements Electriques Moteur | Systeme electrique comportant un onduleur statorique et un dispositif electrique auxiliaire, destines a etre connectes a une source de tension |
Citations (1)
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DE19903426A1 (de) | 1999-01-29 | 2000-08-03 | Bosch Gmbh Robert | Vorrichung und Verfahren zur Regelung eines Generators mit zugeordnetem Spannungswandler |
Family Cites Families (18)
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JP2765857B2 (ja) * | 1988-06-24 | 1998-06-18 | 株式会社日立製作所 | Pwm電力変換装置 |
JP3250329B2 (ja) * | 1993-08-02 | 2002-01-28 | トヨタ自動車株式会社 | インバータの二相pwm制御装置 |
JP3677804B2 (ja) * | 1994-03-10 | 2005-08-03 | 株式会社デンソー | インバータ制御装置 |
JP3337119B2 (ja) * | 1997-03-11 | 2002-10-21 | 株式会社日立製作所 | Pwm制御装置 |
DE19947476A1 (de) * | 1999-10-01 | 2001-04-05 | Bosch Gmbh Robert | Umrichter für die Umformung von elektrischer Energie |
DE10112820A1 (de) * | 2001-03-16 | 2002-10-02 | Bosch Gmbh Robert | Verfahren zur Messung von Strömen in Multiphasenwandlern mit Strommesselement-Auslösung |
JP2005000510A (ja) * | 2003-06-13 | 2005-01-06 | Toshiba Corp | 洗濯機およびインバータ装置 |
JP2005051838A (ja) * | 2003-07-29 | 2005-02-24 | Toyota Industries Corp | インバータ装置及びリップル電流の低減方法 |
DE10346060A1 (de) * | 2003-10-04 | 2005-05-12 | Sensor Technik Wiedemann Gmbh | Verfahren zum Betreiben einer Drehfeldmaschine und Wechselrichter dafür |
JP4199144B2 (ja) * | 2004-03-11 | 2008-12-17 | 株式会社東芝 | ウェイト関数生成装置、参照信号生成装置、送信信号生成装置、信号処理装置及びアンテナ装置 |
JP2009232546A (ja) * | 2008-03-21 | 2009-10-08 | Nissan Motor Co Ltd | モータ制御装置 |
US8269434B2 (en) * | 2008-09-23 | 2012-09-18 | GM Global Technology Operations LLC | Electrical system using phase-shifted carrier signals and related operating methods |
US8115433B2 (en) * | 2008-09-23 | 2012-02-14 | GM Global Technology Operations LLC | Electrical system for pulse-width modulated control of a power inverter using phase-shifted carrier signals and related operating methods |
DE102008042352A1 (de) * | 2008-09-25 | 2010-04-08 | Robert Bosch Gmbh | Ansteuerung eines Synchrongleichrichters |
DE102009045489A1 (de) * | 2009-10-08 | 2011-04-21 | Robert Bosch Gmbh | Verfahren zum Überwachen eines Gleichrichters |
DE102009046955A1 (de) * | 2009-11-23 | 2011-05-26 | Robert Bosch Gmbh | Vermeidung von Lastabwurf-Überspannungen bei Synchrongleichrichtern |
US8233294B2 (en) * | 2010-08-23 | 2012-07-31 | Ford Global Technologies, Llc | Method and system for controlling a power converter system connected to a DC-bus capacitor |
DE102011076676A1 (de) | 2011-05-30 | 2012-12-06 | Robert Bosch Gmbh | Verfahren zur Ansteuerung einer mehrphasigen Maschine |
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2012
- 2012-06-26 WO PCT/EP2012/062324 patent/WO2013007512A2/de active Application Filing
- 2012-07-06 JP JP2014517817A patent/JP2014528229A/ja active Pending
- 2012-07-06 WO PCT/EP2012/063222 patent/WO2013007623A2/de active Application Filing
- 2012-07-06 DE DE102012211802A patent/DE102012211802A1/de not_active Withdrawn
- 2012-07-06 BR BR112014000291A patent/BR112014000291A2/pt not_active IP Right Cessation
- 2012-07-06 CN CN201280034017.8A patent/CN103650322A/zh active Pending
Patent Citations (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DE19903426A1 (de) | 1999-01-29 | 2000-08-03 | Bosch Gmbh Robert | Vorrichung und Verfahren zur Regelung eines Generators mit zugeordnetem Spannungswandler |
Also Published As
Publication number | Publication date |
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CN103650322A (zh) | 2014-03-19 |
WO2013007512A2 (de) | 2013-01-17 |
JP2014528229A (ja) | 2014-10-23 |
WO2013007623A3 (de) | 2013-10-10 |
WO2013007623A8 (de) | 2014-07-17 |
WO2013007512A3 (de) | 2013-10-17 |
BR112014000291A2 (pt) | 2017-02-07 |
DE102012211802A1 (de) | 2013-01-10 |
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