WO2012137494A1 - Réactance et procédé d'évaluation de celle-ci - Google Patents

Réactance et procédé d'évaluation de celle-ci Download PDF

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Publication number
WO2012137494A1
WO2012137494A1 PCT/JP2012/002340 JP2012002340W WO2012137494A1 WO 2012137494 A1 WO2012137494 A1 WO 2012137494A1 JP 2012002340 W JP2012002340 W JP 2012002340W WO 2012137494 A1 WO2012137494 A1 WO 2012137494A1
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Prior art keywords
core
reactor
air
coil
protrusion
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PCT/JP2012/002340
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English (en)
Japanese (ja)
Inventor
井上　憲一
享司 財津
裕志 橋本
三谷　宏幸
Original Assignee
株式会社神戸製鋼所
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Priority to CN201280010301.1A priority Critical patent/CN103403817B/zh
Publication of WO2012137494A1 publication Critical patent/WO2012137494A1/fr

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F37/00—Fixed inductances not covered by group H01F17/00
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F41/00—Apparatus or processes specially adapted for manufacturing or assembling magnets, inductances or transformers; Apparatus or processes specially adapted for manufacturing materials characterised by their magnetic properties
    • H01F41/02—Apparatus or processes specially adapted for manufacturing or assembling magnets, inductances or transformers; Apparatus or processes specially adapted for manufacturing materials characterised by their magnetic properties for manufacturing cores, coils, or magnets
    • H01F41/0206—Manufacturing of magnetic cores by mechanical means
    • H01F41/0246—Manufacturing of magnetic circuits by moulding or by pressing powder
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F1/00—Magnets or magnetic bodies characterised by the magnetic materials therefor; Selection of materials for their magnetic properties
    • H01F1/01—Magnets or magnetic bodies characterised by the magnetic materials therefor; Selection of materials for their magnetic properties of inorganic materials
    • H01F1/03—Magnets or magnetic bodies characterised by the magnetic materials therefor; Selection of materials for their magnetic properties of inorganic materials characterised by their coercivity
    • H01F1/12—Magnets or magnetic bodies characterised by the magnetic materials therefor; Selection of materials for their magnetic properties of inorganic materials characterised by their coercivity of soft-magnetic materials
    • H01F1/34—Magnets or magnetic bodies characterised by the magnetic materials therefor; Selection of materials for their magnetic properties of inorganic materials characterised by their coercivity of soft-magnetic materials non-metallic substances, e.g. ferrites
    • H01F1/342—Oxides
    • H01F1/344—Ferrites, e.g. having a cubic spinel structure (X2+O)(Y23+O3), e.g. magnetite Fe3O4
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F27/00—Details of transformers or inductances, in general
    • H01F27/24—Magnetic cores
    • H01F27/255—Magnetic cores made from particles
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F27/00—Details of transformers or inductances, in general
    • H01F27/28—Coils; Windings; Conductive connections
    • H01F27/2847—Sheets; Strips

Definitions

  • the present invention relates to a reactor evaluation method for evaluating a reactor and a reactor having a suitable shape determined from the evaluation method, and in particular, in order to increase inductance, cores are arranged at both ends and an outer peripheral portion of an air-core coil. Reactor related.
  • FIG. 48 is a perspective view for explaining a method of creating reactor DP according to Patent Document 1.
  • an air-core coil 101 formed by winding a long strip-shaped conductor 110 in its thickness direction is replaced with that shown in FIG. ) To (D), it is formed by being housed in a core 102 composed of a pair of core members 103 and 104.
  • the core members 103 and 104 include cylindrical outer peripheral portions 103a and 104a, and end plates 103b and 104b that close one end and become diameter portions.
  • the air-core coil 101 is accommodated in the recesses 103c and 104c thus formed.
  • the outer peripheral parts 103a and 104a should just be able to form a magnetic path (yoke), and may be another shape.
  • one core member 103 is an outer peripheral portion having a length corresponding to the total length of two outer peripheral portions 103a and 104a, and the other core member 104 is only an end plate 103b fitted into the outer peripheral portion.
  • the way of assigning these outer peripheral portions 103a and 104a is arbitrary. However, by forming the two outer peripheral portions 103a and 104a to have the same height, the core members 103 and 104 can have the same shape (can be made with the same mold), and such an allocation method can be used. Is preferred.
  • Patent Document 1 when the radius A of the bottom surfaces (opposing surfaces) of the protrusions 103d and 104d is r, the radius of the air core SP of the air core coil 101 is r, and the width of the strip conductor 110 is W. R> ⁇ (A 2 + (W / 2) 2 ). That is, in Patent Document 1, the radius r of the air core part is formed larger than the distance R1 from the center P0 of the reactor DP (air core coil 101) to the outer peripheral edge P1 of the protrusion parts 103d, 104d, and the protrusion part 103d. , 104d, the reactor DP is configured to move away the air-core coil 101.
  • the reactor DP is configured such that the leakage magnetic flux of the protrusions 103d and 104d does not reach the strip conductor 110 on the inner peripheral side of the air-core coil 101, and the eddy current loss in the strip conductor 10 is suppressed. .
  • the core members 103 and 104 are formed of a magnetically isotropic material such as a powdered soft magnetic iron powder or a ferrite core in order to exhibit a three-dimensional shape.
  • the permeability ⁇ is assumed to be relatively high.
  • the above-described conventional technology assumes, for example, a several tens kW level that is used for hybrid or electric vehicles, for example, a few kW level that is used for a converter of a two-wheeled vehicle or a solar power generation device.
  • a desire to apply since the above-described conventional reactor DP has a relatively large power of several tens of kW and a large current, the distance between the opposing surfaces of the protrusions 103d and 104d is avoided in order to avoid magnetic saturation.
  • the reactor needs to reduce the gap g ′ and pass a large amount of magnetic flux.
  • the above-described prior art reactor DP suppresses the eddy current loss of the strip conductor 110 due to the leakage magnetic flux l.
  • the core material is low and the capacity is small as described above. As a result, it was found that the hysteresis loss of the core also becomes a problem.
  • the present invention has been made in view of the above circumstances, and an object thereof is to provide a reactor and a reactor evaluation method capable of reducing the hysteresis loss of the core while ensuring the inductance.
  • a reactor according to the present invention includes an air-core coil, and a core that is disposed outside the air-core coil and includes a projecting portion that enters the air-core portion of the air-core coil.
  • the sectional area is S
  • the gap length between the protrusions is g
  • the gap permeability is ⁇ 0
  • the reactor's target inductance is L
  • the number of turns of the air-core coil is N
  • the coil current I
  • ge ⁇ 0 ⁇ N ⁇ I / Bc
  • Se L ⁇ ge / ⁇ 0 / N 2
  • ⁇ N / N 0
  • ⁇ Ge / g
  • ⁇ Se / S
  • the number N of turns of the air-core coil, the cross-sectional area S of the tip of the protrusion, the height of the protrusion, and the skirt shape of the protrusion are set.
  • the reactor having such a configuration can reduce the hysteresis loss of the core while ensuring the inductance.
  • the reactor evaluation method of the present invention is evaluated by the normalized parameters ⁇ , ⁇ , ⁇ .
  • FIG. 2 is a perspective view showing a magnetic circuit model when the core shown in FIG. 1 is a C-shaped core.
  • 3 is an equivalent circuit that electrically shows the magnetic circuit model shown in FIG. 2.
  • It is sectional drawing for demonstrating the core structural parameter of the core in the reactor of embodiment.
  • It is a figure which shows an example of the phase diagram by the combination of the normalization parameter calculated
  • It is a figure which shows the cross-sectional shape of a one part specific reactor among the some samples shown to the phase diagram shown in FIG. 5, and the magnetic flux line generated.
  • FIG. 3 It is a perspective view which shows the core structure of the other 1st aspect in the reactor shown in FIG. It is a perspective view which shows the core structure of the other 2nd aspect in the reactor shown in FIG. 3 is a graph showing magnetic flux density-relative permeability characteristics at each density of an iron powder core. It is a figure which shows the relationship between the structure of a reactor, and a magnetic flux line. It is a graph which shows the experimental result of the change of the inductance with respect to an electric current change in the reactor concerning embodiment and a comparative example. It is sectional drawing of a reactor which has an air core coil of an edgewise winding structure. It is a graph which shows the relationship between the frequency and loss in the reactor of a flatwise winding structure and an edgewise winding structure.
  • the later-described embodiments similarly have a relatively low permeability such as a dust core and a ferrite core instead of an ideal high magnetic permeability and low hysteresis loss high-grade electromagnetic steel sheet as described above.
  • a relatively low permeability such as a dust core and a ferrite core
  • an inexpensive lower magnetic material having a large hysteresis characteristic (loop) is used for the core, it is as close as possible when an electromagnetic steel sheet is used within a wide material range of the lower magnetic material.
  • a core geometry is defined that can achieve low loss reactor performance. As described above, most of the reactor loss in the lower magnetic material is the hysteresis loss of the material. The value of the hysteresis loss is proportional to the magnetic flux density Bc in the core material.
  • the inductance L is expressed by the following equation (1 ).
  • the magnetic permeability ⁇ c in the magnetic pole is sufficiently larger than the magnetic permeability ⁇ 0 of the magnetic pole gap.
  • the magnetic flux density Bc can be expressed by the following equation (2), where I is the current flowing through the winding.
  • the magnetic flux density Bc represents the magnetic flux density near the center of the gap. Therefore, for the purpose described above, the combination of geometric structure parameters (N, g, S) that minimizes the magnetic flux density Bc may be optimized.
  • N 0 the number of turns N 0 when an ideal core material ( ⁇ c >> ⁇ 0 ) is used is also defined by the following equation (5).
  • N 0 ⁇ (L ⁇ g / ⁇ 0 / S) (5)
  • each geometric structure parameter (N 0 , ge, Se) and the actual geometric structure parameter (N, g, S) Introducing original normalization parameters ⁇ , ⁇ , ⁇ defined by The material and structure of the reactor are evaluated by a combination of the values of these normalization parameters ⁇ , ⁇ , and ⁇ , and the optimum shape is determined.
  • FIG. 1 is a perspective view showing an assembled state for explaining the basic structure of the reactor in the embodiment.
  • FIG. 46 is a magnetic flux diagram in the reactor shown in FIG.
  • FIG. 47 is a cross-sectional view showing the core structure when the reactor shown in FIG.
  • FIG. 2 is a perspective view showing a magnetic circuit model when the core shown in FIG. 1 is a C-shaped core.
  • FIG. 3 is an equivalent circuit electrically showing the magnetic circuit model shown in FIG.
  • Drawing 4 is a sectional view for explaining the core structure parameter of the core in the reactor of an embodiment.
  • the reactor D ⁇ b> 1 in the first embodiment is an air core formed by winding a strip-shaped conductor member 10 so that the width direction of the conductor member 10 is along the axial direction of the coil 1.
  • a coil 1 and a core 2 made of a magnetically isotropic material and disposed outside the air-core coil 1 are provided.
  • the core 2 includes outer peripheral portions 3a and 4a that cover at least part of the outer periphery of the air-core coil 1, diameter portions 3b and 4b that cover at least part of both end portions of the air-core coil 1, and the center of the diameter portions 3b and 4b.
  • the protrusions 3d and 4d that enter the air core portion of the air core coil 1 and allow the magnetic flux to pass therethrough.
  • the core 2 includes a pair of core members 3 and 4, and these core members 3 and 4 are cylindrical outer peripheral portions 3 a and 4 a and end plates that close one end and become a diameter portion. 3b and 4b.
  • the air-core coil 1 is accommodated in the recesses 3c and 4c thus formed.
  • outer peripheral parts 3a and 4a should just be able to form a magnetic path (yoke), and may be another shape.
  • one core member 3 is an outer peripheral portion having a length corresponding to the total length of two outer peripheral portions 3a and 4a, and the other core member 4 is only an end plate 3b fitted into the outer peripheral portion.
  • These outer peripheral portions 3a and 4a are arbitrarily assigned.
  • the reactor D1 includes an air-core coil 1 formed by winding a long strip-shaped conductor 10 in the thickness direction, as shown in FIGS. As shown by (), it is formed by being housed in a core 2 composed of a pair of core members 3 and 4.
  • the number N of turns of the strip-shaped conductor 10 in the air-core coil 1, the shape of the core members 3, 4, and the protrusions are adapted to the desired inductance L and the material (magnetic permeability ⁇ c) of the core members 3, 4.
  • Geometric structures such as 3d and 4d shapes (cross-sectional areas S, Se and gap length g) are determined based on the above-described concept.
  • the shape of the protrusions 3d and 4d changes particularly between the area of the proximal end side and typically changes from the truncated cone shape shown in FIGS. 1 and 46 to the cylindrical shape shown in FIG.
  • FIG. 2 is a perspective view showing a magnetic circuit model when the core shown in FIG. 1 is a C-shaped core.
  • the cylindrical shape shown in FIG. 47 is used as the shape of the protrusions 3d and 4d, and the air-core coil 1 is shown divided at the gap portion.
  • the magnetic flux density at the core 2 (return yoke portion) is By, the magnetic flux density at the protrusions 3d and 4d (magnetic poles) is Bp, the magnetic flux density at the gap is Bg,
  • the cross-sectional area of the core 2 is Sy
  • the cross-sectional area of the protrusions 3d and 4d is Sp
  • the cross-sectional area of the gap is Sg
  • the relationship of the following formula (9) is established.
  • the relationship with the cross-sectional area S can be expressed by the following equation (14) when the radius of the tip of the protrusions 3d and 4d is R 0 in FIG. it can.
  • the effective value Se corresponds to the area of the magnetic flux leaking from the gap to the vicinity of the coil, and can be interpreted as a cross-sectional area when the integral of the magnetic flux lines is approximated to a rectangle. Can be expressed as
  • FIG. 4 also shows the relationship between the cross-sectional area S in the vicinity of the tip portions of the protrusions 3d and 4d and the effective value thereof, that is, the cross-sectional area Se in the vicinity of the base end portion.
  • the normalization parameters ⁇ , ⁇ , ⁇ will be described.
  • the space of the normalization parameters ⁇ , ⁇ , ⁇ can be expressed in the form of a so-called ternary alloy phase diagram, and the results for changes in the normalization parameters ⁇ , ⁇ , ⁇ can be easily recognized.
  • Three optimization parameters ⁇ , ⁇ , and ⁇ were set.
  • the scales of all three sides are logarithmic scales, enlarged according to the order, and inverted if they are reciprocals.
  • FIG. 5 is an example of a phase diagram created by the present inventors.
  • FIG. 5 is a diagram showing an example of a phase diagram based on a combination of standardization parameters obtained from the core structure parameters.
  • the scale and polarity of the shaft are appropriately adjusted as described above so as to enlarge the possible range (practical range) of each parameter ⁇ , ⁇ , ⁇ as will be described later.
  • the value of 1 for the parameters ⁇ , ⁇ , and ⁇ is not located at the center of the layer diagram.
  • nine samples A to I actually calculated by the present inventor are mapped and shown based on the obtained values of the parameters ⁇ , ⁇ , and ⁇ .
  • Table 1 shows the calculation results of the geometric structure parameters (L, N 0 , g, S, N, ge, Se) that are the basis of the mapping.
  • Samples A to F are samples of several kW level for applications such as relatively small power two-wheeled vehicles and converters of solar power generation devices. It is a sample of several tens of kW level for use in a relatively large power hybrid or electric vehicle.
  • Table 1 the analysis results of the effective cross-sectional area Se of the protrusions 3d and 4d are also shown. As shown in FIG. 4, the analysis was performed by integrating magnetic flux lines leaking from the gaps of the protrusions 3d and 4d to the coil region and approximating the integration result to a rectangle. That is, the following formula (20) was used for the analysis. As shown in Table 1, it is understood that this is almost the same as effective Se.
  • Table 1 and FIG. 5 explain some of the relationship between the mapping position in the phase diagram and the features of the actual geometric core structure.
  • the sample A is of higher magnetic steel plates
  • the number of turns N of the strip-shaped conductive member 10 is equal to the number of turns N 0 of the ideal
  • the effective value of the gap length ge equally to the actual gap length g
  • the value (if 0 ⁇ c> ⁇ ) If the gap is empty, always a ⁇ ⁇ 1.
  • ⁇ is asymptotic to 1 and ⁇ is also asymptotic to 1 ( ⁇ ⁇ 1, ⁇ ⁇ 1).
  • the magnetic resistance Ry of the core 2 return yoke portion
  • the magnetic resistance Rg of the gap ⁇ ⁇ 1.
  • the copper loss is increased, and when it is smaller than 1, the copper loss is decreased.
  • the total loss should be considered as the sum of hysteresis loss ( ⁇ Bc ⁇ / ⁇ ). Therefore, in Table 1, along with the geometry and analysis parameters, the actual measurement loss is also shown as a difference from the sample A for some samples.
  • the shape of the core 2 is optimized using the above items as design guidelines.
  • the constraint condition is 2g> ge> g, that is, 1 ⁇ ⁇ 2.
  • the gap length g is the maximum value, that is, when there are no protrusions (magnetic poles) 3d and 4d, Se ⁇ 3S, that is, so as not to exceed the outer shape of the coil (R / W ⁇ 4)
  • 1 ⁇ ⁇ ⁇ 3 is the actual solution.
  • the number of turns N is excessive, the length of the strip-shaped conductor member 10 is excessively increased and the cross-sectional area is excessively decreased, thereby causing an increase in copper loss. Therefore, it is preferable that 1/2 ⁇ ⁇ 2.
  • FIG. 5 shows shaded areas where ⁇ / ⁇ ⁇ 1 or ⁇ ⁇ ⁇ > 1 and 1/2 ⁇ ⁇ 2, 1 ⁇ ⁇ 2, 1 ⁇ ⁇ ⁇ 3. .
  • the magnetic pole gap (gap length g) is relatively wide, the magnetic flux lines are leaked to the air-core coil 1, the effective cross-sectional area Se on the magnetic pole (projection) surface is increased, and the magnetic pole The magnetic flux density Bc inside can be reduced.
  • the thickness t of the strip conductor 10 is equal to or less than the skin thickness ⁇ , and the air-core coil 1 is a flat-wise type substantially parallel to the leakage magnetic flux as described later.
  • the relationship between the normalization parameters ⁇ , ⁇ , ⁇ and the characteristics of the reactor is as follows.
  • Bc is the maximum value of the magnetic flux density at or around the center of the gap
  • ge of the gap length and the effective cross-sectional area Se of the protrusions (magnetic poles) 3d and 4d are When obtained, they are the following equations (22) and (23), respectively, and these two parameters can be easily obtained from the magnetic field analysis results.
  • the design policy of the reactor D1 of the present embodiment is that the desired number of turns N of the air-core coil 1 is smaller while the desired inductance L shown in Expression (16) is secured, and the protrusions (magnetic poles) 3d and 4d are effectively disconnected.
  • the empirical magnetic flux density of the core 2 can be reduced. It is to reduce the iron loss (mainly hysteresis loss) (by shifting the range of use of pure iron characteristics).
  • sample A is an example of a conventional reactor using a high-grade electromagnetic steel sheet as a core material as described above.
  • the core material volume is small (S is small) and the number of turns N is large.
  • the remaining samples B to I are obtained by using iron powder compression-molded core material for the core 2, and based on the design guidelines described above, using the sample B as a prototype, B ⁇ C ⁇ D ⁇ E And improved.
  • 5 and Table 1 for the samples B to G, more specific cross-sectional shapes of the reactors and generated magnetic flux lines are shown in accordance with (B) to (G) of FIG. . By referring to FIG. 6 together, the core shape can be better understood.
  • FIG. 6 is a diagram showing a specific cross-sectional shape of a reactor among a plurality of samples shown in the phase diagram shown in FIG. 5 and generated magnetic flux lines.
  • FIG. 7 is a diagram showing a change in magnetic flux density for a part of the samples in FIG.
  • ⁇ is slightly smaller than 1.
  • the magnetic flux density of the return yoke portion is high, that is, the magnetoresistance Ry of the return yoke portion is the gap magnetic field (mainly because the end plates 3b and 4b of the core members 3 and 4 are thin).
  • the resistance Rg is larger than the resistance Rg, and the hysteresis loss of the return yoke portion is increased accordingly.
  • ⁇ ⁇ 1 means an unbalance of the magnetic resistance between the gap and the return yoke as described above.
  • an increase in copper loss due to ⁇ > 1 and an excessive number of turns also significantly affects the loss increase.
  • the sample C is obtained by reducing ⁇ , that is, by reducing the number of turns N, and the air core coil 1 is made compact by the reduction of the number of turns N, as shown in FIGS. 7B to 7C.
  • the core 2 is enlarged (the end plates 3b and 4b are thickened).
  • this increases the magnetic flux density Bc and increases the hysteresis loss. Therefore, as shown in FIGS. 7C to 7D, the sample D is a more optimal design because the gap length g is increased, the magnetic flux density Bc is reduced, and the hysteresis loss is reduced. That is, due to the improvement of C ⁇ D, ⁇ > 1 slightly.
  • sample E is obtained by increasing the aspect ratio t / W of the strip-shaped conductor member 10 and flattening the air-core coil 1.
  • N N 0 and the effective value ge of the gap length is also large.
  • Sample F is obtained by reducing the density of the iron powder in the core 2 from that of the sample E. Therefore, the number of turns N is increased and the effective value ge of the gap length is decreased.
  • Samples G, H, and I are large power reactors having a large inductance L, and ⁇ / ⁇ ⁇ 0.8 or ⁇ ⁇ ⁇ > 1.25 and 1/2 ⁇ ⁇ 2, 1 ⁇ . ⁇ 2, 1 ⁇ ⁇ ⁇ 3 is satisfied.
  • Samples G, H, and I have densities of 7 g / cm 3 , 6 g / cm 3 , and 5 g / cm 3 , respectively.
  • sample I has ⁇ , that is, the shape of protrusions (magnetic poles) 3d and 4d, but the effective value ge of the gap length is large and the number of turns N is also large.
  • Samples D, E, and F are outside the particularly preferred range ⁇ / ⁇ ⁇ 0.8 or ⁇ ⁇ ⁇ > 1.25, but this is a small power application, in addition to electrical properties, size and weight. This is because it is necessary to satisfy the required specifications, and the magnetic flux density Bc cannot be lowered.
  • FIG. 8 is a perspective view showing the core structure of another first aspect of the reactor shown in FIG.
  • FIG. 9 is a perspective view showing a core structure of another second aspect of the reactor shown in FIG.
  • the core 2 has a yoke portion, that is, the core members 3 and 4 and the portions of the outer peripheral portions 3a and 4a and the end plates 3b and 4b excluding the protruding portions 3d and 4d that become magnetic poles. Need not cover the entire outer peripheral portion of the air-core coil 1 as long as the magnetic flux density By of the yoke can be maintained higher than the magnetic flux density Bg of the gap portion as described above.
  • the reactor D1 has a cage shape in which a part of the reactor D1 is opened to the outside for ventilation, or a core 2 'is formed into a U-shaped core member 3', 4 'as shown by a reactor D1' in FIG. May be configured in combination. For example, although depending on the magnetic material, it is sufficient that the yoke covers a half or more of the outer peripheral portion of the air-core coil 1 in total.
  • the pair of core members 3 and 4 may be combined at any position as long as they are formed to be equal to each other. In that case, in the axial direction, end faces of the outer peripheral portions 3a and 4a However, it is easy to cause deviation in the radial direction. Therefore, as shown by the core member 3 ′′ (4 ′′) in FIG. 9, the protrusion 3b1 (4b1) corresponds to one end surface of the outer peripheral portions 3a and 4a of the pair of core members 3 and 4, and the other end surface corresponds to the other end surface. By providing the recess 4b2 (3b2), the radial shift in the pair of core members 3 and 4 can be eliminated. Further, like the core member 3 ′′ (4 ′′) in FIG.
  • both core members 3 ′′ and 4 ′′ can be shared and formed with the same mold by forming them alternately (90 ° in FIG. 9).
  • the core members 3 and 4 are preferably made of the same material in order to reduce the cost.
  • desired magnetic characteristics relatively high magnetic permeability
  • the core members 3 and 4 are preferably formed by molding soft magnetic powder from the viewpoint of ease of molding.
  • the soft magnetic powder is a ferromagnetic metal powder, and more specifically, pure iron powder, iron-based alloy powder (Fe—Al alloy, Fe—Si alloy, Sendust, Permalloy, etc.) and amorphous powder, And iron powder having an electrical insulating film such as a phosphoric acid-based chemical film formed on the surface.
  • These soft magnetic powders can be manufactured by an atomizing method or the like. In general, since the saturation magnetic flux density is large even with the same magnetic permeability, it is preferable to use a metal material such as the pure iron powder, iron-based alloy powder, and amorphous powder for the soft magnetic powder.
  • the core members 3 and 4 are obtained by compacting such a soft magnetic powder to a predetermined density by using, for example, a known conventional means.
  • This powder (iron powder) core has, for example, the magnetic flux density-relative permeability characteristic shown in FIG.
  • FIG. 10 is a diagram showing the magnetic flux density-relative permeability characteristics for each density in the dust (iron powder) core.
  • the horizontal axis in FIG. 10 is the magnetic flux density [T], and the vertical axis is the relative permeability [H / m].
  • a member having a density of 6.00 [g / cc] or more in this example, a density of 5.99 [g / cc]; ( ⁇ ), a density of 6.50 [g / cc]; ), Density 7.00 [g / cc]; ( ⁇ ), density 7.50 [g / cc]; ( ⁇ )), the magnetic flux density-relative permeability characteristic is It is a profile in which the relative permeability gradually increases and reaches a peak (maximum value) as the magnetic flux density increases, and then the relative permeability gradually decreases as the magnetic flux density increases.
  • the magnetic flux density-relative permeability characteristic shows that when the magnetic flux density is increased from the initial relative permeability of about 120 [H / m], the magnetic flux density becomes 0.00.
  • the relative permeability increases rapidly to about 200 [H / m], and then the relative permeability gradually decreases as the magnetic flux density increases.
  • the magnetic flux density at which the relative permeability becomes the initial relative permeability again as the magnetic flux density increases from the initial relative permeability is about 1T. .
  • the material having an initial magnetic permeability of about 50 to 250 [H / m] in this example, the material of about 70 to about 160 [H / m] has substantially the same magnetic flux density-relative magnetic permeability characteristics.
  • the material has a relatively high relative permeability.
  • FIG. 11 shows the relationship between the reactor configuration and the magnetic flux lines.
  • 11A shows the configuration of the reactor of Comparative Example 1
  • FIG. 11B shows the configuration of the reactor D1 in the present embodiment
  • FIG. 11C shows the configuration of the reactor of Comparative Example 2.
  • the reactor of this comparative example 1 is not provided with the core 2 and is only the air-core coil 1, and the reactor of the comparative example 2 has no gap, that is, the projections (magnetic poles) 3d and 4d are formed as cylinders 15 and end. It is the structure which connects between board 3b, 4b.
  • FIGS. 11A to 11C are axial sectional views corresponding to the radius.
  • FIG.11 (D) is a magnetic flux diagram of the reactor in the comparative example 1
  • FIG.11 (E) is a magnetic flux diagram of the reactor D1 in this embodiment
  • FIG.11 (F) is a comparative example.
  • 2 is a magnetic flux diagram of a reactor in FIG. In consideration of the visibility of the drawing, the description of the boundary line between adjacent windings is omitted in FIGS. 11D to 11F.
  • FIG. 12 is a diagram showing experimental results regarding changes in inductance when the current is changed in the range of 0 to 200 [A] in the reactors of this embodiment and Comparative Examples 1 and 2.
  • a graph A is a graph showing a change in inductance in the reactor of the comparative example 1
  • a graph B is a graph showing a change in inductance in the reactor D1 of the present embodiment
  • a graph C is a graph of the comparative example 2. It is a graph which shows the change of the inductance in a reactor.
  • the presence of the core portion 2 prevents or suppresses the leakage of magnetic flux lines from the reactor D1 to the same extent as the reactor of the comparative example 2. can do. Further, as shown in the graph B of FIG. 12, there is an advantage that stable inductance characteristics are obtained in the entire range of the current, and the inductance is larger than that of the reactor of the comparative example 1.
  • FIG. 13 is a cross-sectional view of a reactor having an air-core coil 1x having an edgewise winding structure.
  • FIG. 14 is a graph showing the relationship between frequency and loss in a reactor having a flatwise winding structure and an edgewise winding structure. The horizontal axis in FIG. 14 is the frequency f, and the vertical axis is the loss.
  • FIG. 15 is a diagram for explaining the aspect ratio of the conductor member constituting the air-core coil.
  • FIG. 15 shows an enlarged cross-sectional shape corresponding to the radius of the air-core coils 1 and 1y.
  • the air core coils 1 and 1x are formed from the conductor member 10, when the air core coils 1 and 1x are energized, an eddy current is generally generated on a plane (orthogonal plane) perpendicular to the magnetic field lines. A loss occurs.
  • the magnitude of the eddy current is proportional to the area intersecting the magnetic flux lines, that is, the area of a continuous surface perpendicular to the magnetic flux direction when the magnetic flux density is the same. Since the magnetic flux direction is along the axial direction in the air-core coils 1 and 1x, the eddy current is generated in the radial direction perpendicular to the axial direction in the strip-shaped conductor member 10 forming the air-core coils 1 and 1x. It is proportional to the area of the surface.
  • the conductor member 10 has a large area in the radial direction and easily generates eddy currents. Therefore, the loss caused by the eddy current rather than the loss caused by the electrical resistance. Is more dominant. Therefore, in the reactor of the edgewise winding structure, the loss depends on the frequency of the energization current, and as shown in FIG. 14, the loss increases with the increase of the frequency, and the initial loss is relatively small due to the relatively small electric resistance. Become.
  • the strip-shaped conductor member 10 has a small area in the radial direction and hardly generates eddy currents. Large area. Therefore, in the reactor D1 having the flatwise winding structure, almost no eddy current is generated, and as shown in FIG. 14, the loss is substantially constant regardless of the frequency of the energization current, and the initial loss is also caused by a relatively small electric resistance. Relatively small.
  • the reactor having the edgewise winding structure has a structure in which the conductor member 10 is overlapped in the axial direction.
  • the conductor member 10 has a width direction substantially coincident with the axial direction and is continuous. Therefore, the reactor D1 having the flatwise winding structure is more effective than the reactor having the edgewise winding structure. Can conduct heat. For this reason, the reactor D1 of the flatwise winding structure is superior to the reactor of the edgewise winding structure in terms of the loss and heat conduction.
  • the conductor member 10 constituting the air-core coil 1 has a width W that is a length in the radial direction. It is a strip-shaped conductor of t or more (hereinafter referred to as thickness).
  • the air-core coil 10 of the reactor D1 is configured by the conductor member 10 having a rectangular cross section in which the aspect ratio (t / W) of the thickness t to the width W is 1 or less.
  • the present embodiment is compared with a reactor including an air-core coil 1y composed of a conductor member 10y having a rectangular cross section in which the thickness t is longer than the width W.
  • the reactor D1 has a smaller area in the radial direction.
  • the eddy current loss can be reduced for the same reason as the reason why the reactor D1 of the flatwise winding structure is superior to the reactor of the edgewise winding structure in terms of the loss.
  • the aspect ratio (t / W) of the width W to the thickness t of the conductor member 10 is 1/10 or less, the occurrence of eddy current loss can be significantly reduced.
  • the thickness t of the strip-shaped conductor member 10 is set to be equal to or less than the skin thickness ⁇ with respect to the driving frequency of the reactor D1, eddy current loss is almost certainly eliminated.
  • the skin thickness ⁇ is expressed by the following equation (29).
  • ⁇ is the angular frequency
  • ⁇ is the magnetic permeability
  • ⁇ is the electrical conductivity
  • the inner wall surfaces of the end plates 3b and 4b of the core members 3 and 4 respectively facing the upper and lower end surfaces of the air-core coil 1 are parallel to each other at least in a region covering the coil ends. Is formed. Further, the inner wall surfaces of the end plates 3b and 4b and the width direction of the strip conductor 10 of the air-core coil 1 are arranged so as to be orthogonal to each other. When these conditions are not satisfied, the magnetic flux lines passing through the inside of the air-core coil 1 deviate from the state parallel to the axial direction even if the conditions concerning the cross-sectional shape of the strip conductor 10 are set. Therefore, in this embodiment, as described below, parallelism is defined on the inner wall surfaces of the end plates 3b and 4b so as to be regarded as parallel to each other.
  • FIG. 16 is an explanatory diagram of a method for calculating the parallelism of the core.
  • the interval at the innermost circumferential position (hereinafter referred to as the innermost circumferential position) is L1
  • the outermost position (hereinafter referred to as the outermost position).
  • the interval at the outer peripheral position) is L2.
  • an average value of the interval in the range from the innermost peripheral position to the outermost peripheral position is L3.
  • the average value L3 is an average value of intervals at a plurality of positions inscribed in the radial direction at a predetermined interval between the innermost circumferential position and the outermost circumferential position.
  • the difference (L1-L2) between the distance L1 between the inner wall surfaces of the end plates 3b, 4b at the innermost circumferential position of the air-core coil 1 and the distance L2 at the outermost circumferential position is divided by the average value L3.
  • the value ((L1-L2) / L3) obtained in this way is defined as the parallelism.
  • FIG. 17 to 19 are diagrams showing magnetic flux lines according to parallelism according to the simulation of the present inventors.
  • FIG. 17 shows the case where the parallelism is ⁇ 1/10
  • FIG. 18 shows the case where the parallelism is 1/10
  • FIG. 19 shows the parallelism is 1/100. Show the case.
  • the magnetic flux lines passing through the interior of the air-core coil 1 (the magnetic flux lines indicated by dotted lines) are parallel to the axial direction.
  • the parallelism is ⁇ 1/10 and +1/10
  • the magnetic flux lines passing through the interior of the air-core coil 1 are parallel to the axial direction. Don't be.
  • the magnetic flux lines passing through the inside of the air-core coil 1 are not parallel, as described above, the eddy current loss increases and the inductance becomes absolutely small.
  • the present inventors verified the distribution of magnetic flux lines while changing the parallelism in various ways. As a result, the present inventor needs to set the absolute value of the parallelism to 1/50 or less, preferably 1/100 or less in order to make the magnetic flux lines passing through the inside of the air-core coil 1 parallel. Obtained knowledge. Furthermore, the present inventor has found that the width direction of the strip-shaped conductor member 10 needs to be arranged so as to be orthogonal to the inner wall surfaces of the end plates 3b and 4b. With this configuration, the magnetic flux lines passing through the air-core coil 1 are parallel to the axial direction, eddy current loss in the strip-shaped conductor member 10 can be reduced, and the inductance L can be increased. it can. Therefore, the strip-shaped conductor member 10 can efficiently take the magnetic flux generated in the width direction into the core 2.
  • the inventor of the present invention has a ratio between a radius R (see FIG. 46) from the axis of the air-core coil 1 to the outer peripheral surface of the air-core coil 1 and a width W of the conductor member 10 forming the air-core coil 1.
  • R / W a simulation experiment was conducted on the mode of magnetic flux line distribution when the ratio R / W was changed.
  • 20 to 29 are diagrams showing magnetic flux lines according to the ratio R / W when the total volume of the reactor D1, the cross-sectional area of the rectangular cross section of the conductor member 10, and the number of turns of the air-core coil 1 are constant values, respectively. It is. 20 shows a case where the ratio R / W is 10, FIG.
  • FIG. 21 shows a case where the ratio R / W is 5, and FIG. 22 shows a case where the ratio R / W is 3.3.
  • FIG. 23 shows a case where the ratio R / W is 2.5
  • FIG. 24 shows a case where the ratio R / W is 2
  • FIG. 25 shows a case where the ratio R / W is 1.
  • 26 shows a case where the ratio R / W is 1.4
  • FIG. 27 shows a case where the ratio R / W is 1.3
  • FIG. 29 shows the case where the ratio R / W is 1. 20 to 29, the description of the boundary line between adjacent windings is omitted.
  • the following equation (30) is defined as an index representing the stability of the inductance L.
  • Lmin is an inductance (hereinafter referred to as a minimum inductance) in a minimum current in a current range (hereinafter referred to as a use range) that can be supplied to the inverter
  • Lmax is a maximum current in the current range
  • Lav is an average value of a plurality of inductances corresponding to a plurality of current values in the current range (hereinafter referred to as an average inductance). According to the above equation (30), the smaller the value of the stability I, the higher the inductance stability.
  • FIG. 30 is a graph K showing a change in inductance and its stability with respect to a change in the ratio.
  • the horizontal axis in FIG. 30 is the ratio R / W, and the vertical axis on the right side of the sheet is the stability I.
  • FIG. 30 also shows a graph representing changes in the maximum inductance Lmax, the minimum inductance Lmin, and the average inductance Lav with respect to the change in the ratio R / W, by representing the inductance of each reactor with the vertical axis on the left side of the drawing. ing.
  • the maximum inductance Lmax increases substantially in proportion to the ratio R / W
  • the minimum inductance Lmin has a peak waveform that is maximized when the ratio R / W is about 6.
  • the average inductance Lav changes so as to have a mountain-shaped waveform that becomes maximum when the ratio R / W is about 8.
  • the ratio R / W needs to be set to 4 or less (R / W ⁇ 4). Therefore, by selecting the ratio R / W from the range of 1.3 to 4, the reactor D1 can stabilize the inductance L while suppressing eddy current loss.
  • the raw material powder is put into a mold and molded by using a dust core obtained by compacting soft magnetic powder as the core members 3 and 4.
  • a desired shape can be created, the material cost is low, and a desired magnetic property (density) can be obtained relatively easily.
  • the raw material powder can be made into a mold and molded (fired) to be formed into a desired shape.
  • a powder core of iron-based soft magnetic powder is preferable to soft ferrite.
  • FIG. 31 is a cross-sectional view showing a plurality of modes when an insulating member is interposed between the core and the air-core coil.
  • FIG. 31 (A) shows the reactor D1a of the first mode including the insulating member IS1 (IS1-1, IS1-2), and
  • FIG. 31 (B) shows the insulating member IS2 (IS2-1, IS2-2).
  • the reactor D1b of the 2nd aspect provided is shown, and
  • FIG.31 (C) shows the reactor D1c of the 3rd aspect provided with insulation member IS3.
  • the insulating member IS IS1, IS2, IS3 is a resin sheet having heat resistance such as PEN (polyethylene naphthalate) or PPS (polyphenylene sulfide).
  • Insulating members IS1-1 and IS1-2 in reactor D1a shown in FIG. 31A are provided between the end of air-core coil 1 and the inner wall surfaces of end plates 3b and 4b of opposing core members 3 and 4. Be placed. Further, the insulating members IS2-1 and IS2-2 in the reactor D1b shown in FIG. 31 (B) are not only the portions facing the end plates 3b and 4b, but also the inner peripheral side and part of the outer peripheral side of the air-core coil 1. It has a cylindrical rising part that covers. In addition, the insulating member IS3 in the reactor D1c shown in FIG. 31C is obtained by extending the rising portions of the insulating members IS2-1 and IS2-2 and connecting them to each other.
  • the insulating member IS3 is formed like an annular tube, and the air-core coil 21 is accommodated therein.
  • the dielectric strength between the air-core coil 1 and the core 2 can be further improved.
  • Table 2 shows changes in dielectric strength voltage (2.0 kV) with respect to changes in the materials and thickness ( ⁇ m) of the insulating members IS1-1 and IS1-2 in the reactor D1a configured as shown in FIG.
  • the insulating members IS1-1 and IS1-2 are Kapton sheets (polyimide)
  • the thickness is changed to 25 ⁇ m, 50 ⁇ m and 100 ⁇ m, respectively, and a voltage of 2.0 kV is applied to the sheet in each case Then, the withstand voltage (whether or not the insulation is maintained) was tested.
  • the thickness was changed to 75 ⁇ m and 125 ⁇ m, respectively, and a voltage of 2.0 kV was applied to the sheet in each case, and the withstand voltage was tested.
  • the insulating members IS1-1 and IS1-2 were PPS and Nomex, the thicknesses thereof were both set to 100 ⁇ m, a voltage of 2.0 kV was applied to the sheet in each case, and the withstand voltage was tested.
  • the insulating members IS1-1 and IS1-2 are Kapton sheets (polyimide) having a thickness of 100 ⁇ m
  • the insulating members IS1-1 and IS1-2 are PEN sheets having a thickness of 125 ⁇ m.
  • the thickness of the insulating member IS is preferably 100 ⁇ m or more.
  • the insulating member IS is not limited to the above-described resin, and BN (boron nitride) ceramic or the like may be used.
  • the insulating member IS may be formed not only by the sheet body as described above but also by filling the compound. Filling can be realized by applying an appropriate amount of filler to the inner surfaces of the core members 3, 4, housing the air core coil 1, and joining the core members 3, 4. Note that the hardness of the filler depends on the application specifications, and depending on the application (hardness), a curing treatment with heat or a catalyst may be required. Thus, the dielectric strength between the air-core coil 1 and the core 2 can be further improved.
  • the low-permeability magnetic body may be filled as a filler.
  • FIG. 32 is a perspective view of the reactor according to the second embodiment with a part thereof cut away.
  • the reactor D2 in the second embodiment is similar to the reactor D1 shown in FIG.
  • the air-core coil 1 and the core 2 are basically formed in a cylindrical shape.
  • the present invention is not limited to this, and is not limited to this. It may be formed in a polygonal tube shape (a cross-sectional polygonal tube shape) such as a rectangular tube shape and an octagonal tube shape (a cross-sectional octagonal tube shape).
  • a combination in which one of the air-core coil 1 and the core 2 is cylindrical and the other is a polygonal cylinder is also possible.
  • the air-core coil 11 and the core 12 are both formed in a square cylinder shape. Therefore, the protrusions 13d and 14d of the core members 13 and 14 that form the core 12 of the reactor D2 are formed in a square frustum shape, and the air core portion S2 of the air core coil 11 has a square cylindrical space. .
  • the reactor D2 of this embodiment includes the air-core coil 11 having a flat-wise winding structure and the core 12 covering the air-core coil 11.
  • the pair of core members 13 and 14 constituting the core 12 is made of a magnetically isotropic material, and includes square cylindrical outer peripheral portions 13a and 14a and square plate-like end plates 13b and 14b. Composed.
  • the air-core coil 11 is accommodated in the rectangular tubular recesses 13c and 14c formed in this way.
  • projections 13d and 14d are formed at the center of the inner wall surface facing the air-core coil 12.
  • the radius R in the air-core coil 1 described above is read as the shortest distance from the center of the air-core coil 12 to the outer peripheral surface.
  • FIG. 33 is a diagram showing the magnetic flux density in the reactor shown in FIG. 32 as a vector, and is an axial sectional view of the core 12 divided into two.
  • FIG. 34 is a graph showing a comparison of the inductance characteristics of the reactor shown in FIG. 1 and the reactor shown in FIG.
  • the reactor D1 having the configuration shown in FIG. 1 is compared with the reactor D2 having the configuration shown in FIG. 32 under the condition that the inductance at 40A is substantially the same.
  • the horizontal axis in FIG. 34 is current [A], and the vertical axis is normalized inductance.
  • the quadrangular cylindrical reactor D2 also causes the magnetic flux lines in the air-core coil 11 to be substantially parallel to the axial direction, and has the same effect as the cylindrical reactor D1 shown in FIG. Moreover, when the maximum outer dimensions are the same, as can be seen from FIG. 34, the inductance of the rectangular cylindrical reactor D2 is larger than the inductance of the cylindrical reactor D1. Furthermore, the inductance characteristic of the rectangular cylindrical reactor D2 is the same profile as the inductance characteristic of the cylindrical reactor D1. These inductance characteristics are substantially constant in a range where the current value is relatively small (a range of about 80 A or less in FIG. 34), and when the range is exceeded, the inductance characteristic gradually decreases as the energization current increases.
  • FIG. 35 is a front view of the core member 23 in the reactor according to the third embodiment as viewed from the inside.
  • the core member 23 is similar to the core members 3 and 4 described above, and portions corresponding to the core member 3 are denoted by the same reference numerals, and the description thereof is omitted.
  • cooling grooves 23a and 23b are provided in the core member 23 of the present embodiment.
  • the concave groove 23b is formed in an annular shape surrounding the periphery of the protrusion 3d, and a plurality of the concave grooves 23a are provided at equal intervals in the circumferential direction, and extend radially from the concave groove 23b toward the outer peripheral side. It penetrates and opens to the outside.
  • cooling media such as air and cooling water
  • the cooling medium is supplied from a concave groove 23b provided in one area divided into two with a diameter line as a boundary, and is discharged from the concave groove 23b provided in the other area.
  • FIG. 36 to 38 are sectional views in the axial direction of the reactor of each aspect in the fourth embodiment.
  • FIG. 36 shows the reactor D4a of the first embodiment
  • FIG. 37 shows the reactor D4b of the second embodiment
  • FIG. 38 shows the reactor D4c of the third embodiment.
  • (A) of each of these figures shows the overall configuration
  • (B) of each figure is an enlarged sectional view showing the vicinity of the air-core coil 1 in FIGS. 36 (A) to 38 (A).
  • reactors D4a, D4b, and D4c are similar to reactor D1 shown in FIG. 1 and reactor D1c shown in FIG. 31 (C), and corresponding portions are denoted by the same reference numerals and description thereof is omitted. To do. These reactors D4a, D4b, and D4c further include a heat sink HS outside the core 2.
  • One of the core members 3 and 4 constituting the core 2 (the core member 4 in FIGS. 36 to 38) is fixed to the heat sink HS via the heat transfer member PG1.
  • a heat sink HS may be provided on both of the core members 3 and 4.
  • an insulating material used to insulate between the strip-shaped conductor members 10 constituting the air-core coil 1 is also provided on the end surface side, and the heat of the air-core coil 1 is transferred to the core. It is also used as a heat transfer member that conducts heat to members 3 and 4. More specifically, in the reactor D4a of the first mode shown in FIG. 36, the heat transfer member PG2 is provided on one end side (heat sink HS side) of the air-core coil 1, and in the reactor D4b of the second mode shown in FIG.
  • a heat transfer member PG3 is further provided on the other end side (the side opposite to the heat sink HS) of the air-core coil 1, and in the reactor D4c of the third mode shown in FIG. 38, the heat transfer member PG4 is entirely contained in the internal space. Filled.
  • the heat transfer member PG (PG1 to PG4) is a member for conducting heat of the air-core coil 1 to the core portions 3 and 4, and is preferably a material having a relatively high heat transfer coefficient, and It is preferable that the air-core coil 1 and the core portions 3 and 4 are in close contact with each other. Heat transfer grease or the like is used for the heat transfer members PG1 to PG4.
  • the heat generated in the air-core coil 1 can be more efficiently conducted to the heat sink HS via the core members 3 and 4.
  • the thermal conductivity of the heat transfer members PG1 to PG4 is preferably 0.2 [W / mK] or more, and more preferably 1.0 [W / mK] or more.
  • the example which applied the thermal radiation structure to the reactor D1 was demonstrated above, the case where it applies to the reactor D2 can also be demonstrated similarly.
  • FIGS. 39 (B) and 40 (B) are cross-sectional lines A1- in FIGS. 39 (A) and 40 (A), respectively. It is sectional drawing seen from A1 and A2-A2.
  • the reactor D5 is similar to the reactors D4a, D4b, and D4c shown in FIGS. 36 to 38 described above in that the heat sink HS is provided, but heat transfer members PG1 to PG4 may be further provided.
  • the heat sink HS is a base for mounting the core members 33 and 34. Used as a stand.
  • the bolt 35 and a nut 36 which are fastening members in a state where the air-core coil 1 is accommodated
  • the bolt 37 which is a fixing member is attached to the heat sink HS. Fixed.
  • the bolts 35, nuts 36, and bolts 37 are arranged at different positions.
  • a combination of a bolt 35 and a nut 36 is disposed at the center of the core members 33 and 34, and the bolt 35, the nut 36, and the bolt 37 are equally spaced in the circumferential direction (120 And the bolts 35, nuts 36, and bolts 37 are arranged alternately (every 60 °).
  • the bolt 35, the nut 36, and the bolt 37 are respectively arranged at the apexes of the equilateral triangle, and can be fastened stably.
  • the hole 39 of the bolt 35 is appropriately countersunk.
  • the core members 33 and 34 are not similar in shape to the air core coil 1 having the outer cylindrical shape, but are different from the air core coil 1 having the outer cylindrical shape.
  • Another hexagonal cylinder is formed with one end closed.
  • the hole 39 for combining the core members 33 and 34 and the hole 40 for fixing to the heat sink HS at different positions, it is possible to improve the productivity of assembly and attachment of the reactor D5. . More specifically, in the method in which the core member is temporarily fixed with a clamp or the like, when the reactor is fixed to the base after being temporarily fixed, the clamp needs to be removed and fixed, which lowers assembly productivity. Similarly, when temporarily fixing with bolts and nuts, the reactor must be fixed to the base after releasing the temporary fixing.
  • the core members 33 and 34 are fastened by the bolt 35 and the nut 36. Since it can be carried into a curing apparatus such as a heating furnace and is not integrated with the heat sink HS having a large area, it is easy to handle.
  • a base a housing or the like may be used instead of the heat sink HS.
  • FIG. 41 is a diagram for explaining a strip-shaped conductor member 10 ′ used in the reactor according to the sixth embodiment of the present invention.
  • 41A is a perspective view
  • FIG. 41B is a cross-sectional view taken along the section line BB in FIG. 41A
  • FIG. 41C is the above-described belt-like shape.
  • FIG. 41 (D) is a schematic diagram of strip
  • the above-described strip-shaped conductor member 10 is formed of a uniform solid conductor, whereas the strip-shaped conductor member 10 ′ of the sixth embodiment has the conductor layer 101 and the insulating layer 102 in the thickness direction.
  • a plurality of stacked layers are stacked (in the example shown in FIG. 41, three insulating layers 102 are sandwiched between four conductor layers 101), and each end 103 in the longitudinal direction is connected to the core 2
  • the adjacent conductor layers are short-circuited without interposing the insulating layer 102 therebetween.
  • the magnitude of the eddy current is a continuous surface perpendicular to the magnetic field lines (magnetic flux lines). Since it is proportional to the area of the (continuous surface), the above-described conductor member 10 wound as one conductor is perpendicular to the magnetic field lines (magnetic flux lines) like this conductor member 10 '. By dividing and forming into a plurality of layers, the magnitude of the eddy current can be reduced.
  • the conductor cross-sectional area that is, the amount of current that can be flowed is reduced, the eddy current loss can be further reduced, and the electric resistance of the air-core coil can be reduced even if the same magnetic flux is generated. it can.
  • or 44 is a figure for demonstrating the air-core coil of each aspect used for the reactor in 7th Embodiment. 42 shows the air core coil of the first embodiment, FIG. 43 shows the air core coil of the second embodiment, and FIG. 44 shows the air core coil of the third embodiment.
  • the strip-shaped conductor member 10 ′′ in the air-core coil 1 ′′ is similar to the aforementioned strip-shaped conductor member 10 ′. That is, this conductor member 10 ′′ is a laminate of a plurality of conductor layers 101 and insulating layers 102 laminated in the thickness direction (in the example shown in FIG. 42, one layer between two conductor layers 101). The insulating layer 102 is sandwiched between the two ends in the longitudinal direction and the end 103 on the outer peripheral side drawn out of the core 2 in a wound state is short-circuited.
  • each of the conductor layers 101 itself or lead wires 105 led out separately from each conductor layer 101 are in opposite phases to the inductor core 106 provided outside the core 2. After being routed, they are joined at the connection point 107.
  • the magnitude of the eddy current is the area of a continuous surface (continuous surface) perpendicular to the magnetic field lines (magnetic flux lines). Therefore, the above-mentioned strip-shaped conductor 10 wound as a single conductor is divided into a plurality of layers in a direction perpendicular to the magnetic field lines (magnetic flux lines) like the strip-shaped conductor 10 ′′. In the magnetic field, the eddy current flows in the opposite direction on the front and back of the wire, and gradually returns in the conductor as the magnetic field decreases.
  • the inductor core 106 functions as a large resistance only to the antiphase eddy current and suppresses the current, but does not affect the drive current flowing in the same phase. Therefore, the conductor layer 101 divided into a plurality of layers passes through the inductor core 106 so as to be in opposite phases and then joined at the connection point 107, so that the eddy current loss can be reduced more effectively. Can do.
  • FIG. 42 shows an example in which the conductor layer 101 has two layers. In the case of a multi-layer, there are a plurality of inductor cores 106 and connection points 107.
  • FIG. 43 shows an example in which the conductor layer 101 has three layers
  • FIG. 44 shows an example in which the conductor layer 101 has four layers.
  • two inductor cores 106 are provided, and one inductor core 106-1 causes the current flowing through the first conductor layer 101-1 and the current flowing through the second conductor layer 101-2 to have opposite phases to each other.
  • the conductor layer 101 has four layers, three inductor cores 106 are provided. Then, the first inductor core 106-1 causes the current flowing through the first conductor layer 101-1 and the current flowing through the second conductor layer 101-2 to have opposite phases to each other, and then at the connection point 107-1, Combine the current. Further, the second inductor core 106-2 causes the current flowing through the third conductor layer 101-3 and the current flowing through the fourth conductor layer 101-4 to have opposite phases, and then at the connection point 107-2 Combine the current. Then, the two currents that are joined together are reversed in phase by the third inductor core 106-3 and then joined at the connection point 107-3.
  • the eddy current loss of the reactor D1 having the structure shown in FIG. 1 in which the strip-shaped conductor member 10 is a single layer having a thickness of 0.6 mm and the number of turns of the air-core coil 1 is 32 turns was examined. Further, the eddy current loss of the first multilayer reactor having the structure in which the conductor layer 101 is two layers having a thickness of 0.3 mm and the ends of the conductor layers 101-1 and 101-2 are joined outside the core 2. was investigated. Also, although the conductor layer 101 is similarly two layers having a thickness of 0.3 mm, lead wires 105 respectively led out from the respective conductor layers 101-1 and 101-2 are provided outside the core 2.
  • the eddy current loss of the second multi-layer reactor having a structure in which the inductor core 106 is joined after being in opposite phases to each other was examined. More specifically, the eddy current loss is measured by a resistance value at 10 kHz using an LCR meter.
  • the eddy current loss is about 56% in the case of a single layer (basic), and in the second multilayer reactor, the eddy current loss is about 32% in the case of a single layer (basic). It was possible to reduce. Thus, by forming the strip-shaped conductor 10 in multiple layers and further using the inductor core 106, eddy current loss can be reduced.
  • FIG. 45 is a plan view schematically showing the reactor according to the eighth embodiment.
  • a reactor can be used as a transformer, for example, a three-phase transformer disclosed in Japanese Patent Laid-Open No. 2001-345224.
  • the three-phase transformer is a cable winding type.
  • a magnetic circuit is formed by providing iron core yokes on the upper and lower parts of three iron cores corresponding to the three phases of the U phase, the V phase, and the W phase.
  • Such an iron core is combined in the shape of a square numeral “8” to form a magnetic line.
  • the three-phase transformer (reactor) having such a configuration is arranged in the middle of the power transmission system, and helps to stabilize the voltage.
  • AC motors have been arranged in factories, automobiles, etc. in order to reduce the need for maintenance.
  • three three-phase AC power wires are wired from the inverter.
  • a three-phase transformer (reactor) is usually connected in series between them. Is done.
  • the mainstream of power sources such as hybrid vehicles in recent years is a synchronous AC motor with a built-in permanent magnet. From the viewpoint of improving riding comfort, this electric motor is required to have smooth rotation.
  • the permanent magnet type synchronous AC motor is basically a combination (4 to 6) in which the number of magnetic poles on the rotor side is 4, and the number of magnetic poles on the stator side is 6, for example.
  • a combination of 8 magnetic poles on the rotor side and 12 magnetic poles on the stator side (8 to 12), or 16 magnetic poles on the rotor side and 16 magnetic poles on the stator side. 24 combinations (16 to 24) are used. As the number of poles increases, torque fluctuation, so-called cogging torque, is alleviated, and the occurrence of vibration is suppressed, leading to improved riding comfort.
  • the excitation coil inductances of the U phase, the V phase, and the W phase change asymmetrically with the rotation of the rotor.
  • the three-phase AC voltage waveform applied from the inverter is distorted and does not become an ideal sine wave waveform, resulting in torque fluctuation. Therefore, by inserting a three-phase reactor between an in-vehicle inverter mounted on a hybrid vehicle or the like and an electric motor, an unnecessary voltage waveform caused by nonlinear inductance, that is, a harmonic voltage component is absorbed and relaxed. Measures are effective.
  • the above-described conventional three-phase transformer is inconvenient when mounted on an automobile having a relatively large physique and limited mounting space due to its shape characteristics. Therefore, in the reactor D8 of the present embodiment, as shown in FIG. 45, U, V, and W of a single-layer coil formed by winding a long conductor member that is insulated and coated with an insulating material as a basic unit.
  • a three-layer air-core coil 51 formed by laminating three single-layer coils 51u, 51v, 51w corresponding to each phase in the thickness direction is used.
  • the winding start ends of these three single-layer coils 51u, 51v, 51w are independent from each other as first terminals 51au, 51av, 51aw of current lines.
  • the winding end ends of the three single-layer coils 51u, 51v, 51w are also independent from each other as the second terminals 51bu, 51bv, 51bw of the current line.
  • the three single-layer coils 51u, 51v, 51w are laminated in the thickness direction while being electrically insulated by an electrical insulating film, and are firmly fixed in the core 2.
  • the cross section of the long strip-shaped conductor member 10 is preferably a rectangular shape so that it can be easily laminated.
  • These three stacked single-phase coils 51u, 51v, 51w are not electrically connected because they are electrically insulated, but are magnetically coupled to each other by the proximity effect of the stacked layers. Thus, a magnetic circuit is formed.
  • the reactor D8 By configuring the reactor D8 in this way, three-phase coils can be accommodated in one coil space, so that the physique can be made smaller than a conventional three-phase reactor having the same power capacity. it can.
  • the reactor D8 having such a configuration is particularly suitable when mounted on a moving body (vehicle) such as an electric vehicle, a hybrid vehicle, a train, and a bus with a limited mounting space. Further, the reactor D8 having such a configuration can absorb and smooth the harmonic distortion voltage (so-called ripple) from the inverter in the power line from the inverter to the AC motor. As a result, the reactor D8 has a sinusoidal waveform. A close waveform can be output to the motor.
  • a moving body such as an electric vehicle, a hybrid vehicle, a train, and a bus with a limited mounting space.
  • the reactor D8 having such a configuration can absorb and smooth the harmonic distortion voltage (so-called ripple) from the inverter in the power line from the inverter to the
  • the reactor D8 having such a configuration has high rigidity as a structure because the coils 51u, 51v, 51w for three phases are fixedly coupled together with the electric insulating film, and a magnetic force generated by application of an alternating current is provided. Force contraction vibration can also be suppressed.
  • a reactor according to one aspect is magnetically isotropic with an air-core coil formed by winding a strip-shaped conductor member so that the width direction of the conductor member is along the axial direction of the coil.
  • a core formed of a material and disposed outside the air-core coil, the core covering at least one part of the outer periphery of the air-core coil, and at least one of both ends of the air-core coil.
  • G is the gap length, which is the length of the gap between the protrusions
  • ⁇ 0 is the permeability of the gap
  • L is the target inductance of the reactor
  • N the number of turns of the strip-shaped conductor member in the air-core coil
  • N 0 ⁇ (L ⁇ g / ⁇ 0 / S)
  • ge ⁇ 0 ⁇ N ⁇ I / Bc
  • Se L ⁇ ge / ⁇ 0 / N 2
  • ⁇ N / N
  • the reactor according to another aspect is magnetically equivalent to an air-core coil formed by winding a strip-shaped conductor member so that the width direction of the conductor member is along the axial direction of the coil.
  • the cross-sectional area is S
  • the gap length which is the length of the gap between the protrusions, is g
  • the gap permeability is ⁇ 0
  • the reactor's target inductance is L
  • the strip-shaped conductor in the air-core coil The number of turns of the member is N .
  • the coil current is a Bc average of the magnetic flux density at the central point or the vicinity thereof of the gap in the case of I
  • the hysteresis loss increases in proportion to the magnetic flux density in the core material, and becomes maximum at the saturation magnetic flux density Bs. For this reason, when a desired target inductance L is determined for the reactor, the hysteresis loss can be reduced by reducing the magnetic flux density Bc in the core material within a range where it can be ensured.
  • a geometric shape that can reduce the hysteresis loss of the core and reduce the loss while ensuring the necessary inductance is determined according to the material of the core and the protruding portion.
  • This reactor can reduce the hysteresis loss of the core while ensuring the necessary inductance.
  • ⁇ / ⁇ ⁇ 0.8 or ⁇ ⁇ ⁇ > 1.25 and 1/2 ⁇ ⁇ 2, 1 ⁇ ⁇ 2, 1 ⁇ ⁇ . ⁇ 3 is satisfied.
  • the magnetic pole gap (gap length g) is made relatively wide, and the magnetic flux lines are leaked to the winding portion of the air-core coil, so that the effective cross-sectional area Se on the surface of the magnetic pole (projection) is increased.
  • the reactor having the above-described configuration can reduce the magnetic flux density Bc in the magnetic pole.
  • At least regions covering the ends of the air-core coils are formed in parallel to each other, and the strip-shaped conductor The width direction of is arranged so as to be orthogonal to the surface direction of the diameter portion.
  • the magnetic flux lines passing through the inside of the air-core coil are parallel to the axial direction by arranging the strip-shaped conductor member so that the width direction thereof is orthogonal to the surface direction of the diameter portion.
  • the reactor having the above configuration can reduce eddy current loss in the conductor member and increase the inductance L.
  • the magnetic flux generated in the width direction of the conductor member can be efficiently taken into the core.
  • the ratio R / W when the radius from the center to the outer periphery of the air-core coil is R and the width of the strip-shaped conductor member is W, the ratio R / W However, the conditions of 1.3 or more and 4 or less are satisfied.
  • the ratio R / W when the ratio R / W is set to be larger than 4, the magnetic flux leaks to the outside of the core, and when set to less than 1.3, the magnetic flux passes through the inside of the air-core coil.
  • the line is not parallel to the axial direction.
  • the ratio t / W of the thickness t to the width W of the strip-shaped conductor member preferably satisfies a condition of 1/10 or less.
  • the strip-shaped conductor member is a tape-shaped conductor having a large aspect ratio, the thickness t tends to be equal to or less than the skin thickness with respect to the driving frequency of the reactor, and eddy current loss can be reduced.
  • the thickness t of the strip-shaped conductor member satisfies the condition of the skin thickness ⁇ or less with respect to the driving frequency of the reactor.
  • the interval at the innermost peripheral position is L1
  • the interval at the outermost peripheral position is L2.
  • the value obtained by ((L1-L2) / L3) is defined as parallelism, and the absolute value of the parallelism Satisfies the condition of 1/50 or less, more preferably 1/100 or less.
  • the magnetic flux lines passing through the inside of the air-core coil are parallel to the axial direction, and the eddy current loss in the strip conductor can be reduced and the inductance can be increased. Therefore, the strip-shaped conductor member can efficiently take in the magnetic flux generated in the width direction thereof.
  • the band-shaped conductor member is formed by laminating a plurality of sets of conductor layers and insulating layers laminated in the thickness direction, and each end portion in the longitudinal direction.
  • the conductor layers adjacent to each other outside the core are short-circuited.
  • the reactor having the above-described configuration can further reduce the eddy current loss and reduce the electric resistance of the air-core coil even when the same magnetic flux is generated.
  • the band-shaped conductor member is formed by laminating a plurality of sets of conductor layers and insulating layers laminated in the thickness direction, and the length of each conductor layer. At each end in the direction, each conductor layer itself or a lead wire led out separately from each conductor layer is provided so that the inductor cores provided outside the core are in opposite phases to each other. Then connected.
  • both ends are individually drawn out and joined to an inductor core provided outside the core so as to be in opposite phases to each other.
  • the inductor core acts as a large resistance only to the eddy current in the opposite phase and suppresses the eddy current, but has no effect on the drive current flowing in the same phase. Therefore, the reactor having the above-described configuration can further reduce the eddy current loss and reduce the electric resistance of the air-core coil even when the same magnetic flux is generated.
  • the air-core coil is a single-layer coil formed by winding a long strip-shaped conductor member that is insulated with an insulating material.
  • the winding start ends of each single layer coil are independent from each other as the first terminal of the current line, and the winding end ends are independent from each other as the second terminal of the current line. is doing.
  • the three single-layer coils are magnetically coupled to each other due to the proximity effect due to the lamination.
  • the conventional three-phase reactor Such a magnetic circuit can be formed. Therefore, the reactor having the above-described configuration is not housed in a single core, but is housed in a single core, so that the size of the reactor is larger than that of a conventional three-phase reactor having the same power capacity. Can be small.
  • the reactor of the said structure is suitable especially when mounted in moving bodies (vehicles), such as an electric vehicle with a limited mounting space, a hybrid vehicle, a train, and a bus.
  • the reactor having the above configuration can absorb and smooth the harmonic distortion voltage (so-called ripple) from the inverter in the power line from the inverter to the motor. As a result, a waveform close to a sine wave waveform can be obtained. Can also be output.
  • an insulating member is preferably disposed between the air-core coil and at least the facing surface of the air-core coil in the diameter portion of the core.
  • the dielectric strength between the air-core coil and the core portion can be further improved.
  • the core includes a plurality of core members formed of the magnetically isotropic material, and a base on which the core members are attached.
  • a fastening member that fastens the plurality of core members to each other in a state in which the air-core coil is accommodated, and a fixing member that fixes the fastened core members to the base, wherein the fixing member The arrangement position of and the arrangement position of the fastening member are different from each other.
  • the core in order to accommodate the air-core coil in the core, the core is formed of a plurality of core members, and these core members are assembled together in a state where the air-core coil is accommodated.
  • a fastening member in order to perform the said assembly, a fastening member is needed, and on the other hand, in order to fix the assembled core member to a base, a fixing member is needed. Therefore, in the reactor having the above-described configuration, the fastening member and the fixing member are alternately arranged in the circumferential direction, for example, or are divided into a central portion and a peripheral portion. Therefore, the reactor of the said structure can improve the productivity of the assembly and attachment.
  • the core is formed of a dust core obtained by compacting a soft magnetic powder.
  • the raw material powder when realizing a magnetically isotropic core as described above, the raw material powder can be formed in a mold and formed into a desired shape.
  • the material cost is low, and desired magnetic properties (density) can be obtained relatively easily.
  • the core is formed of a ferrite core.
  • the raw material powder is put into a mold and molded (fired), so that it can be formed into a desired shape.
  • the reactor evaluation method includes an air-core coil formed by winding a strip-shaped conductor member so that the width direction of the conductor member is along the axial direction of the coil, and a magnetic In a method for evaluating a reactor, which is formed of a material having a specific isotropic property and includes a core disposed outside the air-core coil, the core has an outer periphery that covers at least a part of the outer periphery of the air-core coil.
  • the cross-sectional area at or near the tip of the protrusion is S
  • the gap length that is the length of the gap between the protrusions is g
  • the permeability of the gap is ⁇ 0
  • the target inductance of the reactor is L.
  • the permeability of the material of the core and the protrusion is N and the average magnetic flux density at or near the center point of the gap when the coil current is I is Bc
  • the permeability of the material of the core and the protrusion is In the step of setting the number of turns N, the tip cross-sectional area S of the protrusion, the height of the protrusion, and the skirt shape of the protrusion according to the magnetic permeability, the ideal number of turns N 0 , the effective gap length ge, and the effective (protrusion)
  • the number of turns N, the tip cross-sectional area S of the protrusion, the height of the protrusion, and the base shape of the protrusion are set according to the magnetic permeability of the material of the core and the protrusion.
  • increasing the parameter ⁇ indicates that the winding is wound extra, and corresponds to a case where the core material is poor.
  • the parameter ⁇ is to obtain the relationship of the magnetic flux density Bc allowable to the core, that is, the gap length ge suitable for the magnetic permeability ⁇ c.
  • Increasing ⁇ uses a material having a high magnetic permeability ⁇ c. .
  • the parameter ⁇ is 1, which means that the cross-sectional areas from the base end portion to the tip end portion of the protrusion are equal, and the larger the value is, the more the shape becomes trapezoidal in the axial cross section of the protrusion.
  • the space of the normalization parameters ⁇ , ⁇ , ⁇ is expressed in a phase diagram of a ternary alloy.
  • the results for changes in the parameters ⁇ , ⁇ , and ⁇ can be easily recognized.
  • the scale on all three sides becomes a logarithmic scale, which is enlarged according to the order, and is inverted to indicate the reciprocal, whereby evaluation for obtaining an optimal geometric shape can be easily performed.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Manufacturing & Machinery (AREA)
  • Coils Or Transformers For Communication (AREA)

Abstract

L'invention concerne une réactance qui comporte un noyau muni de parties en saillie qui font saillie dans la partie de noyau creuse d'une bobine à noyau d'air. Etant donné que S est l'aire de section transversale à ou à proximité de l'extrémité avant des parties en saillie, g est la longueur d'espace libre entre les saillies, μ0 est la perméabilité magnétique de l'espace libre, L est l'inductance cible, N est le nombre de spires et Bc est la densité de flux magnétique moyen à ou à proximité du centre de l'espace libre lorsque le courant de bobine est I, le nombre idéal de spires N0, la longueur d'espace libre effective ge et l'aire de section transversale (partie d'extrémité distale de la saillie) effective Se sont déterminés comme étant définis respectivement par N0=√(L∙g/μ0/S), ge=μ0∙N∙I/Bc, et Se=L∙ge/μ0/N2 ; en outre, des paramètres normalisés α, β, γ définis par α=N/N0, β=ge/g et γ=Se/S sont déterminés. Le nombre N de spires de la bobine à noyau d'air, l'aire de section transversale S de l'extrémité avant des parties en saillie, la hauteur des parties en saillie et la forme de la base des parties en saillie sont définis sur la base de la perméabilité magnétique de la matière du noyau et des parties en saillie de sorte que la relation α/β<1 ou, sous la condition que l'inductance cible L est constante, α∙γ>1, soit satisfaite.
PCT/JP2012/002340 2011-04-06 2012-04-04 Réactance et procédé d'évaluation de celle-ci WO2012137494A1 (fr)

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JP2014225516A (ja) * 2013-05-15 2014-12-04 Ｎｅｃトーキン株式会社 リアクトル
CN104425112A (zh) * 2013-09-04 2015-03-18 台达电子企业管理（上海）有限公司 变压器
WO2015098500A1 (fr) * 2013-12-26 2015-07-02 株式会社 豊田自動織機 Dispositif électronique
JP2016127109A (ja) * 2014-12-26 2016-07-11 ダイキン工業株式会社 リアクトルの冷却構造
CN108875287A (zh) * 2018-08-27 2018-11-23 云南电网有限责任公司电力科学研究院 一种电抗器结构复杂度的分析方法及系统
JP2019054158A (ja) * 2017-09-15 2019-04-04 ファナック株式会社 三相変圧器
JP2019179929A (ja) * 2019-06-21 2019-10-17 ファナック株式会社 三相変圧器
CN114496536A (zh) * 2021-10-19 2022-05-13 天津经纬正能电气设备有限公司 大型干式空心tcr电抗器漏磁引起周边附件发热的治理方法
JPWO2022130583A1 (fr) * 2020-12-17 2022-06-23
WO2022153744A1 (fr) * 2021-01-18 2022-07-21 株式会社村田製作所 Réacteur
CN116884739A (zh) * 2023-05-31 2023-10-13 江苏征日电力设备有限公司 一种新型三相磁控电抗器的对称结构铁芯柱

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CN108231391B (zh) * 2017-05-31 2019-12-10 上海申世电气有限公司 一种用于转子变频器的电抗器铁芯损耗设计方法
JP2020088116A (ja) * 2018-11-22 2020-06-04 トヨタ自動車株式会社 リアクトルユニット
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JP2014225516A (ja) * 2013-05-15 2014-12-04 Ｎｅｃトーキン株式会社 リアクトル
CN104425112A (zh) * 2013-09-04 2015-03-18 台达电子企业管理（上海）有限公司 变压器
WO2015098500A1 (fr) * 2013-12-26 2015-07-02 株式会社 豊田自動織機 Dispositif électronique
JP2016127109A (ja) * 2014-12-26 2016-07-11 ダイキン工業株式会社 リアクトルの冷却構造
US10692650B2 (en) 2017-09-15 2020-06-23 Fanuc Corporation Three-phase transformer
JP2019054158A (ja) * 2017-09-15 2019-04-04 ファナック株式会社 三相変圧器
CN108875287B (zh) * 2018-08-27 2022-09-27 云南电网有限责任公司电力科学研究院 一种电抗器结构复杂度的分析方法及系统
CN108875287A (zh) * 2018-08-27 2018-11-23 云南电网有限责任公司电力科学研究院 一种电抗器结构复杂度的分析方法及系统
JP2019179929A (ja) * 2019-06-21 2019-10-17 ファナック株式会社 三相変圧器
JPWO2022130583A1 (fr) * 2020-12-17 2022-06-23
WO2022130583A1 (fr) * 2020-12-17 2022-06-23 日新電機株式会社 Procédé d'essai d'augmentation de température pour réactances
JP7328601B2 (ja) 2020-12-17 2023-08-17 日新電機株式会社 リアクトルの温度上昇試験方法
WO2022153744A1 (fr) * 2021-01-18 2022-07-21 株式会社村田製作所 Réacteur
CN114496536A (zh) * 2021-10-19 2022-05-13 天津经纬正能电气设备有限公司 大型干式空心tcr电抗器漏磁引起周边附件发热的治理方法
CN114496536B (zh) * 2021-10-19 2024-02-06 天津经纬正能电气设备有限公司 大型干式空心tcr电抗器漏磁引起周边附件发热的治理方法
CN116884739A (zh) * 2023-05-31 2023-10-13 江苏征日电力设备有限公司 一种新型三相磁控电抗器的对称结构铁芯柱
CN116884739B (zh) * 2023-05-31 2024-04-26 河北邦能电气制造有限公司 一种三相磁控电抗器的对称结构铁芯柱

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