WO2012101905A1 - スイッチング電源装置 - Google Patents
スイッチング電源装置 Download PDFInfo
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- WO2012101905A1 WO2012101905A1 PCT/JP2011/078244 JP2011078244W WO2012101905A1 WO 2012101905 A1 WO2012101905 A1 WO 2012101905A1 JP 2011078244 W JP2011078244 W JP 2011078244W WO 2012101905 A1 WO2012101905 A1 WO 2012101905A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/338—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement
- H02M3/3381—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement using a single commutation path
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K3/00—Circuits for generating electric pulses; Monostable, bistable or multistable circuits
- H03K3/02—Generators characterised by the type of circuit or by the means used for producing pulses
- H03K3/26—Generators characterised by the type of circuit or by the means used for producing pulses by the use, as active elements, of bipolar transistors with internal or external positive feedback
- H03K3/30—Generators characterised by the type of circuit or by the means used for producing pulses by the use, as active elements, of bipolar transistors with internal or external positive feedback using a transformer for feedback, e.g. blocking oscillator
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Definitions
- the present invention relates to a switching power supply device that includes a switching element on the primary side and a rectifier circuit on the secondary side, and transmits power using an electromagnetic resonance phenomenon.
- a current resonance half bridge converter that operates by flowing a sinusoidal resonance current through a transformer using the LC resonance phenomenon is highly efficient in a market such as a flat-screen TV in which the characteristics of output current ripple are relatively relaxed. Utilizing the features, practical application is progressing.
- Patent Document 1 is disclosed as an LC series resonance type DC-DC converter.
- FIG. 1 is a basic circuit diagram of a switching power supply device disclosed in Patent Document 1.
- This switching power supply device is a current resonance type half-bridge DC / DC converter, and an LC resonance circuit composed of an inductor Lr and a capacitor Cr and two switching elements Q1 and Q2 are connected to a primary winding np of a transformer T. ing.
- a rectifying and smoothing circuit including diodes Ds1 and Ds2 and a capacitor Co is formed in the secondary windings ns1 and ns2 of the transformer T.
- the switching elements Q1 and Q2 are alternately turned on and off with a dead time therebetween, and the current waveform flowing through the transformer T becomes a sinusoidal resonance waveform.
- power is transmitted from the primary side to the secondary side in both the on-period / off-period of the two switching elements Q1, Q2.
- the transformer is used as an insulating transformer using electromagnetic induction, and is only used as a transformer using magnetic coupling.
- transformers that use electromagnetic induction it is important to efficiently convert from electricity to magnetism and electricity by linking the magnetic flux generated by the current flowing in the primary winding with the secondary winding to flow the current. ing.
- the ratio of the magnetic flux interlinked with the secondary winding out of the magnetic flux generated by the current flowing through the primary winding is called (magnetic) coupling degree.
- the power conversion efficiency is increased.
- the switching power supply device of the present invention is configured as follows. (1) an electromagnetic field coupling circuit including a primary winding and a secondary winding; A primary side AC voltage that includes a switching circuit connected to the primary winding and that is configured by a parallel connection circuit of a switching element, a diode, and a capacitor, and generates an AC voltage from an input DC voltage Generating circuit; A secondary side rectifier circuit for rectifying the AC voltage into a DC voltage; A first resonant circuit configured on the primary side and including a first series resonant inductor and a first series resonant capacitor; A second resonant circuit configured on the secondary side and including a second series resonant inductor and a second series resonant capacitor; A switching control circuit for generating a substantially square wave or trapezoidal AC voltage by alternately turning on / off switching elements of the primary side AC voltage generation circuit with a dead time therebetween; In a switching power supply device comprising: In the switching control circuit, a current flowing into a multi-re
- the switching operation of the switching element of the primary side AC voltage generating circuit is performed at a switching frequency higher than a specific resonance frequency at which the impedance is smallest with respect to the double resonance circuit
- the electromagnetic field coupling circuit constitutes an electromagnetic field resonance circuit in which a magnetic field coupling via a mutual inductance and an electric field coupling via a mutual capacitance are mixed between the primary winding and the secondary winding,
- the first resonance circuit and the second resonance circuit resonate to transmit power from the primary side to the secondary side of the electromagnetic field coupling circuit.
- the switching control circuit has a switching frequency of the primary side AC voltage generating circuit constant, and a plurality of switching operations with a period in which current is conducted to the switching circuit being an on period and another period being an off period.
- the output power obtained from the secondary side rectifier circuit is adjusted by controlling the on-period ratio of the circuit.
- the switching control circuit makes the switching frequency of the primary side AC voltage generation circuit constant, and controls the on-period ratio of the switching element, whereby the output power obtained from the secondary side rectifier circuit Adjust.
- the secondary side rectifier circuit stores the voltage generated in the secondary winding as electrostatic energy in the second resonant capacitor in either the on period or the off period, or both periods, It is preferable to add the voltage generated in the secondary winding during each of the on period and the off period and output the result as a DC voltage.
- a parallel resonant capacitor is provided in parallel with the primary winding or the secondary winding.
- the parallel resonant capacitor is composed of a stray capacitance of the primary winding or the secondary winding.
- the mutual capacitance is composed of a stray capacitance formed between the primary winding and the secondary winding.
- the first series resonant inductor or the second series resonant inductor is configured by a leakage inductance of the electromagnetic field coupling circuit.
- the mutual inductance is constituted by an exciting inductance formed equivalently between the primary winding and the secondary winding.
- the switching circuit is preferably a MOSFET.
- the rectifying element that rectifies the AC voltage provided in the secondary side rectifier circuit into a DC voltage is a MOSFET.
- the secondary rectifier circuit acts as the primary AC voltage generator, and the primary AC voltage generator is It is preferable that it acts as a secondary side rectifier circuit and can transmit power in both directions.
- the primary winding is a winding provided on the primary side of a transformer having a magnetic core such as ferrite
- the secondary winding is a winding provided on the secondary side of the transformer.
- the primary winding is a power transmission coil provided in a power transmission device
- the secondary winding is a power reception coil provided in a power reception device arranged close to the power transmission device.
- the LC resonance circuit is provided on both the primary side and the secondary side, and the two LC resonance circuits are resonated to couple the magnetic field and the electric field between the primary winding and the secondary winding. Can be used to transmit power.
- the resonance phenomenon only active power is transmitted from the primary side to the secondary side, and reactive power is circulated in both the primary and secondary LC resonance circuits, so power loss is extremely high. Small.
- switching frequency switching is performed at a frequency higher than the natural resonance frequency at which the input impedance becomes the smallest in the entire double resonance circuit including the primary side resonance circuit including the electromagnetic field coupling circuit and the secondary side resonance circuit.
- a zero voltage switching (ZVS) operation in the switching element can be performed by turning on and off the element.
- FIG. 1 is a basic circuit diagram of a switching power supply device disclosed in Patent Document 1.
- FIG. 2 is a circuit diagram of the switching power supply apparatus 101 according to the first embodiment.
- FIG. 3 is a voltage-current waveform diagram of each part of the switching power supply apparatus 101 shown in FIG.
- FIG. 4 is a circuit diagram of the switching power supply apparatus 102 according to the second embodiment.
- FIG. 5A is a waveform diagram of voltage / current of each part of the switching power supply apparatus 102.
- FIG. 5B is a waveform diagram of voltage and current in each part of the switching power supply device shown in FIG.
- FIG. 6 is a circuit diagram of the switching power supply apparatus 103 according to the third embodiment.
- FIG. 7 is a circuit diagram of the switching power supply device 104 of the fourth embodiment.
- FIG. 8 is a circuit diagram of the switching power supply device 105 of the fifth embodiment.
- FIG. 9 shows the waveform of the voltage input to the series resonant capacitor Cr shown in FIG.
- FIG. 10 shows the output voltage Vo with respect to the on-time ratio D, which is the ratio of the conduction period of the switching circuit S1 to the switching cycle, and the on-period ratio Da, which is the ratio of the conduction period of the switching circuit S2 to the conduction period of the switching circuit S1.
- D the on-time ratio
- Da the on-period ratio
- FIG. 11 is a circuit diagram of the switching power supply device 106 of the sixth embodiment.
- FIG. 11 is a circuit diagram of the switching power supply device 106 of the sixth embodiment.
- FIG. 12 is a circuit diagram of the switching power supply device 107 of the seventh embodiment.
- FIG. 13 is a circuit diagram of the switching power supply device 108 of the eighth embodiment.
- FIG. 14 is a circuit diagram of the switching power supply device 109 of the ninth embodiment.
- FIG. 15 is a circuit diagram of the switching power supply device 110 of the tenth embodiment.
- FIG. 16 is a circuit diagram of a switching power supply device 111 used as the power transmission system of the eleventh embodiment.
- FIG. 17 is a circuit diagram of the switching power supply device 112 used as the power transmission system of the twelfth embodiment.
- FIG. 18 is a circuit diagram of the switching power supply device 113 used as the power transmission system of the thirteenth embodiment.
- FIG. 19 is a circuit diagram of the switching power supply device 114 used as the power transmission system of the fourteenth embodiment.
- FIG. 20 is a circuit diagram of the switching power supply device 115 used as the power transmission system of the fifteenth embodiment.
- FIG. 21 is a circuit diagram of the switching power supply 116 used as the power transmission system of the sixteenth embodiment.
- FIG. 22 is a circuit diagram of a switching power supply device 117 used as the power transmission system of the seventeenth embodiment.
- FIG. 23 is a circuit diagram of a switching power supply device 118 used as the power transmission system of the eighteenth embodiment.
- FIG. 2 is a circuit diagram of the switching power supply apparatus 101 according to the first embodiment.
- the switching power supply device 101 is a circuit in which an input power supply Vi is input to an input unit and supplies stable DC power from an output unit to a load Ro.
- the switching power supply apparatus 101 includes the following units.
- An electromagnetic field coupling circuit 90 using a transformer having a primary winding np and a secondary winding ns A switching circuit S1 including a switching element Q1 and a switching circuit S2 including a switching element Q2 connected to the primary winding np -Rectifier diodes D3 and D4 connected to the secondary winding ns and the smoothing capacitor Co
- a double resonance circuit 40 including the electromagnetic coupling circuit 90 and including a first LC series resonance circuit and a second LC series resonance circuit.
- the electromagnetic field coupling circuit constitutes an electromagnetic field coupling circuit (electromagnetic resonance circuit) in which magnetic field coupling and electric field coupling are combined. Both the series resonant capacitors Cr and Crs also serve as capacitors for holding a DC voltage.
- the capacitor Cr On the primary side, the capacitor Cr is charged during the conduction period of the switching element Q1, and the capacitor Cr is discharged during the conduction period of the switching element Q2.
- the capacitor Crs On the other hand, on the secondary side, the capacitor Crs is discharged during the conduction period of the switching element Q1, and the capacitor Crs is charged using the voltage generated in the secondary winding ns during the conduction period of the switching element Q2 as electrostatic energy.
- Q2 add the voltages of the secondary windings ns generated during each conduction period and output the result.
- the circuit including the rectifier diodes D3 and D4 and the capacitor Crs constitutes an addition rectifier circuit 80 that performs charge / discharge and rectification.
- the primary-side inductor Lm may be an inductor as a component, or may represent the excitation inductance of the primary winding np of the transformer T.
- the primary-secondary capacitance Cm may be a capacitance as a component or may represent a mutual capacitance which is a stray capacitance of the transformer T.
- a portion surrounded by a thick broken line constitutes an electromagnetic field coupling circuit 90
- a portion surrounded by a thin broken line constitutes a multiple resonance circuit 40.
- the multi-resonance circuit 40 including the electromagnetic field coupling circuit 90 resonates with two LC resonance circuits on the primary side and the secondary side.
- the specific action is as follows.
- (1) The first resonance circuit made of Lr—Cr and the second resonance circuit made of Lrs—Crs resonate to resonate with each other, and between the primary winding np and the secondary winding ns.
- power transmission is performed using two couplings of a magnetic field due to mutual inductance and an electric field due to mutual capacitance.
- the exciting inductance of the transformer T is used as a mutual inductance (Lm), and illustration as a circuit element is omitted.
- the capacitors Cp and Cs promote power transmission through electromagnetic coupling. That is, the capacitors Cp and Cs and the mutual capacitance Cm constitute a power transmission circuit by ⁇ -type electric field coupling to transmit power. Incidentally, the mutual capacitance Cm constitutes a power transmission circuit by electric field coupling with the resonance capacitors Cr and Crs.
- the capacitors Cp and Cs are arranged such that, in the commutation period when the switching element is turned off, on the primary side, the resonance current ir flowing in the resonance capacitor Cr is parallel to the switching circuit parallel capacitor (switching elements Q1 and Q2).
- the current flows to the capacitor (connected capacitor) and the capacitor Cp.
- the larger the resonance current ir the larger the current flowing through the capacitor Cp.
- the current flowing through the parallel capacitance of the switching circuit during the commutation period is substantially constant.
- the dead time period can be reduced with respect to fluctuations in output power.
- the difference between the period when the current path is switched between the diode D3 and the diode D4 can be corrected.
- the switching elements Q1 and Q2 are alternately turned on and off with a dead time therebetween, thereby shaping the DC voltage Vi into a square wave or trapezoidal voltage waveform.
- the rectifier diodes D3 and D4 are alternately turned on to shape a square wave or trapezoidal voltage waveform into a DC voltage.
- the double resonance circuit 40 includes two resonance circuits including a primary side and a secondary side including the electromagnetic field coupling circuit 90.
- the double resonance circuit 40 has a specific resonance frequency fr that minimizes the combined impedance of the double resonance circuit 40, and the switching frequency fs and the resonance frequency fr approach each other to resonate.
- the flowing current increases and the output power increases. That is, the switching element is turned on / off at a switching frequency fs higher than the inherent resonance frequency fr of the entire multiple resonance circuit 90 that is a combination of the primary side resonance circuit including the electromagnetic field coupling circuit and the secondary side resonance circuit. As the switching frequency fs approaches the inherent resonance frequency fr and resonates, the current flowing into the multiple resonance circuit increases and the output power increases.
- the primary-side and secondary-side capacitors Cr and Crs perform two actions, that is, an operation for holding a DC voltage and a resonance operation.
- the transformer 2 includes a parasitic inductance of the transformer T such as the exciting inductance Lm of the primary winding np of the transformer T, the exciting inductance Lms of the secondary winding ns, the series resonant inductors Lr and Lrs, and the capacitors Cp and Cs. You may be comprised with the component.
- the transformer can be referred to as a resonant composite transformer that integrates a function as a transformer that enables electrical insulation and electrical parameters such as a resonant inductor and a resonant capacitor, and is used as an electromagnetic coupling device. be able to.
- FIG. 3 is a voltage-current waveform diagram of each part of the switching power supply apparatus 101 shown in FIG. The operation of the switching power supply apparatus 101 at each timing is as follows.
- the exciting inductance of the primary winding np of the transformer T is represented by Lm, and the exciting current is represented by im.
- the gate-source voltages of the switching elements Q1, Q2, Q3, and Q4 are represented by vgs1 and vgs2, the drain-source voltages are represented by vds1 and vds2, respectively, and the drain current of Q1 is represented by id1.
- Q1 and Q2 are alternately turned on and off with a short dead time when both switching elements are turned off, and the current flowing in Q1 and Q2 is commutated in the dead time period, respectively, so that zero voltage switching (ZVS) operation is performed. I do.
- ZVS zero voltage switching
- the switching control circuit 10 performs the following control.
- the switching frequency is set higher than the natural resonance frequency fr at which the input impedance is minimized for the entire multiple resonance circuit including the primary side resonance circuit including the electromagnetic field coupling circuit and the secondary side resonance circuit. .
- ZVS zero voltage switching
- the on-period ratio of the switching elements Q1 and Q2 is set to 1, and the switching elements Q1 and Q2 are controlled so as to change the switching frequency of the primary side AC voltage generation circuit, thereby secondary side rectification. Adjust the output power available from the circuit.
- the output obtained from the secondary side rectifier circuit is controlled by combining the on period ratio control of (2) and the switching frequency control of (3) so as to obtain an optimum control characteristic. Adjust the power.
- an electromagnetic field coupling circuit (electromagnetic resonance circuit) that combines magnetic field coupling and electric field coupling using resonance on the primary side and the secondary side, power transmission is performed only by magnetic field coupling.
- the power transmission efficiency becomes high and high-efficiency operation becomes possible.
- the switching frequency is set to the natural resonance frequency fr where the input impedance is minimized.
- a converter By configuring an electromagnetic field coupling circuit using leakage inductance, excitation inductance, stray capacitance, mutual capacitance, etc. of the transformer, a converter can be configured with a small number of parts, and a reduction in size and weight can be achieved. .
- the primary-side and secondary-side capacitors Cr and Crs perform the two roles of holding the DC voltage and the resonance operation, thereby converting the DC voltage into the AC voltage, while the double resonance circuit is Since the resonance operation is performed as the resonance capacitance to be configured, the number of components can be reduced. Further, ON period ratio control (PWM control) at a constant switching frequency is possible.
- FIG. 4 is a circuit diagram of the switching power supply apparatus 102 according to the second embodiment.
- switching elements Q3 and Q4 using FETs are provided instead of the rectifier diodes D3 and D4 on the secondary side. That is, the secondary side rectifier circuit is constituted by the switching elements Q3 and Q4.
- the switching elements Q3 and Q4 each include a diode (parasitic diode) and a capacitor (parasitic capacitance) in parallel, and constitute switching circuits S3 and S4.
- a capacitor Ci is provided in the power input section.
- the switching control circuit 20 controls the secondary side switching elements Q3 and Q4.
- the excitation inductances of the primary winding np and the secondary winding ns of the transformer T are Lm and Lms, the parasitic capacitances of the switching elements Q1, Q2, Q3, and Q4 and the parasitic diode are not shown.
- the secondary side switching control circuit 20 turns on / off the switching element Q3 in synchronization with the primary side switching element Q1, and turns on / off the switching element Q4 in synchronization with the primary side switching element Q2. That is, synchronous rectification is performed.
- the overall operation of the switching power supply 102 is the same as that of the switching power supply 101 shown in the first embodiment.
- FIG. 5A is a waveform diagram of voltage and current of each part of the switching power supply device 102.
- FIG. FIG. 5B is a waveform diagram of voltage and current in each part of the switching power supply device shown in FIG.
- vds1 is the drain-source voltage of the switching element Q1
- ir is the current flowing through the capacitor Cr
- Vds3 is the drain-source voltage of the switching element Q3
- id3 is the current flowing through the switching element Q3
- id4 is flowing through the switching element Q4. Current.
- a diode element having a low withstand voltage has a small forward voltage drop and a FET having a low withstand voltage. Since the on-resistance is small, the conduction loss due to the flowing current can be reduced, and high-efficiency operation is possible.
- the switching power supply 102 of the second embodiment has a symmetrical topology between input and output. Therefore, when power is transmitted from the output part of the secondary side rectifier circuit, the secondary side rectifier circuit acts as a primary side AC voltage generation circuit, and the primary side AC voltage generation circuit by the switching elements Q1 and Q2 is 2 Acts as a secondary rectifier circuit. Therefore, power transmission is possible in both directions from the primary side to the secondary side of the transformer T or from the secondary side to the primary side.
- the load Ro is a rechargeable battery, a storage capacitance, or a circuit including its charge / discharge control circuit
- power is transmitted from the primary side to the secondary side of the transformer T, whereby the rechargeable battery Is charged.
- a load circuit is connected to the portion to which the input power source Vi is connected in FIG. 4, the primary side from the secondary side of the transformer T with the rechargeable battery or the storage capacitance as the input power source and the direction of power transmission reversed. Power transmission to the side becomes possible.
- FIG. 6 is a circuit diagram of the switching power supply apparatus 103 according to the third embodiment.
- capacitors Ci1 and Ci2 that divide the voltage of the input power source Vi and capacitors Cis1 and Cis2 that divide the output voltage Vo are provided.
- the primary winding np of the transformer T the exciting inductance of the secondary winding ns, or inductors Lm and Lms which are external inductances are illustrated. Others are the same as those of the second embodiment shown in FIG.
- the input voltage Vi is divided by the capacitors Ci1 and Ci2, and the output voltage Vo is divided by the capacitors Cis1 and Cis2. Since the capacitors Ci1 and Cis1 divide the DC input voltage and perform the function of holding the DC voltage, the series resonance capacitors Cr and Crs act as resonance capacitors and hold the DC voltage, that is, DC voltage components. It does not function as a function of resonance operation by biasing.
- the overall converter operation is as shown in the first embodiment.
- the input power source Vi is divided as the respective voltages of the capacitors Ci1 and Ci2, and current flows from the input power source Vi to the capacitors Ci1 and Ci2 in both ON / OFF cycles of the switching elements Q1 and Q2, and the input power source Vi The effective value of the input current flowing out of the current becomes small, and the conduction loss in the current path is reduced.
- the output voltage Vo is divided as the respective voltages of the capacitors Cis1 and Cis2, and the output voltage from the capacitors Cis1 and Cis2 in both the on / off cycles of the switching elements Q1 and Q2.
- the effective value of the current flowing to Vo becomes small, and the conduction loss is reduced.
- FIG. 7 is a circuit diagram of the switching power supply device 104 of the fourth embodiment.
- capacitors Cr1 and Cr2 for dividing the voltage of the input power source Vi and capacitors Crs1 and Crs2 for dividing the output voltage Vo are provided. That is, the series resonance capacitor Cr in the switching power supply device shown in the second embodiment is divided into Cr1 and Cr2, and the series resonance capacitor Crs is divided into Crs1 and Crs2.
- an equivalent mutual inductance Lm formed between the primary winding np and the secondary winding ns of the transformer T is illustrated, and the transformer T composed of the primary winding np and the secondary winding ns is , Illustrated as an ideal transformer.
- the inductor Lr, the inductor Lrs, and the capacitors Cp and Cs can be configured by a single circuit element. It is also possible to configure the electromagnetic coupling circuit 90 itself by a single resonance composite transformer using parasitic elements of the transformer T. Others are the same as those of the second embodiment shown in FIG.
- the loss due to the capacitor is dispersed, the overall loss is reduced, and the heat generation is dispersed.
- the capacitors Cr1 and Cr2 and the capacitors Crs1 and Crs2 play both roles of holding a DC voltage and acting as a series resonance capacitor.
- FIG. 8 is a circuit diagram of the switching power supply device 105 of the fifth embodiment.
- a capacitor Cc is provided on the primary side to constitute a voltage clamp circuit.
- Others are the same as those of the second embodiment shown in FIG.
- the switching power supply device shown in FIG. 8 After the switching element Q1 is turned off, the voltage of the primary winding np is charged to the capacitor Cc through the parasitic diode of the switching element Q2 in the direction shown in FIG. When Q2 is on, the voltage (+ Vc) charged in the capacitor Cc is applied to the multiple resonance circuit. That is, the input voltage Vi is converted into a square wave voltage, and the square wave voltage has voltage amplitudes of + Vi and ⁇ Vc.
- FIG. 9 is a waveform of a voltage applied to the multiple resonance circuit including the series resonance capacitor Cr, the electromagnetic field coupling circuit 90, and the series resonance capacitor Crs shown in FIG.
- the solid line is the waveform in the case of the fifth embodiment
- the broken line is the waveform in the case of the first to fourth embodiments.
- the input power supply voltage to the resonance circuit changes between + Vi and 0 V
- the voltage amplitude is Vi in the fifth embodiment, compared to + Vi.
- the voltage Vc across the capacitor Cc constituting the voltage clamp circuit changes according to the ON period ratio D which is the ratio of the conduction period of the switching element Q1 to the switching period, and the output voltage Vo can be controlled over a wide range.
- the present invention is excellent in application when the input power supply voltage varies over a wide range when the output voltage is constant.
- control characteristics with respect to fluctuations in the input voltage are improved. That is, the output voltage can be stabilized even if the input voltage varies greatly.
- FIG. 10 shows the output voltage Vo with respect to the on-time ratio D, which is the ratio of the conduction period of the switching circuit S1 to the switching cycle, and the on-period ratio Da, which is the ratio of the conduction period of the switching circuit S2 to the conduction period of the switching circuit S1.
- the solid line is the characteristic curve of the on-period ratio Da
- the broken line is the characteristic curve of the on-time ratio D.
- FIG. 11 is a circuit diagram of the switching power supply device 106 of the sixth embodiment.
- a capacitor Cc is provided on the primary side to constitute a voltage clamp circuit.
- capacitors Ci1 and Ci2 that divide the voltage of the input power source Vi and capacitors Cis1 and Cis2 that divide the output voltage Vo are provided.
- the exciting inductance of the primary winding np is shown as a circuit parameter.
- an equivalent mutual inductance Lm formed between the primary winding np and the secondary winding ns of the transformer T is illustrated, and the transformer T composed of the primary winding np and the secondary winding ns is: It is shown as an ideal transformer.
- the inductor Lr, the inductor Lrs, and the capacitors Cp and Cs can be configured by a single circuit element. It is also possible to configure the electromagnetic coupling circuit 90 itself by a single resonance composite transformer using parasitic elements of the transformer T. Others are the same as those of the second embodiment shown in FIG.
- the control characteristic with respect to the fluctuation of the input voltage is improved.
- the input power source Vi is divided by the capacitors Ci1 and Ci2
- FIG. 12 is a circuit diagram of the switching power supply device 107 of the seventh embodiment.
- a capacitor Cc is provided on the primary side to constitute a voltage clamp circuit on the primary side
- a capacitor Ccs is provided on the secondary side to constitute a voltage clamp circuit on the secondary side.
- Others are the same as those of the fifth embodiment shown in FIG.
- the input voltage Vi is converted into a square wave voltage, and the square wave voltage has voltage amplitudes of + Vi and ⁇ Vc. Further, since the secondary capacitor Ccs is charged with a negative voltage (Vcs), the AC square wave voltage applied to the synchronous rectifier circuit by the switching elements Q3 and Q4 has a voltage amplitude of + Vo and ⁇ Vcs. Since the voltage amplitude is thus increased, the control characteristics with respect to fluctuations in the output voltage are also improved. That is, the output voltage can be easily adjusted over a wide range.
- FIG. 13 is a circuit diagram of the switching power supply device 108 of the eighth embodiment.
- a primary AC voltage generating circuit having a full bridge circuit configuration by four switching elements Q1, Q2, Q5, and Q6 is provided.
- a secondary side rectifier circuit having a bridge rectification configuration by four switching elements Q3, Q4, Q7, and Q8 is provided.
- the primary side switching elements Q1, Q2, Q5, Q6 and the secondary side switching elements Q3, Q4, Q7, Q8 Since the voltage applied to each becomes half, the loss in the switching element can be reduced.
- FIG. 14 is a circuit diagram of the switching power supply device 109 of the ninth embodiment.
- the primary-side resonant capacitor is divided into two capacitors Cr1 and Cr2
- the secondary-side resonant capacitor is divided into two capacitors Crs1 and Crs2.
- a primary side AC voltage generating circuit having a full bridge circuit configuration by four switching elements Q1, Q2, Q5, and Q6 is provided.
- a secondary side rectifier circuit having a bridge rectification configuration by four switching elements Q3, Q4, Q7, and Q8 is provided.
- the voltage applied to each of the resonant capacitors Cr and Crs shown in the first to third embodiments and the like is divided and applied to two capacitors. Loss can be distributed. Further, since the voltages applied to the primary side switching elements Q1, Q2, Q5, and Q6 and the secondary side switching elements Q3, Q4, Q7, and Q8 are each halved, the loss in the switching elements can be reduced. .
- the capacitors Cr1 and Cr2 and the capacitors Crs1 and Crs2 play both roles of holding a DC voltage and acting as a series resonance capacitor.
- FIG. 15 is a circuit diagram of the switching power supply device 110 of the tenth embodiment.
- Lp is a power transmission coil on the power transmission device side
- Ls is a power reception coil on the power reception device side.
- the equivalent leakage inductor of the power transmission coil Lp is the inductor Lr shown in the first to ninth embodiments
- the parallel capacitor between the equivalent windings of the power transmission coil Lp is the first to ninth embodiments.
- the inductor Lrs shown in the first to ninth embodiments is an equivalent leakage inductor of the power receiving coil Ls
- the parallel capacitor between the equivalent windings of the power receiving coil Ls is shown in the first to ninth embodiments.
- the capacitor Cs is configured.
- an equivalent inductance involved in magnetic field coupling in the power transmission coil Lp is configured as a mutual inductance Lm
- an equivalent capacitance involved in electric field coupling between the power transmission coil Lp and the reception coil Ls is configured as a mutual capacitance Cm.
- the mutual coefficient M as the electromagnetic field coupling is configured by combining the magnetic field coupling by the mutual inductance (mutual coefficient Ml) and the electric field coupling by the mutual capacitance (mutual coefficient Mc).
- the switching power supply 110 used as the power transmission system has a symmetrical topology between input and output, as shown in FIG. Therefore, when power is transmitted from the output part of the secondary side rectifier circuit, the secondary side rectifier circuit acts as a primary side AC voltage generation circuit, and the primary side AC voltage generation circuit by the switching elements Q1 and Q2 is 2 Acts as a secondary rectifier circuit. Therefore, it is possible to transmit power by exchanging the relationship between power transmission and power reception.
- the load Ro is a rechargeable battery, a storage capacitance, or a circuit including its charge / discharge control circuit
- the rechargeable battery is charged by transmitting power from the power transmission coil Lp to the power reception coil Ls. .
- a load circuit is connected to a portion to which the input power source Vi is connected in FIG. 15, power is transmitted from the power receiving coil Ls to the power transmitting coil Lp using the rechargeable battery or the storage capacitance as an input power source.
- the tenth embodiment has the following effects.
- FIG. 16 is a circuit diagram of a switching power supply device 111 used as the power transmission system of the eleventh embodiment.
- a parallel capacitor Cp is provided on the power transmission device side, and a parallel capacitor Cs is provided on the power reception device side.
- FIG. 17 is a circuit diagram of the switching power supply device 112 used as the power transmission system of the twelfth embodiment.
- the resonance capacitors Cr and Crs are divided into resonance capacitors Cr1 and Cr2, Crs1 and Crs2, respectively.
- the current flowing through each of the capacitors Cr and Crs is divided into two capacitors, so that losses in the capacitors can be dispersed and heat generation is also dispersed.
- the capacitors Cr1 and Cr2 and the capacitors Crs1 and Crs2 play both roles of holding a DC voltage and acting as a series resonance capacitor.
- FIG. 18 is a circuit diagram of the switching power supply device 113 used as the power transmission system of the thirteenth embodiment.
- an AC voltage generation circuit on the power transmission device side is configured by a full bridge circuit including four switching elements Q1, Q2, Q5, and Q6.
- a side rectifier circuit on the power receiving device side is configured by a bridge rectifier circuit including four switching elements Q3, Q4, Q7, and Q8.
- the parameter M shown in FIG. 18 is shown as a mutual coefficient of electromagnetic field coupling by combining magnetic field coupling by mutual inductance and electric field coupling by mutual capacitance.
- the switching elements Q1, Q2, Q5, Q6 on the power transmission device side, and the switching elements Q3, Q4, Q7, Q8 on the power reception device side Since the voltage applied to each becomes half, the loss in the switching element can be reduced.
- FIG. 19 is a circuit diagram of the switching power supply device 114 used as the power transmission system of the fourteenth embodiment.
- a capacitor Cc is provided on the power transmission device side to constitute a voltage clamp circuit.
- Others are the same as those of the tenth embodiment shown in FIG.
- the fourteenth embodiment if the negative voltage charged to the capacitor Cc is ⁇ Vc, the square wave voltage generated on the power transmission device side has voltage amplitudes of + Vi and ⁇ Vc.
- the control characteristic with respect to the fluctuation of the is improved.
- FIG. 20 is a circuit diagram of the switching power supply device 115 used as the power transmission system of the fifteenth embodiment.
- a capacitor Ccs is provided on the power receiving device side, and a voltage clamp circuit is configured on the secondary side.
- Others are the same as those of the fourteenth embodiment shown in FIG.
- the input voltage Vi is converted into a square wave voltage on the power transmission device side, and the square wave voltage has voltage amplitudes of + Vi and ⁇ Vc.
- the negative voltage (Vcs) is charged in the capacitor Ccs on the power receiving device side
- the AC square wave voltage applied to the synchronous rectifier circuit by the switching elements Q3 and Q4 has voltage amplitudes of + Vo and ⁇ Vcs. Since the voltage amplitude is increased in this way, the control characteristics with respect to fluctuations in the output voltage are also improved. That is, the output voltage can be easily adjusted over a wide range.
- FIG. 21 is a circuit diagram of the switching power supply 116 used as the power transmission system of the sixteenth embodiment.
- the rectifier circuit on the power receiving device side is constituted by rectifier diodes D3 and D4. According to this configuration, the power receiving device can be used as a unidirectional power transmission system with a simple configuration.
- FIG. 22 is a circuit diagram of a switching power supply device 117 used as the power transmission system of the seventeenth embodiment.
- an AC voltage generation circuit on the power transmission device side is configured by a full bridge circuit including four switching elements Q1, Q2, Q5, and Q6.
- the rectifier circuit on the power receiving device side is constituted by a diode bridge formed by rectifier diodes D3, D4, D7, and D8.
- the seventeenth embodiment it can be used as a unidirectional power transmission system.
- the withstand voltage of the rectifier diode can be halved.
- FIG. 23 is a circuit diagram of a switching power supply device 118 used as the power transmission system of the eighteenth embodiment.
- Ml is the mutual inductance that is the magnetic field coupling between the inductors Lp and Ls of the coil
- Mc is the mutual capacitance that is the electric field coupling between the capacitors Cp and Cs
- Mcr is the mutual capacitance that is the electric field coupling between the capacitors Cr and Crs.
- the electromagnetic field coupling circuit 90 including the capacitors Cr and Crs is illustrated.
- an electromagnetic resonance circuit by appropriately setting the mutual inductance Ml, the mutual capacitance Mc, and the mutual capacitance Mcr, and perform high-efficiency power transmission by electromagnetic coupling. it can.
Abstract
Description
(1)1次巻線および2次巻線を備える電磁界結合回路と、
前記1次巻線に接続されたスイッチング回路を備え、該スイッチング回路をスイッチング素子、ダイオード、およびキャパシタの並列接続回路で構成して、入力される直流電圧から交流電圧を発生する1次側交流電圧発生回路と、
前記交流電圧を直流電圧に整流する2次側整流回路と、
1次側に構成され、第1の直列共振インダクタおよび第1の直列共振キャパシタを含む第1の共振回路と、
2次側に構成され、第2の直列共振インダクタおよび第2の直列共振キャパシタを含む第2の共振回路と、
前記1次側交流電圧発生回路のスイッチング素子をデッドタイムを挟んで交互にオン/オフすることによりほぼ方形波状または台形波状の交流電圧を発生させるスイッチング制御回路と、
を備えたスイッチング電源装置において、
前記スイッチング制御回路は、電磁界結合回路を含めた前記第1の共振回路と前記第2の共振回路とを合わせた全体となる複共振回路に流入する電流が、前記1次側交流電圧発生回路から発生する交流電圧よりも遅れる正弦波状の共振電流波形となって、前記スイッチング素子のオン期間およびオフ期間の両期間に前記電磁界結合回路を介して1次側から2次側へ電力が伝送されるように、前記複共振回路に対してインピーダンスが最も小さくなる固有の共振周波数よりも高いスイッチング周波数で前記1次側交流電圧発生回路のスイッチング素子をスイッチング動作し、
前記電磁界結合回路は、前記1次巻線と前記2次巻線との間で相互インダクタンスを介した磁界結合および相互キャパシタンスを介した電界結合とが混合した電磁界共鳴回路を構成し、
前記第1の共振回路と前記第2の共振回路とが共鳴して前記電磁界結合回路の1次側から2次側へ電力が伝送されることを特徴とする。
図2は第1の実施形態のスイッチング電源装置101の回路図である。
スイッチング電源装置101は、入力部に入力電源Viが入力され、出力部から負荷Roへ安定した直流電力を供給する回路である。スイッチング電源装置101は次の各部を備えている。
・1次巻線npおよび2次巻線nsを備えるトランスを用いた電磁界結合回路90
・1次巻線npに接続された、スイッチング素子Q1を含むスイッチング回路S1、スイッチング素子Q2を含むスイッチング回路S2
・2次巻線nsに接続された整流ダイオードD3,D4および平滑キャパシタCo
・1次巻線npに接続された直列共振インダクタLrおよび直列共振キャパシタCrによる第1のLC直列共振回路
・2次巻線nsに接続された直列共振インダクタLrsおよび直列共振キャパシタCrsによる第2のLC直列共振回路
・電磁界結合回路90を含めて、第1のLC直列共振回路と第2のLC直列共振回路により構成される複共振回路40
・スイッチング素子Q1,Q2に接続されたスイッチング制御回路10
・負荷Roへの出力電圧の検出信号をスイッチング制御回路10へフィードバックする絶縁回路30
・1次巻線npに対して並列に接続された並列共振キャパシタCp
・1次巻線nsに対して並列に接続された並列共振キャパシタCs
・1次巻線npと2次巻線nsとの間に接続された相互キャパシタンスCm
前記電磁界結合回路は磁界結合と電界結合を融合した電磁界結合回路(電磁界共鳴回路)を構成している。前記直列共振キャパシタCr,Crsは共に直流電圧を保持するためのキャパシタを兼ねている。
(1)Lr-Crからなる第1の共振回路と、Lrs-Crsからなる第2の共振回路とが共鳴することによりそれぞれが共振し、1次巻線npと2次巻線nsとの間で相互インダクタンスによる磁界と相互キャパシタンスによる電界の2つの結合を利用して電力伝送を行う。ただし、図2ではトランスTの励磁インダクタンスを相互インダクタンス(Lm)として利用し、回路素子としての図示を略している。
スイッチング素子Q1は導通しており、巻線npに電流が流れ、キャパシタCrは充電される。ダイオードD3は導通しており、巻線npに印加された電圧により、巻線nsに電圧が誘起され、巻線nsに誘起された電圧とキャパシタCrsの両端電圧が加算されて負荷に電圧が印加され、キャパシタCrsは放電して電流が供給される。スイッチング素子Q1がターンオフするとState2となる。
インダクタLrに流れていた電流irにより、スイッチング素子Q1の並列キャパシタ(寄生容量)は充電され、スイッチング素子Q2の並列キャパシタ(寄生容量)は放電される。電圧vds1が電圧Vi、電圧vds2が0VになるとState3となる。
スイッチング素子Q2の並列ダイオードは導通している。この期間においてスイッチング素子Q2をターンオンすることでZVS動作が行われる。ダイオードD3に流れる電流が0AになるとState4となる。
スイッチング素子Q2は導通しており、巻線npには電流が流れ、キャパシタCrは放電される。ダイオードD4は導通しており、巻線npに印加された電圧により、巻線nsに電圧が誘起され、キャパシタCrsは充電される。負荷にはキャパシタCoの電圧が印加されて電流が供給される。このようにしてインダクタLrに流れる電流irは正弦波状の共振電流波形となる。ダイオードD4に流れる電流が0になるとState5となる。
1次側ではトランスの励磁電流imが流れ、電流irと等しくなる。2次側では、負荷にはキャパシタCoの電圧が印加されて電流が供給される。Q2がターンオフするとState6となる。
インダクタLrに流れていた電流irにより、スイッチング素子Q1の並列キャパシタ(寄生容量)は放電され、スイッチング素子Q2の並列キャパシタ(寄生容量)は充電される。電圧vds1が電圧0V、電圧vds2がViになるとState1となる。
(1)電磁界結合回路を含めた1次側共振回路と2次側共振回路とを合わせた全体の複共振回路に対して、入力インピーダンスが最も小さくなる固有共振周波数frよりスイッチング周波数を高くする。このことにより、そのスイッチング周波数では複共振回路は誘導性となる。そのため、インダクタLrに流れる電流位相が、1次側交流電圧発生回路による方形波(台形波)状の交流電圧の電圧位相に対して遅れた状態にできるので、スイッチング素子Q1の電圧Vds1が0の状態でスイッチング素子Q1をターンオンできる。同様に、スイッチング素子Q2の電圧vds2が0の状態でスイッチング素子Q2をターンオンできる。すなわちZVS(ゼロ電圧スイッチング)動作を行うことになり、スイッチング損失を大幅に低減でき、高効率動作が可能となる。また、全負荷範囲において共振周波数frより高いスイッチング周波数にて動作をするため、全負荷範囲に亘ってゼロ電圧スイッチング(ZVS)動作が実現できる。
(a)1次側と2次側の共振を用いて磁界結合と電界結合を融合した電磁界結合回路(電磁界共鳴回路)を構成することにより、磁界結合だけで電力伝送を行う場合よりも電力伝送効率が高くなり、高効率動作が可能となる。
図4は第2の実施形態のスイッチング電源装置102の回路図である。この例では第1の実施形態のスイッチング電源装置101と異なり、2次側の整流ダイオードD3,D4に代えてFETによるスイッチング素子Q3,Q4を備えている。すなわちスイッチング素子Q3,Q4で2次側整流回路を構成している。スイッチング素子Q3,Q4は、それぞれ並列にダイオード(寄生ダイオード)、キャパシタ(寄生容量)を備えており、スイッチング回路S3、S4を構成している。また、電源入力部にキャパシタCiを設けている。スイッチング制御回路20は2次側のスイッチング素子Q3,Q4の制御を行う。
(a)FETによるスイッチング素子Q3,Q4で同期整流動作を行うことにより、順方向降下電圧が小さくなり、整流回路での導通損が低減できる。
図6は第3の実施形態のスイッチング電源装置103の回路図である。この例では入力電源Viの電圧を分圧するキャパシタCi1,Ci2、および出力電圧Voを分圧するキャパシタCis1,Cis2を備えている。ここでは、トランスTの1次巻線np、2次巻線nsの励磁インダクタンス、または外付けのインダクタンスであるインダクタLm、Lmsを図示している。その他は第2の実施形態で図4に示したものと同様である。
(a)入力電源ViがキャパシタCi1,Ci2のそれぞれの電圧として分圧され、スイッチング素子Q1,Q2のオン/オフの両サイクルで入力電源ViからキャパシタCi1,Ci2へと電流が流れ、入力電源Viから流出する入力電流の実効値が小さくなって、電流経路での導通損が低減される。
図7は第4の実施形態のスイッチング電源装置104の回路図である。この例では入力電源Viの電圧を分圧するキャパシタCr1,Cr2、および出力電圧Voを分圧するキャパシタCrs1,Crs2を備えている。すなわち、第2の実施形態で示したスイッチング電源装置における直列共振キャパシタCrをCr1,Cr2に分割し、直列共振キャパシタCrsをCrs1,Crs2に分割したものである。ここでは、トランスTの1次巻線npと2次巻線nsとの間に形成される等価的な相互インダクタンスLmを図示し、1次巻線npと2次巻線nsからなるトランスTは、理想トランスとして図示されている。トランスTを理想的なトランスにて構成する場合、インダクタLr、インダクタLrs、およびキャパシタCp、Csを単体の回路素子にて構成できる。また、トランスTの寄生要素を用いて電磁結合回路90そのものを単体の共振複合トランスにて構成することも可能である。その他は第2の実施形態で図4に示したものと同様である。
図8は第5の実施形態のスイッチング電源装置105の回路図である。この例では1次側にキャパシタCcを設けて電圧クランプ回路を構成している。その他は第2の実施形態で図4に示したものと同様である。
図11は第6の実施形態のスイッチング電源装置106の回路図である。この例では1次側にキャパシタCcを設けて電圧クランプ回路を構成している。また、入力電源Viの電圧を分圧するキャパシタCi1,Ci2、および出力電圧Voを分圧するキャパシタCis1,Cis2を備えている。また1次巻線npの励磁インダクタンスを回路パラメータとして表記している。ここでは、トランスTの1次巻線np、2次巻線nsの間に形成される等価的な相互インダクタンスLmを図示し、1次巻線npと2次巻線nsからなるトランスTは、理想トランスとして図示されている。トランスTを理想的なトランスにて構成する場合、インダクタLr、インダクタLrs、およびキャパシタCp、Csを単体の回路素子にて構成できる。また、トランスTの寄生要素を用いて電磁結合回路90そのものを単体の共振複合トランスにて構成することも可能である。その他は第2の実施形態で図4に示したものと同様である。
図12は第7の実施形態のスイッチング電源装置107の回路図である。この例では1次側にキャパシタCcを設けて1次側に電圧クランプ回路を構成し、2次側にキャパシタCcsを設けて2次側にも電圧クランプ回路を構成している。その他は第5の実施形態で図7に示したものと同様である。
図13は第8の実施形態のスイッチング電源装置108の回路図である。この例では4つのスイッチング素子Q1,Q2,Q5,Q6によるフルブリッジ回路構成の1次側交流電圧発生回路を設けている。また、4つのスイッチング素子Q3,Q4,Q7,Q8によるブリッジ整流構成の2次側整流回路を設けている。
図14は第9の実施形態のスイッチング電源装置109の回路図である。この例では1次側の共振キャパシタを二つのキャパシタCr1,Cr2に分割配置し、2次側の共振キャパシタを二つのキャパシタCrs1,Crs2に分割配置している。また、4つのスイッチング素子Q1,Q2,Q5,Q6によるフルブリッジ回路構成の1次側交流電圧発生回路を設けている。また、4つのスイッチング素子Q3,Q4,Q7,Q8によるブリッジ整流構成の2次側整流回路を設けている。
これまでに示した各実施形態では、部品としてのトランスを備えて、DC-DCコンバータとして用いるスイッチング電源装置を例に挙げたが、以降の各実施形態では対向する装置間で電気的には非接触で電力伝送を行う装置の例を示す。
(a)非常にシンプルな電力伝送システムとして利用できる。
図16は第11の実施形態の電力送電システムとして用いられるスイッチング電源装置111の回路図である。
図17は第12の実施形態の電力送電システムとして用いられるスイッチング電源装置112の回路図である。
図18は第13の実施形態の電力送電システムとして用いられるスイッチング電源装置113の回路図である。この例では4つのスイッチング素子Q1,Q2,Q5,Q6によるフルブリッジ回路で送電装置側の交流電圧発生回路を構成している。また、4つのスイッチング素子Q3,Q4,Q7,Q8によるブリッジ整流回路で受電装置側の側整流回路を構成している。図18に示すパラメータMは、相互インダクタンスによる磁界結合と相互キャパシタンスによる電界結合との合成による電磁界結合の相互係数として示している。
図19は第14の実施形態の電力送電システムとして用いられるスイッチング電源装置114の回路図である。この例では、送電装置側にキャパシタCcを設けて電圧クランプ回路を構成している。その他は第10の実施形態で図15に示したものと同様である。
図20は第15の実施形態の電力送電システムとして用いられるスイッチング電源装置115の回路図である。この例では、受電装置側にキャパシタCcsを設けて2次側にも電圧クランプ回路を構成している。その他は第14の実施形態で図19に示したものと同様である。
図21は第16の実施形態の電力送電システムとして用いられるスイッチング電源装置116の回路図である。この例では、受電装置側の整流回路を整流ダイオードD3,D4で構成している。この構成によれば、受電装置は簡素な構成で単方向の電力伝送システムとして用いることができる。
図22は第17の実施形態の電力送電システムとして用いられるスイッチング電源装置117の回路図である。この例では、4つのスイッチング素子Q1,Q2,Q5,Q6によるフルブリッジ回路で送電装置側の交流電圧発生回路を構成している。また、受電装置側の整流回路を整流ダイオードD3,D4,D7,D8によるダイオードブリッジで構成している。
図23は第18の実施形態の電力送電システムとして用いられるスイッチング電源装置118の回路図である。この例では、コイルのインダクタLp,Ls間の磁界結合となる相互インダクタンスをMl、キャパシタCp,Cs間の電界結合となる相互キャパシタンスをMc、キャパシタCr,Crs間の電界結合となる相互キャパシタンスをMcrとしてそれぞれ示している。ここでは、キャパシタCr,Crsを含めて電磁界結合回路90を構成する実施例を図示している。
Cp,Cs…並列共振キャパシタ
Cm…相互キャパシタンス
Cr,Crs…直列共振キャパシタ
Cr1,Cr2…共振キャパシタ
Crs…直列共振キャパシタ
Crs1,Crs2…キャパシタ
D3,D4,D7,D8…整流ダイオード
Ds1,Ds2…ダイオード
im…励磁電流
Lp…送電コイル
Lm、Lms…励磁インダクタンス、または相互インダクタンス
Ls…受電コイル
Lr,Lrs…直列共振インダクタ
Mc…電界結合の相互係数
Mcr…電界結合の相互係数
Ml…磁界結合の相互係数
np…1次巻線
ns…2次巻線
Q1,Q2,Q3,Q4…スイッチング素子
Q5,Q6,Q7,Q8…スイッチング素子
S1,S2,S3,S4…スイッチング回路
S5,S6,S7,S8…スイッチング回路
10,20…スイッチング制御回路
30…絶縁回路
40…複共振回路
90…電磁界結合回路
101~118…スイッチング電源装置
Claims (15)
- 1次巻線および2次巻線を備える電磁界結合回路と、
前記1次巻線に接続されたスイッチング回路を備え、該スイッチング回路をスイッチング素子、ダイオード、およびキャパシタの並列接続回路で構成して、入力される直流電圧から交流電圧を発生する1次側交流電圧発生回路と、
前記交流電圧を直流電圧に整流する2次側整流回路と、
1次側に構成され、第1の直列共振インダクタおよび第1の直列共振キャパシタを含む第1の共振回路と、
2次側に構成され、第2の直列共振インダクタおよび第2の直列共振キャパシタを含む第2の共振回路と、
前記1次側交流電圧発生回路のスイッチング素子をデッドタイムを挟んで交互にオン/オフすることによりほぼ方形波状または台形波状の交流電圧を発生させるスイッチング制御回路と、
を備えたスイッチング電源装置において、
前記スイッチング制御回路は、電磁界結合回路を含めた前記第1の共振回路と前記第2の共振回路とを合わせた全体となる複共振回路に流入する電流が、前記1次側交流電圧発生回路から発生する交流電圧よりも遅れる正弦波状の共振電流波形となって、前記スイッチング素子のオン期間およびオフ期間の両期間に前記電磁界結合回路を介して1次側から2次側へ電力が伝送されるように、前記複共振回路に対してインピーダンスが最も小さくなる固有の共振周波数よりも高いスイッチング周波数で前記1次側交流電圧発生回路のスイッチング素子をスイッチング動作し、
前記電磁界結合回路は、前記1次巻線と前記2次巻線との間で相互インダクタンスを介した磁界結合および相互キャパシタンスを介した電界結合とが混合した電磁界共鳴回路を構成し、
前記第1の共振回路と前記第2の共振回路とが共鳴して前記電磁界結合回路の1次側から2次側へ電力が伝送されることを特徴とするスイッチング電源装置。 - 前記スイッチング制御回路は、前記1次側交流電圧発生回路のスイッチング周波数を一定にし、前記スイッチング回路に電流が導通する期間をオン期間、その他の期間をオフ期間として、複数のスイッチング回路のオン期間比率を制御することで、前記2次側整流回路から得られる出力電力を調整する、請求項1に記載のスイッチング電源装置。
- 前記スイッチング制御回路は、前記1次側交流電圧発生回路のスイッチング周波数を変化させて前記スイッチング素子のオン期間比率を制御することで、前記2次側整流回路から得られる出力電力を調整する、請求項1に記載のスイッチング電源装置。
- 前記2次側整流回路は、オン期間またはオフ期間のいずれか、または両期間に、前記2次巻線に発生する電圧を静電エネルギーとして前記第2の共振キャパシタに蓄えて、前記オン期間とオフ期間のそれぞれの期間に前記2次巻線に発生する電圧を加算して直流電圧として出力する、請求項1~3のいずれかに記載のスイッチング電源装置。
- 前記第1の直列共振キャパシタと前記第2の直列共振キャパシタのいずれかまたは両方は直流電圧を保持する、請求項1~4のいずれかに記載のスイッチング電源装置。
- 前記1次巻線または前記2次巻線に対して並列に並列共振キャパシタを備えた、請求項1~5のいずれかに記載のスイッチング電源装置。
- 前記並列共振キャパシタを前記1次巻線または前記2次巻線の浮遊容量で構成した、請求項6に記載のスイッチング電源装置。
- 前記相互キャパシタンスを前記1次巻線と前記2次巻線との間に形成される浮遊容量で構成した、請求項1~7のいずれかに記載のスイッチング電源装置。
- 前記第1の直列共振インダクタまたは前記第2の直列共振インダクタを前記電磁界結合回路の漏れインダクタンスで構成した、請求項1~8のいずれかに記載のスイッチング電源装置。
- 前記相互インダクタンスを前記1次巻線と前記2次巻線との間に等価的に形成される励磁インダクタンスで構成した、請求項1~9のいずれかに記載のスイッチング電源装置。
- 前記スイッチング回路はMOSFETである、請求項1~10のいずれかに記載のスイッチング電源装置。
- 前記2次側整流回路に備えられる前記交流電圧を直流電圧に整流する整流素子はMOSFETである、請求項1~11のいずれかに記載のスイッチング電源装置。
- 前記2次側整流回路の出力部から電力が伝送されるとき、前記2次側整流回路は前記1次側交流電圧発生回路として作用するとともに、前記1次側交流電圧発生回路は前記2次側整流回路として作用し、
双方向に電力伝送が可能な、請求項12に記載のスイッチング電源装置。 - 前記1次巻線は磁芯を有するトランスの1次側に設けられた巻線、前記2次巻線は前記トランスの2次側に設けられた巻線である、請求項1~13のいずれかに記載のスイッチング電源装置。
- 前記1次巻線は送電装置に設けられた送電コイル、前記2次巻線は前記送電装置に向けて配置される受電装置に設けられた受電コイルである、請求項1~13のいずれかに記載のスイッチング電源装置。
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Also Published As
Publication number | Publication date |
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US9106141B2 (en) | 2015-08-11 |
EP2670037A1 (en) | 2013-12-04 |
JP5321758B2 (ja) | 2013-10-23 |
EP2670037B1 (en) | 2022-11-16 |
CN103339843B (zh) | 2016-06-01 |
US20130301308A1 (en) | 2013-11-14 |
KR20130114693A (ko) | 2013-10-17 |
KR101439495B1 (ko) | 2014-09-11 |
EP2670037A4 (en) | 2018-03-21 |
CN103339843A (zh) | 2013-10-02 |
JPWO2012101905A1 (ja) | 2014-06-30 |
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