WO2010016232A1 - 無線受信装置 - Google Patents
無線受信装置 Download PDFInfo
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- WO2010016232A1 WO2010016232A1 PCT/JP2009/003701 JP2009003701W WO2010016232A1 WO 2010016232 A1 WO2010016232 A1 WO 2010016232A1 JP 2009003701 W JP2009003701 W JP 2009003701W WO 2010016232 A1 WO2010016232 A1 WO 2010016232A1
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/08—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station
- H04B7/0837—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the receiving station using pre-detection combining
- H04B7/0842—Weighted combining
- H04B7/0848—Joint weighting
- H04B7/0854—Joint weighting using error minimizing algorithms, e.g. minimum mean squared error [MMSE], "cross-correlation" or matrix inversion
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L1/00—Arrangements for detecting or preventing errors in the information received
- H04L1/02—Arrangements for detecting or preventing errors in the information received by diversity reception
- H04L1/06—Arrangements for detecting or preventing errors in the information received by diversity reception using space diversity
- H04L1/0618—Space-time coding
- H04L1/0631—Receiver arrangements
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B7/00—Radio transmission systems, i.e. using radiation field
- H04B7/02—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas
- H04B7/04—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas
- H04B7/06—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station
- H04B7/0613—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission
- H04B7/0667—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of delayed versions of same signal
- H04B7/0669—Diversity systems; Multi-antenna system, i.e. transmission or reception using multiple antennas using two or more spaced independent antennas at the transmitting station using simultaneous transmission of delayed versions of same signal using different channel coding between antennas
Definitions
- the present invention relates to a radio reception apparatus that receives radio communication, and more particularly, to a radio reception apparatus that receives a signal spatially transmitted from a radio transmission station using a plurality of antennas.
- FIG. 17 shows a conventional wireless transmission device and wireless reception device disclosed in Patent Document 1.
- the wireless transmission device includes a signal input terminal 800, a space-time encoder (described as “STE1” in FIG. 17) 801, a space-time encoder (described as “STE2” in FIG. 17) 802, Inverse Fast Fourier Transform (described as “IFFT1” in FIG. 17) 803, Inverse Fast Fourier Transform (indicated as “IFFT2” in FIG. 17) 804, Inverse Fast Fourier Transform (indicated as “IFFT3” in FIG. 17) 805 , Inverse fast Fourier transform (indicated as “IFFT4” in FIG. 17) 806, transmitting antenna (indicated as “TA1” in FIG. 17) 807, transmitting antenna (indicated as “TA2” in FIG. 17) 808, transmitting antenna 17 (described as “TA3” in FIG. 17) and a transmission antenna 810 (described as “TA4” in FIG. 17).
- the wireless receiver includes a receiving antenna (described as “RA1” in FIG. 17) 811, a receiving antenna (described as “RA2” in FIG. 17) 812, and a receiving antenna (denoted as “RAp” in FIG. 17).
- RA1 receiving antenna
- RA2 receiving antenna
- RAp receiving antenna
- FFT1 Fast Fourier Transform subsystem
- FFT2 Fast Fourier Transform subsystem
- FFTp Fast Fourier Transform subsystem
- FFTp Fast Fourier Transform subsystem
- STP space-time processor
- STD1 space-time decoder
- STD1 space-time decoder
- FIG. 819 space-time decoder
- CPE channel parameter estimator
- the data block input to the input terminal 800 is separated into a data block b1 [n, k] and a data block b2 [n, k].
- the data block b1 [n, k] is input to the space time encoder 801
- the data block b2 [n, k] is input to the space time encoder 802.
- the space-time encoder 801 and the space-time encoder 802 each generate two data pairs, and the data block b1 [n, k] and the data block b2 [n, k] have a total of four data (tm1 [n , K] to tm4 [n, k]).
- the inverse fast Fourier transform 803 to the inverse fast Fourier transform 806 modulate the four pieces of converted data (tm1 [n, k] to tm4 [n, k]), and output each as an OFDM signal.
- the transmission antenna 807 to the transmission antenna 810 wirelessly transmit these OFDM signals.
- the wirelessly transmitted OFDM signal is spatially transmitted and then received from the receiving antenna 811 by the receiving antenna 813. As shown in FIG. 17, the OFDM signals transmitted from the transmitting antenna 807 by the transmitting antenna 810 are received by the receiving antenna 811 from the receiving antenna 811 in a state where they are superimposed on each other in the transmission space.
- the fast Fourier transform subsystem 814 converts the signal r 1 [n, k] received by the receiving antenna 811 into a frequency space signal and supplies it to the space time processor 817.
- the fast Fourier transform subsystem 815 converts the signal r 2 [n, k] received by the receiving antenna 812 into a frequency space signal and supplies it to the space time processor 817.
- the fast Fourier transform subsystem 816 converts the signal rp [n, k] received by the receiving antenna 813 into a frequency space signal and supplies it to the space time processor 817.
- Channel parameter estimator 820 receives signals transformed by fast Fourier transform subsystem 816 from fast Fourier transform subsystem 814 and determines channel parameter information from those transformed signals.
- Channel parameter estimator 820 then provides the decision results to space time decoder 818 and space time decoder 819 for use in decoding.
- the space-time processor 817, the space-time decoder 818, the space-time decoder 819, and the channel parameter information are used to separate and decode the transmission signal that has been spatially multiplexed and output to the output terminal 821 and the output terminal 822.
- Non-Patent Document 1 discloses an interference suppression reception technique that was technically announced at IEICE 2005.
- FIG. 18 shows a wireless transmission device and a wireless reception device described in Non-Patent Document 1.
- the wireless transmission device 500 includes a communication control unit 501, a first IFFT unit 502, a second IFFT unit 504, a transmission antenna 503, and a transmission antenna 505.
- the principle and operation are the same as those of the wireless transmission device described in Patent Document 1 described above.
- the radio reception apparatus includes a reception antenna 601, a reception antenna 603, a first FFT unit 602, a second FFT unit 604, a demapping unit 611, a Viterbi decoding unit 612, and an interference suppression unit 600.
- the interference suppression unit 600 includes a weighting synthesis unit 605, a transmission path estimation unit 606, an unnecessary signal measurement unit 607, and a reliability evaluation unit 610.
- the interference station 700 transmits a radio interference wave that interferes in the fading transmission path 900 with respect to the radio wave wirelessly transmitted by the wireless transmission device 500.
- the receiving antenna 601 and the receiving antenna 602 receive the OFDM signal mixed with the above-described radio interference wave.
- the first FFT unit 602 and the second FFT unit 604 each perform fast Fourier transform on the received OFDM signal and output the result in units of OFDM subcarriers.
- interference suppression units 600 prepared for the number of subcarriers perform processing for removing interference waves simultaneously with demodulation of signals transmitted from radio transmission apparatus 500.
- transmission path estimation section 606 calculates a transmission path coefficient matrix H representing the transmission state of fading transmission path 900 using the preamble symbol of the packet.
- the transmission path coefficient matrix H is obtained by the same calculation as that of normal MIMO demodulation.
- the unnecessary signal measurement unit 607 detects the interference wave signal at a time when the desired wave packet is not transmitted between the transmission of the desired wave packet and the transmission of the next desired wave packet.
- a variance matrix Ruu is obtained.
- FIG. 19A shows the relationship between the OFDM subcarrier 701 and the noise component 702 before being weighted and combined by the weighting / synthesizing unit 605.
- FIG. 19B illustrates an OFDM subcarrier 703 and a residual error 704 that are normalized after being weighted and combined by the weighting and combining unit 605.
- the reliability evaluation unit 610 calculates the reciprocal of the residual error e (residual interference wave signal) at the time when the subcarrier amplitudes after weighted synthesis are normalized as the likelihood ⁇ representing the signal likelihood.
- the demapping unit 611 restores the mapping of each subcarrier unit signal output from the interference suppression unit 600.
- Viterbi decoding means 612 performs error correction processing on the signal whose mapping has been restored using the likelihood ⁇ described above, and outputs a demodulated signal.
- FIG. 20 shows that the required SIR (signal-to-interference ratio) for obtaining the same PER (packet error rate) is improved by about 10 dB + 5 dB by two processes of interference suppression by weighting synthesis and Viterbi decoding using likelihood. It is a simulation result.
- the horizontal axis indicates the required SIR
- the vertical axis indicates the PER.
- the weighted synthesis effect 212 is about 10 dB
- the effect 211 considering the Viterbi likelihood is further about 5 dB.
- the conventional radio receiving apparatus uses the preamble of the desired wave packet when estimating the transmission path of the desired wave, and therefore has a problem that the transmission path cannot be estimated by continuous wave transmission without the preamble.
- the present invention provides a radio receiving apparatus that performs transmission path estimation and interference wave signal detection even if the desired wave is a continuous wave such as a digital broadcast wave, thereby reducing the deterioration of reception sensitivity due to noise.
- the radio reception apparatus includes a plurality of reception antennas that receive multicarrier transmission waves, a plurality of frequency space conversion units that are individually connected to the reception antennas and convert signals received by the reception antennas into frequency space signals, and a frequency Calculation of the channel coefficient matrix of at least multicarrier transmission wave for frequency space signals individually connected to the space conversion unit and converted by the plurality of frequency space conversion units, and between the antennas between the plurality of receiving antennas
- a plurality of noise wave removal units that perform covariance matrix calculation, a back-end signal processing unit that performs back-end processing on a signal related to the output of the noise wave removal unit, and a specific signal from a signal received by the receiving antenna
- a pattern detection unit that detects data, a broadcast stop detection unit that determines the stop status of a multicarrier transmission wave, and a broadcast stop detection unit And a back-end operation control unit for executing the operation of the back-end signal processing unit upon detection of the stopping of the signal wave.
- the plurality of noise wave removal units calculate the inter
- FIG. 1 is a conceptual diagram showing a broadcasting station, a spatial transmission path, and a radio receiving apparatus according to the present invention.
- FIG. 2A is a time chart showing a received signal.
- FIG. 2B shows an example of a noise waveform.
- FIG. 2C is a time chart showing a received signal.
- FIG. 3 is a functional block diagram of the radio reception apparatus according to Embodiment 1 of the present invention.
- FIG. 4 is a functional block diagram of the noise wave removing unit according to Embodiment 1 of the present invention.
- FIG. 5 is a functional block diagram of the transmission path estimation unit according to Embodiment 1 of the present invention.
- FIG. 6 is a functional block diagram of the unnecessary signal measuring unit according to Embodiment 1 of the present invention.
- FIG. 1 is a conceptual diagram showing a broadcasting station, a spatial transmission path, and a radio receiving apparatus according to the present invention.
- FIG. 2A is a time chart showing a received signal.
- FIG. 7 is a functional block diagram of the weighting synthesis unit in Embodiment 1 of the present invention.
- FIG. 8 is a functional block diagram of the broadcast stoppage detection unit in Embodiment 1 of the present invention.
- FIG. 9 is a functional block diagram of the sync pattern detection unit in the first to fourth embodiments of the present invention.
- FIG. 10 is a functional block diagram of the radio reception apparatus according to Embodiments 2 to 4 of the present invention.
- FIG. 11 is a functional block diagram of the first compensation buffer unit in the second embodiment of the present invention.
- FIG. 12 is a control signal time chart according to Embodiment 2 of the present invention.
- FIG. 13 is a functional block diagram of the second compensation buffer unit in the third embodiment of the present invention.
- FIG. 14 is a control signal time chart according to the third embodiment of the present invention.
- FIG. 15 is a functional block diagram of the third compensation buffer unit in the fourth embodiment of the present invention.
- FIG. 16 is a control signal time chart according to the fourth embodiment of the present invention.
- FIG. 17 is a functional block diagram of a conventional wireless reception device and transmission device.
- FIG. 18 is a functional block diagram of a conventional wireless reception device and transmission device.
- FIG. 19A is an explanatory diagram showing subcarriers and likelihood.
- FIG. 19B is an explanatory diagram showing subcarriers and likelihood.
- FIG. 20 is a diagram illustrating the effect of the interference cancellation technique.
- FIG. 1 is a configuration diagram illustrating a broadcasting station, a transmission path, and a wireless reception device in the first embodiment.
- a broadcast station 1 transmits a digital broadcast wave subjected to multicarrier OFDM modulation.
- a broadcast wave 2 from the broadcast station 1 is spatially transmitted via a fading transmission path 3.
- the fading transmission path 3 is a transmission path in which the broadcast wave 2 has a transmission characteristic with reflection and attenuation.
- the wireless reception device 9 includes a reception antenna 4, a reception antenna 5, a front end unit 6, and a back end unit 7.
- the front end unit 6 is a part that mainly performs processing related to wireless reception.
- the back end unit 7 is a part that mainly performs processing not related to wireless processing.
- the back end unit 7 includes a digital LSI group 8 that decodes a compressed image. Since the digital LSI group 8 generates a noise signal 16 associated with a digital operation during operation, reception quality deteriorates when the noise signal 16 jumps into the reception antenna 4 and the reception antenna 5 in the front stage of the front end unit 6.
- the configuration for canceling the unnecessary noise signal 16 jumping into the receiving antennas 4 and 5 from the inside or the vicinity of the wireless receiving device 9 and improving the reception quality will be described in detail with reference to the drawings.
- the above-described multicarrier OFDM-modulated digital broadcast wave is an example of a multicarrier transmission wave. In the following description of the present invention, a multi-carrier OFDM modulated digital broadcast wave will be described as an example as a multi-carrier transmission wave.
- FIG. 3 is a block configuration diagram of the radio reception apparatus according to Embodiment 1 of the present invention.
- the wireless reception device 9 includes a reception antenna 4, a reception antenna 5, a first FFT (frequency space conversion) unit 26, a second FFT (frequency space conversion) unit 27, a noise wave removal unit 28, and a demapping unit. 29, a Viterbi decoding unit 100, a back-end signal processing unit 32, a back-end operation control unit 33, a broadcast stoppage detection unit 30, and a sync pattern detection unit 31.
- the reception antenna 4 and the reception antenna 5 are examples of a plurality of reception antennas. In the following description of the present invention, the receiving antenna 4 and the receiving antenna 5 will be described as examples of the plurality of receiving antennas.
- the OFDM signal of the multicarrier transmission wave that is a broadcast wave received by the reception antenna 4 is input to the first FFT unit 26.
- An OFDM signal of a multicarrier transmission wave that is a broadcast wave received by the reception antenna 5 is input to the second FFT unit 27.
- These two FFT units receive signals (individual signals received by the receiving antenna 4 and the receiving antenna 5) in units of antennas from time-space signals in frequency space. It is an example of the frequency space conversion part which carries out the Fourier-transform to a signal.
- the first FFT unit 26 and the second FFT unit 27 output the same number as the number of subcarriers constituting the OFDM signal.
- the noise wave removing unit 28 removes the noise signal 16 emitted from the back-end signal processing unit 32 and mixed with the original signal received by the receiving antenna 4 or the receiving antenna 5 for each subcarrier.
- the demapping unit 29 performs a process reverse to the process of mapping the signal from which noise has been removed in units of subcarriers to each subcarrier, rearranges the data, and outputs the result.
- the output of the demapping unit 29 is input to the back-end signal processing unit 32 via the Viterbi decoding unit 100.
- the back-end signal processing unit 32 performs processing for restoring video and audio, such as system decoding and elementary decoding of compressed AV streams, and processing related to display. That is, the back-end signal processing unit 32 executes processing including at least MPEG data decoding processing.
- the back end signal processing unit 32 is included in the back end unit 7 of FIG.
- Broadcast stop detection unit 30 detects whether a desired broadcast wave is being transmitted or stopped, and outputs the detection result to noise wave removal unit 28 and back-end operation control unit 33. In this way, the broadcast stoppage detection unit 30 controls the noise wave removal unit 28 and controls the operation of the backend signal processing unit 32 via the backend operation control unit 33. By doing so, an operation for calculating an inter-antenna covariance matrix Ruu representing a correlation between noise antennas described later is performed.
- the sync pattern detection unit 31 detects a specific pattern from a continuous wave such as a broadcast wave in order to estimate a transmission path of the broadcast wave, and a control signal for obtaining a transmission path coefficient matrix H using the specific pattern Is input to the noise wave removing unit 28.
- the sync pattern detection unit 31 is an example of a pattern detection unit that detects specific data from multicarrier transmission waves received by the reception antennas 4 and 5.
- the back-end operation control unit 33 has a data ROM or the like for operating in the same manner as the broadcast wave reception state. Then, since the broadcast stop detection unit 30 measures the noise signal 16 while outputting the broadcast stop detection signal and obtains the inter-antenna covariance matrix Ruu representing the correlation between the antennas, the back-end operation control unit 33 The end signal processing unit 32 is operated. That is, an operation for forcibly generating the noise signal 16 is performed. In the case of digital broadcasting, the above-described operation can be realized by having MPEG2TS data that can be decoded in a ROM or the like.
- FIG. 2A to 2C illustrate the difference between the packet transmission of the conventional example and the continuous wave transmission of the first embodiment.
- FIG. 2A is a time chart showing conventional packet transmission, and the horizontal axis is time t.
- the wireless packet 10 includes a preamble 11 and a data body 12, and the wireless packet 13 includes a preamble 14 and a data body 15.
- a fixed pattern symbol is transmitted in the preambles 11 and 14 at the head of each of the wireless packets 10 and 13. Transmission path estimation during packet communication is usually performed using preamble 11 and 14 signals.
- FIG. 2B shows the noise signal 16.
- FIG. 2A is a time chart showing conventional packet transmission, and the horizontal axis is time t.
- the wireless packet 10 includes a preamble 11 and a data body 12
- the wireless packet 13 includes a preamble 14 and a data body 15.
- a fixed pattern symbol is transmitted in the preambles 11 and 14 at the head of each of the wireless packets 10 and 13.
- Transmission path estimation during packet communication
- FIG. 2C is a time chart illustrating a digital broadcast wave.
- the horizontal axis indicates time t.
- the MPEG2TS packet 17 is composed of a part representing the head (header) 18 of the MPEG2TS and a part representing the data body 19.
- the MPEG2 TS packet 20 is composed of a portion representing the head (header) 21 of the MPEG2 TS and a portion representing the data body 22.
- the MPEG2 TS packet 23 is composed of a portion representing the head (header) 24 of the MPEG2 TS and a portion representing the data body 25.
- the part representing the heads (headers) 18, 21 and 24 of the MPEG2TS has a sync byte at a predetermined position of this part. Since the sync byte of MPEG2TS is “0x47” and is a fixed value, if the sync byte can be found from the data string, it can be used for transmission path estimation instead of the preamble patterns 11 and 14 of FIG. 2A. . Note that “0x” in “0x47” indicates hexadecimal display, and “0x47” indicates “47” in hexadecimal display.
- Sync byte detection is realized by a combination of pattern matching and periodicity detection in a normal MPEG system decoder.
- FIG. 4 is a block configuration diagram showing details of the noise wave removing unit 28.
- the noise wave removal unit 28 includes a signal input terminal 34 from the first FFT unit 26, a signal input terminal 35 from the second FF unit 27, a control signal input terminal 36 from the sync pattern detection unit 31, and broadcast stop detection.
- the evaluation unit 43 is configured.
- the transmission channel estimation unit 41 calculates a transmission channel coefficient matrix H representing the transmission state of the fading transmission channel using the MPEG2TS sync byte pattern “0x47”.
- the sync byte pattern “0x47” is detected by the sync pattern detection unit 31 described above, and is input to the transmission path estimation unit 41 via the control signal input terminal 36.
- the sync pattern detection unit 31 detects not only the sync byte pattern “0x47”.
- the sync pattern detection unit 31 only needs to detect an MPEG standard synchronization code or an MPEG standard start code. That is, the sync pattern detection unit 31 that is a pattern detection unit may be any unit that detects an MPEG standard synchronization code or an MPEG standard start code.
- FIG. 5 is a diagram illustrating a block configuration example of the transmission path estimation unit 41.
- the transmission path estimation unit 41 includes an input terminal 44 from the sync pattern detection unit 31, an input terminal 45 from the first FFT unit 26 and the second FFT unit 27, an output terminal 46 to the weighting synthesis unit 40, and reliability evaluation.
- An output terminal 47 to the unit 43, a transmission channel coefficient calculation unit 48, and a transmission channel coefficient storage unit 49 are included.
- the input terminal 44 is connected to the input terminal 36 of FIG. 4, and the input terminal 45 is connected to the input terminal 34 and the input terminal 35 of FIG.
- the subcarriers after FFT are input to the transmission line coefficient calculation unit 48 via the input terminal 45, and the transmission line coefficient calculation unit 48 corresponds to the sync byte pattern of the subcarrier using the detection result of the sync pattern detection unit 31.
- the transmission path coefficient matrix H is calculated based on the signal to be transmitted.
- the transmission path coefficient calculation unit 48 uses the pattern detection signal input from the input terminal 44 in order to specify the signal corresponding to the sync byte pattern.
- the calculation principle for obtaining the channel coefficient matrix H from the signal corresponding to the sync byte pattern is the same as that of the corresponding block of the conventional example.
- the transmission path coefficient matrix H obtained by the transmission path coefficient calculation section 48 is input to the transmission path coefficient storage section 49, and the transmission path coefficient storage section 49 stores the value of the transmission path coefficient matrix H. Then, the transmission path coefficient storage unit 49 outputs the value of the transmission path coefficient matrix H to the next calculation block (the weighting synthesis unit 40 and the reliability evaluation unit 43) via the output terminals 46 and 47.
- the timing at which the transmission channel coefficient storage unit 49 stores the transmission channel coefficient matrix H is performed in synchronization with the transmission channel coefficient calculation unit 48. Therefore, the sync pattern detection signal input from the input terminal 44 is also given to the transmission path coefficient storage unit 49 for synchronization.
- the unnecessary signal measuring unit 42 determines the broadcast stoppage based on the output signal of the broadcast stoppage detection unit 30 input via the control signal input terminal 37. Then, the unnecessary signal measurement unit 42 detects the noise signals u1 and u2 (hereinafter also referred to as interference wave signals) at the time when the broadcast wave is not transmitted, and further calculates the inter-antenna covariance matrix Ruu (formula Obtained using 1).
- the noise signal u1 is a signal received by the first receiving antenna 4 and is represented by a column vector U.
- the noise signal u2 is a signal received by the second receiving antenna 5 and is represented by a column vector U.
- FIG. 6 is a block diagram showing the unnecessary signal measuring unit 42.
- the unnecessary signal measurement unit 42 includes an input terminal 91 from the first FFT unit 26 and the second FFT unit 27, an input terminal 92 from the broadcast stoppage detection unit 30, and an output terminal to the weighting synthesis unit 40. 50, an output terminal 51 to the reliability evaluation unit 43, an inter-antenna covariance calculation unit 52, and a storage unit 53.
- the input terminal 92 is connected to the input terminal 37 of FIG.
- the noise signals (interference wave signals) u1 and u2 described above are input to the inter-antenna covariance calculation unit 52 from the input terminal 92, and the inter-antenna covariance calculation unit 52 obtains the inter-antenna covariance matrix Ruu according to Equation 1.
- the inter-antenna covariance matrix Ruu is calculated by measuring the noise signal after the broadcast wave stoppage is determined based on the output signal of the broadcast stoppage detection unit 30 input from the input terminal 91.
- the storage unit 53 The calculated inter-antenna covariance matrix Ruu is stored.
- the stored inter-antenna covariance matrix Ruu is output to the weighting synthesis unit 40 and the reliability evaluation unit 43 via the output terminals 50 and 51.
- the weighting combining unit 40 combines the two input signals using the inter-antenna covariance matrix Ruu calculated by Equation 1 and the transmission channel coefficient matrix H for each subcarrier component constituting the OFDM signal. W is calculated by Equation 2.
- the derivation of Equation 2 is as follows.
- a signal vector s is calculated by performing a weighting synthesis operation using the weighting factor W on the received signal vectors r from the two antennas.
- Equation 3 synthesizes the received signal vector r from the two antennas (antenna 4 and antenna 5) so that the mean square error between the signal vector s after the weighted synthesis and the transmission signal from the desired station is minimized.
- I mean Since the inter-antenna covariance matrix Ruu reflects the inter-antenna correlation component of the noise signal 16, it is possible to perform demodulation while suppressing noise waves. Further, when there is no noise wave, the inter-antenna covariance matrix Ruu has only noise wave noise components, which is equivalent to reception by maximum ratio synthesis. Therefore, in the present invention, it is possible to adaptively always keep reception errors small.
- FIG. 7 is a block configuration diagram showing the weighting synthesis unit 40.
- the weighting synthesis unit 40 includes an input terminal 54 from the first FFT unit 26, an input terminal 55 from the second FFT unit 27, an input terminal 56 from the transmission path estimation unit 41, and an input terminal from the unnecessary signal measurement unit 42. 57, an output terminal 58 to the demapping unit 29, a combining unit 59, and a weighting coefficient calculating unit 60.
- the input terminal 54 is connected to the input terminal 34 of FIG. 4, the input terminal 55 is connected to the input terminal 35 of FIG. 4, the output terminal 58 is connected to the output terminal 38 of FIG. 4, and the input terminal 57 is the output of FIG.
- the terminal 50 is connected.
- the transmission path coefficient matrix H input from the input terminal 56 and the inter-antenna covariance matrix Ruu input from the input terminal 57 are input to the weighting coefficient calculator 60.
- the weighting coefficient calculation unit 60 calculates the weighting coefficient W according to Equation 2 and outputs it to the synthesis unit 59.
- the synthesizer 59 uses the received signal vector r obtained by frequency-space conversion of the signals from the two antennas (antennas 4 and 5) input from the input terminals 54 and 55 and the weighting coefficient W from the weighting coefficient calculator 60. 3 is combined to obtain an output signal s.
- the output signal s is output from the output terminal 58 and input to the demapping unit 29 for each subcarrier.
- the channel coefficient matrix H and the inter-antenna covariance matrix Ruu are also input to the reliability evaluation unit 43 in addition to the weighting synthesis unit 40, and the reliability evaluation unit 43 calculates the likelihood ⁇ representing the probability. And output from the output terminal 39.
- FIG. 19A shows the relationship between the OFDM subcarrier 701 and the noise component 702 before weighted synthesis
- FIG. 19B shows the normalized OFDM subcarrier 703 and residual error 704 after weighted synthesis.
- the noise wave signal 704 remaining after the weighted synthesis is different for each subcarrier.
- the residual error e is also called a residual interference wave signal, and the residual error e is expressed by Equation 4. Since the residual error e and the likelihood ⁇ are expressed by the equations 4 and 5, as described above, the reliability evaluation unit 43 calculates the likelihood ⁇ according to this.
- the demapping unit 29 restores and outputs the mapping of each subcarrier unit signal output from the noise wave removing unit 28.
- the Viterbi decoding unit 100 performs error correction processing on the signal obtained by restoring the mapping output from the demapping unit 29, and outputs a demodulated signal.
- FIG. 8 is a block diagram showing the broadcast stoppage detection unit 30.
- the broadcast stoppage detection unit 30 includes an input terminal 61 from the Viterbi decoding unit 100, an input terminal 62 from the reception antenna 4, an input terminal 63 from the reception antenna 5, a noise wave removal unit 28, and back-end operation control.
- the first low noise amplifier 65 amplifies the signal received by the receiving antenna 4 input via the input terminal 62 to a desired amplitude.
- the second low noise amplifier 66 amplifies the signal received by the receiving antenna 5 input via the input terminal 63 to a desired amplitude and outputs the amplified signal.
- the first detector 67a detects the output of the first low noise amplifier 65, converts it to a power signal representing the intensity of the radio wave, and outputs it.
- the second detector 68a detects the output of the second low noise amplifier 66, converts it into a power signal representing the intensity of the radio wave, and outputs it.
- the signals after power conversion output from the first detection unit 67a and the second detection unit 68a are added by, for example, the addition unit 69.
- the threshold determination unit 70 determines that there is a signal if the output signal of the addition unit 69 is equal to or greater than a predetermined threshold, and determines whether the signal is being broadcast or stopped.
- the input terminal 61 performs a broadcast check using a method different from the method of detecting the radio wave and directly measuring the power, such as whether or not the demodulated data is transmitted data, thereby increasing the reliability of the determination. It is provided for this purpose.
- the MPEG2TS input to the back-end signal processing unit 32 is input, and the pattern detection unit 72 compares with the MPEG2TS pattern for determination.
- the MPEG2TS pattern is stored in the first pattern generator 73a.
- the stored pattern may be the sync byte pattern described above or a special header pattern of system / elementary.
- the result determined by the first pattern detection unit 72 a is input to the determination unit 71 simultaneously with the result of the threshold determination unit 70. Since the determination unit 71 determines based on a plurality of determination results, the determination unit 71 outputs a highly reliable determination result to the output terminal 64.
- FIG. 9 is a block diagram showing the sync pattern detection unit 31.
- the sync pattern detection unit 31 includes an input terminal 74 from the Viterbi decoding unit 100, an input terminal 75 from the reception antenna 4, an input terminal 76 from the reception antenna 5, an output terminal 77 to the noise wave removal unit 28, 1st low noise amplifier 65, 2nd low noise amplifier 66, 3rd detection part 67b, 4th detection part 68b, 2nd pattern generation part 73b, 2nd pattern detection part 72b, 1st waveform detection part 78, a second waveform detection unit 79, a first periodicity detection unit 80, a second periodicity detection unit 81, a third periodicity detection unit 82, and an interpolation unit 83.
- the MPEG2TS input to the back-end signal processing unit 32 is also input to the second pattern detection unit 72b via the input terminal 74.
- the second pattern detection unit 72b receives the input MPEG2TS sync byte and the pattern “0x47”. And judge.
- the sync byte pattern “0x47” is stored in the second pattern generation unit 73b.
- the first periodicity detection unit 80 confirms the periodicity of the pattern and excludes the false sync pattern.
- the system connected to the input terminals 75 and 76 is a system for directly determining the pattern in the radio wave state in order to further improve the sync detection accuracy.
- a signal received by the receiving antenna 4 via the input terminal 75 is input to the first low noise amplifier 65, and the first low noise amplifier 65 amplifies the input signal to a desired amplitude and outputs it.
- a signal received by the receiving antenna 5 via the input terminal 76 is input to the second low noise amplifier 66, and the second low noise amplifier 66 amplifies the input signal to a desired amplitude and outputs the amplified signal.
- the third detector 67b detects the output signal of the first low noise amplifier 65 and outputs a signal waveform.
- the fourth detector 68b detects the output signal of the second low noise amplifier 66 and outputs a signal waveform. Unlike the first detection unit 67a and the second detection unit 68a in FIG.
- the third detection unit 67b and the fourth detection unit 68b output waveforms.
- the first waveform detector 78 detects the waveform of the output from the third detector 67b.
- the second waveform detector 79 detects the waveform of the output from the fourth detector 68b.
- the second periodicity detection unit 81 determines the periodicity of the output waveform of the first waveform detection unit 78 and inputs the determination result to the interpolation unit 83.
- the third periodicity detection unit 82 determines the periodicity of the output waveform of the second waveform detection unit 79 and inputs the determination result to the interpolation unit 83.
- the interpolating unit 83 determines whether or not a sync that should have periodicity is missing, and if missing, performs an operation of interpolating the sync at the sync position. In this way, even if a sync detection error occurs, a sync that is not missed can be output.
- the broadcast stop detection unit 30 operates to output the above-described signal, controls the operation of the noise wave removal unit 28, and operates the back end signal processing unit 32 via the back end operation control unit 33.
- the sync pattern detection unit 31 operates to output the above-described signal, and controls the operation of the noise wave removal unit 28.
- the wireless reception device 9 weights and synthesizes the reception signals of the plurality of antennas using the weighting coefficient obtained from the transmission path estimation and the inter-antenna covariance, and transmits the broadcast wave transmission path using the sync pattern “0x47”.
- the back end is operated during the broadcast stop by means of estimating and judging the broadcast stop, and the jumping noise from the back end is detected.
- continuous broadcast waves that cannot be achieved by the conventional method, in particular, interference waves such as noise waves when receiving MPEG2TS broadcasts can be removed, and reception sensitivity can be improved in a digital reception TV or the like.
- FIG. 10 is a block configuration diagram of a radio reception apparatus according to Embodiment 2 of the present invention.
- the other components are the same, and the same reference numerals are used for the same components as those in the first embodiment, and a detailed description thereof is partially omitted.
- FIG. 10 is a block configuration diagram of a radio reception apparatus according to Embodiment 2 of the present invention.
- the other components are the same, and the same reference numerals are used for the same components as those in the first embodiment, and
- a first compensation buffer unit 84a and a back-end operation stop unit 85 are added to the radio reception apparatus of the first embodiment to further improve noise removal performance.
- the first compensation buffer unit 84a is an example of a compensation buffer unit that stores received data and intermittently inputs the stored received data to the back-end signal processing unit.
- the OFDM signal of the multicarrier transmission wave received by the receiving antenna 4 is input to the first FFT unit 26.
- the OFDM signal of the multicarrier transmission wave received by the receiving antenna 5 is input to the second FFT unit 27.
- the first FFT unit 26 and the second FFT unit 27 are frequency space conversion means for Fourier transforming a signal received in antenna units from a time space signal to a frequency space signal.
- the first FFT unit 26 and the second FFT unit 27 output the same number of outputs as the number of subcarriers constituting the OFDM signal, and these outputs are input to the noise wave removing unit 28 prepared for each subcarrier.
- the noise wave removing unit 28 removes the noise signal 16 mixed with the receiving antennas 4 and 5 from the back-end signal processing unit 32 for each subcarrier.
- the demapping unit 29 performs a process reverse to the process of mapping the signal from which noise has been removed in units of subcarriers to each subcarrier, rearranges the data, and inputs the data to the Viterbi decoding unit 100.
- the Viterbi decoding unit 100 performs Viterbi decoding processing on the input signal, and then inputs it to the first compensation buffer unit 84a.
- the first compensation buffer unit 84a intermittently inputs the data input to the first compensation buffer unit 84a to the back-end signal processing unit 32.
- the back-end signal processing unit 32 performs processing related to video / audio restoration and display processing such as system decoding and elementary decoding of a compressed AV stream. In the second embodiment, processing can be performed in accordance with intermittent data input. It is configured as follows.
- the broadcast stop wave detection unit 30 detects whether a desired broadcast wave is being transmitted or stopped, and outputs the detection result to the noise wave removal unit 28 and the back-end operation control unit 33.
- the broadcast stoppage detection unit 30 controls the operation of the noise wave removal unit 28 and also controls the operation of the backend signal processing unit 32 via the backend operation control unit 33.
- the sync pattern detection unit 31 performs an operation of detecting a specific pattern from a continuous wave such as a broadcast wave and inputting the pattern detection result to the back-end operation stop unit 85 in order to estimate the transmission path of the broadcast wave. .
- the back-end operation stop unit 85 periodically outputs a control timing signal to the first compensation buffer unit 84a that compensates for data loss at the time of stop simultaneously with the process of stopping the operation of the back-end signal processing unit 32.
- FIG. 12 is a time chart showing control signals of the FIFO memory in the back-end operation stop unit 85 and the first compensation buffer unit 84a.
- the back-end operation stop unit 85 intermittently thins out the “SYNC” 121 pulse of FIG. 12 that is the output signal of the sync pattern detection unit 31, generates a long-cycle “CTRL” 122 pulse, and generates a noise wave removal unit 28, the data is input to the back-end signal processing unit 32 and the first compensation buffer unit 84a.
- FIG. 11 is a block diagram of the first compensation buffer unit 84a.
- the first compensation buffer unit 84a includes an input terminal 86 from the back-end operation stop unit 85, an input terminal 87 from the Viterbi decoding unit 100, an output terminal 88 to the back-end signal processing unit 32, and a first control signal generation unit. 89a and a FIFO storage unit 90.
- the FIFO storage unit 90 is an example of a storage unit that stores received data.
- the first control signal generation unit 89a is a control signal of the FIFO storage unit 90 based on the CTRL signal (“CTRL” 122 in FIG. 12 and hereinafter referred to as “CTRL” 122) input from the input terminal 86.
- CTRL CTRL
- a certain write enable (“WEN” 123 in FIG. 12, hereinafter referred to as “WEN” 123), write reset (“WRST” 124 in FIG. 12, hereinafter referred to as “WRST” 124), and read enable ( “REN” 125 in FIG. 12 and hereinafter referred to as “REN” 125) and read reset (“RRST” 126 in FIG. 12 and hereinafter referred to as “RRST” 126) are generated.
- FIG. 12 shows the timing relationship of these signals.
- FIG. 12 shows signal waveforms of “SYNC” 121, “CTRL” 122, “WEN” 123, “WRST” 124, “REN” 125, “RRST” 126, “WP” 127, and “RP” 128, respectively. ing.
- the horizontal axis is time.
- “WEN” 123 is always high (corresponding to “High” and “Enable”) because the broadcast wave is continuously received.
- “WRST” 124 is a signal obtained by time-differentiating the rising edge of “CTRL” 122, and becomes High (equivalent to enable) only at the rising edge of “CTRL” 122. At this moment, the write pointer of the FIFO storage unit 90 is Reset.
- the write pointer is “WP” 127 and is hereinafter referred to as “WP” 127.
- “REN” 125 is set to a low (equivalent to Low, disable) period for a time period during which the back-end signal processing unit 32 in the subsequent stage is stopped, and data reading from the FIFO storage unit 90 is periodically prohibited.
- “RRST” 126 is a pulse that becomes High (corresponding to enable) only at the moment when “REN” 125 becomes Low (corresponding to disable) after High (corresponding to disable). This “RRST” 126 resets “RP” 128 (read pointer) of the FIFO storage unit 90. As a result, the read pointer is reset after a desired time from the reset of the write pointer to the FIFO storage unit 90.
- “WP” 127 and “RP” 128 represent changes in the write pointer and the read pointer, respectively. Both have periodicity in the period of “CTRL” 122, but “RP” 128 has a larger rising slope, and the reading speed is set faster because the FIFO reading time is shorter. As a result, data can be read out earlier than at the time of writing, and therefore no data is lost even when intermittent reading is performed.
- the back-end signal processing unit 32 is intermittently operated so as not to operate during the period in which the FIFO reading is stopped in synchronization with the reading cycle, the back-end signal processing is performed during the period in which the back-end signal processing unit 32 is not operating.
- the dive noise signal 16 from the unit 32 to the antenna is not generated. Therefore, the transmission path estimation of the broadcast wave can be performed with high accuracy.
- the wireless reception device 9 performs weighted synthesis of a plurality of antenna reception signals using a weighting coefficient obtained from transmission path estimation and inter-antenna covariance, and a broadcast wave transmission path using the sync pattern “0x47”.
- the back end can be operated during the broadcast stop by the estimation and the means for determining the broadcast stop, and the jumping noise from the back end can be detected.
- continuous broadcast waves that cannot be achieved by the conventional method, in particular, interference waves such as noise waves when receiving MPEG2TS broadcasts can be removed, and reception sensitivity can be improved in a digital reception TV or the like.
- by performing the back-end operation intermittently it is possible to perform broadcast wave transmission channel estimation without the influence of noise, so that transmission channel estimation accuracy can be improved and noise removal performance can be improved.
- the radio reception apparatus in the third embodiment includes a second compensation buffer unit 84b in which means for removing PCR jitter is mounted in the first compensation buffer unit 84a in the radio reception apparatus in the second embodiment of the present invention. ing. Except for the second compensation buffer unit 84b, it is the same as the radio reception apparatus of the second embodiment. Detailed description of the same parts as those of the second embodiment is omitted. Since the operation of the second compensation buffer unit 84b is different from the operation of the first compensation buffer unit 84a in the second embodiment, the operation will be mainly described.
- the second compensation buffer unit 84b is an example of a compensation buffer unit that stores received data and intermittently inputs the stored received data to the back-end signal processing unit.
- FIG. 13 shows a block configuration diagram of the second compensation buffer unit 84b of the third embodiment.
- the second compensation buffer unit 84b includes an input terminal 86 from the back-end operation stop unit 85, an input terminal 87 from the Viterbi decoding unit 100, an output terminal 88 to the back-end signal processing unit 32, a second The control signal generation unit 89b, the FIFO storage unit 90, the PCR extraction unit 101, the PCR offset addition unit 102, and the PCR replacement unit 103 are configured.
- FIG. 14 is a time chart for showing control signals of the back-end operation stop unit 85 and the FIFO storage unit 90 in the second compensation buffer unit 84b, PCR detection pulses from the PCR extraction unit 101, and the like. Specifically, FIG. 14 shows “SYNC” 141, “CTRL” 142, “WEN” 143, “WRST” 144, “REN” 145, “RRST” 146, “WP” 147, “RP” 148, “ Each signal waveform of “PCR” 149 is shown. The horizontal axis is time.
- the back-end operation stop unit 85 intermittently thins out the “SYNC” 141 pulse of FIG. 14 that is the output signal of the sync pattern detection unit 31 to generate the “CTRL” 142 having a long cycle. Then, the back-end operation stop unit 85 also inputs “SYNC” 141 and “CTRL” 142 to the back-end signal processing unit 32 and the second compensation buffer unit 84 b.
- the second control signal generation unit 89 b represents a packet including “SYNC” 141 and “CTRL” 142 input from the input terminal 86 and PCR (clock information and the like) detected by the PCR extraction unit 101. Based on the pulse of “PCR” 149, “WEN” 143, “WRST” 144, “REN” 145, and “RRST” 146 which are control signals of the FIFO storage unit 90 are generated.
- FIG. 14 shows the relationship between these signals.
- “WEN” 143 is always “High” (corresponding to “enable”) because broadcast waves continuously come.
- “WRST” 144 is a signal obtained by time-differentiating the rising edge of “CTRL” 142, and becomes High (corresponding to “enable”) only at the rising edge of “CTRL” 142.
- “WP” (write pointer) of the FIFO storage unit 90 is set.
- REN” 145 is a Low (corresponding to disable) period during which the back-end signal processing unit 32 in the subsequent stage is stopped, and reading of data from the FIFO storage unit 90 is periodically prohibited.
- the “RRST” 146 resets the “RP” (read pointer) 148 of the FIFO storage unit 90 with a pulse that becomes High (corresponding to Enable) at least during the Low (corresponding to disable) period of the “REN” 145.
- the read pointer is reset after a desired time from the reset of the write pointer to the FIFO storage unit 90.
- “WP” 147 and “RP” 148 represent changes in the write pointer and the read pointer, respectively. Both have periodicity with a period of “CTRL” 142. However, “RP” 148 has a larger upward gradient, and the read speed is set faster in accordance with the decrease in the FIFO read time. Thereby, data can be read from the FIFO storage unit 90 in a time earlier than the time of writing. Therefore, no data is lost even when periodic reading is performed, but the longer the “REN” 145 is in the Low (corresponding to disable) period, the longer the delay jitter of the packet passed to the back end.
- a packet including PCR which is reference data for generating a system clock
- a packet including PCR has a problem that correct system clock generation cannot be performed when delay jitter increases.
- a packet including PCR is detected, and the PCR value is corrected by the delay time.
- the data input from the input terminal 87 is input to the FIFO storage unit 90 and simultaneously to the PCR extraction unit 101.
- the PCR extraction unit 101 detects a packet including PCR and outputs a PCR detection pulse. To do.
- This PCR detection pulse is “PCR” 149 in FIG. 14, and the PCR detection pulse is hereinafter referred to as “PCR” 149.
- the PCR extraction unit 101 passes “PCR” 149 to the second control signal generation unit 89b.
- the second control signal generation unit 89 Upon receiving “PCR” 149, the second control signal generation unit 89 returns the time td shown in FIG. 14 to the PCR offset addition unit 102. This time td is the time from when a packet including PCR is written to the FIFO storage unit 90 until it is read.
- the PCR offset addition unit 102 corrects the PCR value by adding an offset to the PCR value for a time td, and inputs the corrected PCR value to the PCR replacement unit 103.
- the PCR replacement unit 103 outputs the output to the output terminal 88 after replacing the original PCR with the PCR supplied from the PCR offset addition unit 102. By this operation, a PCR having a correct clock reference can be transmitted.
- the PCR replacement unit 103 corrects the clock information included in the received data stored in the FIFO storage unit 90 as a storage unit with the clock information detected by the PCR extraction unit 101.
- the system clock can be generated correctly even when the delay jitter increases in the FIFO storage unit 90 for guaranteeing the back-end stop processing. Even if it is necessary to delay the data for a long time in the FIFO storage unit 90 and to stop the back-end signal processing unit 32 for a long time for accurate transmission path estimation, the back-end signal processing unit 32 is normally operated with the correct system clock. It is possible to operate. Then, means for weighting and combining received signals from a plurality of antennas using a weighting coefficient obtained from transmission path estimation and inter-antenna covariance, and broadcast wave transmission path estimation and broadcast stoppage using a sync pattern “0x47”.
- the judging means can operate the back end during the broadcast stop and detect the jumping noise from the back end. In this way, continuous broadcast waves that cannot be achieved by the conventional method, in particular, interference waves such as noise waves at the time of MPEG2TS broadcast reception can be removed, and reception sensitivity can be improved in a digital reception TV or the like. Further, by performing the operation of the back-end signal processing unit 32 intermittently, it is possible to estimate the transmission path of the broadcast wave without the influence of noise, so that the transmission path estimation accuracy is improved and the noise removal performance can be improved. .
- the radio receiving apparatus according to the fourth embodiment is different from the third embodiment in the means for compensating for the PCR jitter in the first compensation buffer unit 84a in the radio receiving apparatus according to the second embodiment of the present invention. It is an implementation. Except for the third compensation buffer unit 84c, it is the same as the radio reception apparatus of the third embodiment. Detailed description of the same parts as those in the third embodiment will be omitted. Since the operation of the third compensation buffer unit 84c is different from that of the second compensation buffer unit 84b in the embodiment, the operation will be mainly described.
- the third compensation buffer unit 84c is an example of a compensation buffer unit that stores received data and intermittently inputs the stored received data to the back-end signal processing unit.
- FIG. 15 is a block diagram of the third compensation buffer unit 84c of the fourth embodiment.
- the third compensation buffer unit 84c includes an input terminal 86 from the back end operation stop unit 85, an input terminal 87 from the Viterbi decoding unit 100, an output terminal 88 to the back end signal processing unit 32 in FIG.
- a third control signal generation unit 89c, a FIFO storage unit 90, a PCR extraction unit 101, and a switching unit 104 are included.
- FIG. 16 is a time chart showing a control signal of the FIFO memory in the back-end operation stop unit 85 and the third compensation buffer unit 84c, a PCR detection signal from the PCR extraction unit 101, and the like.
- the back-end operation stop unit 85 intermittently thins out the pulses of “SYNC” 161 in FIG. 16 that is the output signal of the sync pattern detection unit 31 to generate “CTRL” 162 having a long cycle, and generates “SYNC” 161 and “ The “CTRL” 162 is also input to the back-end signal processing unit 32 and the third compensation buffer unit 84 c.
- the third control signal generation unit 89 c displays “SYNC” 161 and “CTRL” 162 input from the input terminal 86 and “PCR” 169 representing a packet including the PCR detected by the PCR extraction unit 101. Based on this, control signals “WEN” 163, “WRST” 164, “REN” 165, and “RRST” 166 of the FIFO storage unit 90 are generated. FIG. 16 shows the relationship between these signals. Since “WEN” 163 does not store data including PCR in the FIFO storage unit 90, when “PCR” 169 indicating that PCR is detected is input, it becomes Low for a certain time (corresponding to disable), Writing to the FIFO storage unit 90 is prohibited.
- “WRST” 164 is a signal obtained by time-differentiating the rising edge of “CTRL” 162, and becomes “High” (equivalent to enable) only at the rising edge of “CTRL” 162.
- “WP” of FIFO storage unit 90 is “WP”. (Write pointer) 167 is reset.
- “REN” 165 is set to a Low (corresponding to disable) period for a time period during which the back-end signal processing unit 32 in the subsequent stage is stopped, and periodically prohibits reading of data from the FIFO storage unit 90.
- “WP” 167 and “RP” 168 represent changes in the write pointer and the read pointer, respectively. Both of them have periodicity in the period of “CTRL” 162, but “RP” 168 has a larger inclination of increase, and the reading speed is set faster according to the period of FIFO reading. As a result, data can be read out earlier than at the time of writing, so that no data is lost even if periodic reading is performed. However, the longer the Low (corresponding to disable) period of “REN” 165, the longer the delay jitter of the packet passed to the back-end signal processing unit 32.
- a packet including PCR which is reference data for generating a system clock
- a packet including PCR which is reference data for generating a system clock
- the fourth embodiment when a packet including PCR is detected, only the PCR is output from the third compensation buffer unit 84c in real time, so that it is output without being stored in the FIFO storage unit 90.
- the data input from the input terminal 87 is input to the FIFO storage unit 90 and simultaneously to the PCR extraction unit 101.
- the PCR extraction unit 101 detects a packet including the PCR and outputs the PCR detection pulse. 3 to the control signal generator 89c.
- the PCR detection pulse corresponds to “PCR” 169 in FIG.
- the third control signal generation unit 89c immediately sets “WEN” 163 and “REN” 165 to Low (corresponding to disable), and stops writing and reading of the PCR packet into the FIFO. .
- a period tw in FIG. 16 is a period in which writing is not performed.
- the switching unit 104 is operated, and the PCR output from the PCR extraction unit 101 is output to the output terminal 88. Thereby, a PCR having a correct clock reference can be transmitted.
- the system clock can be correctly generated even when the delay jitter increases in the FIFO storage unit 90 for guaranteeing the back-end stop process. Even if it is necessary to delay the data for a long time in the FIFO storage unit 90 and to stop the back-end signal processing unit 32 for a long time for accurate transmission path estimation, the back-end signal processing unit 32 is normally operated with the correct system clock. It is possible to operate.
- means for weighted synthesis of received signals from multiple antennas using weighting coefficients obtained from transmission path estimation and inter-antenna covariance, broadcast wave transmission path estimation using sync pattern “0x47”, and determination of broadcast stoppage By this means, the back end can be operated while the broadcast is stopped, and the jumping noise from the back end can be detected. In this way, continuous broadcast waves that cannot be achieved by the conventional method, in particular, interference waves such as noise waves when receiving MPEG2TS broadcasts can be removed, and reception sensitivity can be improved in a digital reception TV or the like. Further, by performing the back-end operation intermittently, it is possible to perform broadcast wave transmission channel estimation without the influence of noise, so that transmission channel estimation accuracy can be improved and noise removal performance can be improved.
- the wireless receivers described in the first, second, third, and fourth embodiments can be applied to the same technique other than MPEG2TS broadcast, and the application of the present invention is not limited to MPEG2TS broadcast.
- the wireless receiver is described.
- signal processing after reception by the receiving antenna can be realized by software processing (program) implemented on a microcomputer or an integrated circuit.
- the radio reception apparatus of the present invention can provide a radio reception apparatus in which the transmission path estimation of the received transmission wave is detected by detecting the interference wave signal and the reception sensitivity deterioration due to noise is reduced. is there.
- the wireless receiver of the present invention can perform the transmission channel estimation of the broadcast wave without the influence of noise by intermittently performing the operation of the back-end signal processing unit, the transmission channel estimation accuracy is improved and noise removal is performed. The performance can be improved.
- the wireless reception apparatus of the present invention can transmit a PCR having a clock reference with consistency when the received data is data having time information such as MPEG. Therefore, even if the operation of the back-end signal processing unit is intermittently performed and the data is held in the compensation buffer means, a relatively reliable system clock can be generated. Therefore, even if it is necessary to hold (delay) data for a long time in the compensation buffer means for accurate transmission path estimation and to stop the back end for a long time, the back end operates normally with a system clock that maintains consistency. It is possible to make it.
- the wireless receiver of the present invention can transmit a PCR having a correct clock reference. Therefore, even if the operation of the back-end signal processing unit is intermittently performed, it is possible to supply a system clock that maintains consistency even if data is held in the compensation buffer means.
- the wireless reception device of the present invention can detect a pattern by using data constituting the MPEG.
- the wireless reception device of the present invention is capable of canceling noise with respect to noise generated from a decoding processing portion or the like in a wireless receiving device having a decoding processing portion (MPEG decoder or the like) of MPEG data in the wireless receiving device.
- MPEG decoder MPEG decoder
- the wireless receiver of the present invention even if the desired wave that could not be performed conventionally is a continuous wave such as a digital broadcast wave, the transmission path is estimated and the interference wave signal is detected, and the reception sensitivity is deteriorated due to noise. Can be realized.
- the radio reception apparatus can be used in a radio transmission reception system that uses MPEG2TS as a system layer based on transmission path estimation using a sync byte pattern unique to MPEG2TS rather than a packet preamble. Further, by combining the stop of the operation of the signal processing unit, which is a noise source, and buffer compensation, it can be applied to many circuit configurations that generate device noise. The radio reception apparatus according to the present invention can be applied to all applications that effectively remove noise generated inside the apparatus and improve reception sensitivity.
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Abstract
Description
図1は、実施の形態1における放送局と伝送路と無線受信装置を表す構成図である。図1において、放送局1はマルチキャリアOFDM変調されたデジタル放送波を送信する。放送局1からの放送波2は、フェージング伝送路3を介して空間伝送される。フェージング伝送路3は放送波2が反射や減衰を伴う伝達特性を持った伝送路である。無線受信装置9は、受信アンテナ4と受信アンテナ5とフロントエンド部6とバックエンド部7で構成されている。ここで、フロントエンド部6とは、無線受信に係わる処理を主として行う部分である。バックエンド部7とは、無線処理に係わらない処理を主として行う部分である。例えば、バックエンド部7は圧縮画像をデコードするデジタルLSI群8で構成されている。デジタルLSI群8は動作時にデジタル動作に伴うノイズ信号16を発するため、フロントエンド部6の前段にある受信アンテナ4と受信アンテナ5にノイズ信号16が飛び込むと受信品質が劣化することになる。このような無線受信装置9の内部もしくは近傍から受信アンテナ4、5に飛び込む不要なノイズ信号16をキャンセルし受信品質を向上させる構成について図面を用いて詳細を説明する。なお、上述のマルチキャリアOFDM変調されたデジタル放送波は、マルチキャリア送信波の一例である。以降の本発明の説明では、マルチキャリア送信波としてマルチキャリアOFDM変調されたデジタル放送波を例に挙げて説明する。
次に、本発明の実施の形態2における無線受信装置について説明する。図10は、本発明の実施の形態2における無線受信装置のブロック構成図である。図10に示す本発明の実施の形態2における無線受信装置のブロック構成図と図3に示す本発明の実施の形態1における無線受信装置のブロック構成図との相違点は、第1の補償バッファ部84aとバックエンド動作停止部85である。その他は同一であり、実施の形態1と同一の構成要素については同じ符号を用い、それらの詳細な説明は一部省略する。図10において、第1の補償バッファ部84aとバックエンド動作停止部85は実施の形態1の無線受信装置に追加されて、ノイズ除去性能を更に向上させる。なお、第1の補償バッファ部84aは、受信データを記憶し、記憶した受信データをバックエンド信号処理部に間欠的に入力する補償バッファ部の一例である。
次に、本発明の実施の形態3について説明する。実施の形態3における無線受信装置は、本発明の実施の形態2の無線受信装置における第1の補償バッファ部84a内にPCRジッターの除去を行う手段を実装した第2の補償バッファ部84bを備えている。第2の補償バッファ部84b以外は実施の形態2の無線受信装置と同様である。実施の形態2同じの部分は詳しい説明は省略する。第2の補償バッファ部84bの動作が実施の形態2での第1の補償バッファ部84aの動作とは異なるため、その動作を中心に説明する。なお、第2の補償バッファ部84bは、受信データを記憶し、記憶した受信データをバックエンド信号処理部に間欠的に入力する補償バッファ部の一例である。
次に、本発明の実施の形態4について説明する。実施の形態4における無線受信装置は、本発明の実施の形態2での無線受信装置における第1の補償バッファ部84a内に、PCRジッターの補償を行う手段を実施の形態3とは異なる手段で実装をしたものである。第3の補償バッファ部84c以外は実施の形態3の無線受信装置と同様である。実施の形態3同じの部分は詳しい説明は省略する。第3の補償バッファ部84cの動作が実施の形態での第2の補償バッファ部84bとは異なるため、その動作を中心に説明する。なお、第3の補償バッファ部84cは、受信データを記憶し、記憶した受信データをバックエンド信号処理部に間欠的に入力する補償バッファ部の一例である。
16 ノイズ信号
26,27 FFT部
28 ノイズ波除去部
29 デマッピング部
30 放送停波検出部
31 シンクパターン検出部
32 バックエンド信号処理部
33 バックエンド動作制御部
40 重み付け合成部
41 伝送路推定部
42 不要信号測定部
43 信頼度評価部
48 伝送路係数算出部
49 伝送路係数記憶部
52 アンテナ間共分散算出部
53 記憶部
59 合成部
60 重み付け係数算出部
65 第1のローノイズアンプ
66 第2のローノイズアンプ
67a 第1の検波部
67b 第3の検波部
68a 第2の検波部
68b 第4の検波部
69 加算部
70 閾値判定部
71 判定部
72 パターン検出部
73 パターン発生部
78,79 波形検出部
80,81,82 周期性検出部
83 補間部
84a 第1の補償バッファ部
84b 第2の補償バッファ部
84c 第3の補償バッファ部
85 バックエンド動作停止部
89 制御信号生成部
90 FIFO記憶部
100 ビタビ復号部
101 PCR抽出部
102 PCRオフセット加算部
103 PCR挿げ替え部
104 切り替え部
Claims (7)
- マルチキャリア送信波を受信する複数の受信アンテナと、
前記受信アンテナの個々に個別に接続され、前記受信アンテナで受信した信号を周波数空間信号に変換する複数の周波数空間変換部と、
前記周波数空間変換部の個々に個別に接続され、前記複数の周波数空間変換部で変換された周波数空間信号に対して少なくとも
前記マルチキャリア送信波の伝送路係数行列の算出と、
前記複数の受信アンテナ間のアンテナ間共分散行列の算出と
を行う複数のノイズ波除去部と、
前記ノイズ波除去部の出力に関連した信号に対してバックエンド処理を行うバックエンド信号処理部と、
前記受信アンテナで受信したマルチキャリア送信波から特定のデータを検出するパターン検出部と、
前記マルチキャリア送信波の停止状況を判断する放送停波検出部と、
前記放送停波検出部がマルチキャリア送信波の停止を検出した際に、前記バックエンド信号処理部の動作を実行させるバックエンド動作制御部と、
を備え、
前記複数のノイズ波除去部は、前記放送停波検出部が前記マルチキャリア放送波の停止を検出した際に前記アンテナ間共分散行列の算出を実行する
無線受信装置。 - 前記複数のノイズ波除去部は、
前記受信アンテナの出力を重み付け合成する重み付け合成部と、
前記周波数空間信号を入力して、検出された前記特定のデータに基づいて前記マルチキャリア送信波の前記伝送路係数行列を算出する伝送路推定部と、
前記アンテナ間共分散行列を算出する不要信号測定部と、
を備える請求項1に記載の無線受信装置。 - 前記バックエンド信号処理部の処理を停止させるバックエンド動作停止部と、
受信データを記憶し、記憶した前記受信データを前記バックエンド信号処理部に間欠的に入力する補償バッファ部
を更に備え、
前記バックエンド動作停止部が前記バックエンド信号処理部の処理を停止させる停止期間中に、前記伝送路推定部は前記伝送路係数行列を算出し、
前記補償バッファ部は、前記停止期間中の前記受信データを保持する
請求項1に記載の無線受信装置。 - 前記補償バッファ部は、
前記受信データに含まれるクロック情報を検出するPCR抽出部と、
前記PCR抽出部が検出したクロック情報をオフセット加算するPCRオフセット加算部と、
前記受信データを記憶する記憶部と、
前記記憶部に記憶された受信データに含まれるクロック情報を前記検出部が検出したクロック情報で補正するPCR挿げ替え部
を備えた請求項3に記載の無線受信装置。 - 前記補償バッファ部は、
前記受信データを記憶する記憶部と、
受信データに含まれるクロック情報を検出するPCR抽出部と、
前記記憶部に記憶された受信データに含まれるクロック情報を前記検出部が検出したクロック情報に切り替える切り替え部と
を備えた請求項3に記載の無線受信装置。 - 前記パターン検出部は、MPEG規格の同期符号、もしくは、MPEG規格のスタートコードを検出する請求項1から5のいずれか1項に記載の無線受信装置。
- 前記バックエンド信号処理部は、少なくともMPEGデータの復号処理を含む処理を実行する請求項1から6のいずれか1項に記載の無線受信装置。
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JP2010523752A JP5370366B2 (ja) | 2008-08-06 | 2009-08-04 | 無線受信装置 |
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US8290101B2 (en) | 2012-10-16 |
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