EP1061779B1 - Verfahren zum Betreiben mindestens einer Leuchtstofflampe sowie elektronisches Vorschaltgerät dafür - Google Patents

Verfahren zum Betreiben mindestens einer Leuchtstofflampe sowie elektronisches Vorschaltgerät dafür Download PDF

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Publication number
EP1061779B1
EP1061779B1 EP00104995A EP00104995A EP1061779B1 EP 1061779 B1 EP1061779 B1 EP 1061779B1 EP 00104995 A EP00104995 A EP 00104995A EP 00104995 A EP00104995 A EP 00104995A EP 1061779 B1 EP1061779 B1 EP 1061779B1
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EP
European Patent Office
Prior art keywords
circuit
control
load current
δit
load
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP00104995A
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German (de)
English (en)
French (fr)
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EP1061779A2 (de
EP1061779A3 (de
Inventor
Peter Krummel
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Osram GmbH
Original Assignee
Patent Treuhand Gesellschaft fuer Elektrische Gluehlampen mbH
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Publication of EP1061779A3 publication Critical patent/EP1061779A3/de
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Publication of EP1061779B1 publication Critical patent/EP1061779B1/de
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
    • H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions

Definitions

  • the invention relates to a method for operating at least one fluorescent lamp with the aid of an electronic ballast according to the preamble of claim 1 and to a correspondingly designed electronic ballast itself according to the preamble of claim 5.
  • EP-B-0 801 881 such a method for operating at least one fluorescent lamp by means of an electronic ballast is known, which has a coupled to a rectifier circuit half-bridge circuit with two series-connected, alternatively activated power transistors. At the common connection point of these power transistors, which forms the output of the half-bridge arrangement, a load circuit is connected, which contains the at least one fluorescent lamp and the load current is monitored.
  • a control and regulating circuit is provided in the form of an integrated circuit. This is equipped with a monitoring circuit for continuously monitoring the load current and with a derived high-frequency controlled drive circuit for the power transistors.
  • a timer is started defined at each lamp start and each occurring during combustion operation, which generates a time base for subsequent control and regulation operations. Due to this time base, predetermined, different reference levels for the load current to be detected are respectively set in the monitoring circuit, or an automatic switch-off of the electronic ballast is prepared for a predetermined, limited period of time.
  • the monitoring circuit compares the instantaneous value of the load current with the respectively activated reference level and outputs an output pulse when this reference level is reached. These output pulses indicate depending their occurrence or failure during predetermined, defined by the timer periods normal or faulty conditions in the load circuit. With these output pulses, the lamp current is regulated in a time-dependent manner in the undisturbed operating state via the controlled drive circuit or, in the event of a fault, an already prepared automatic switch-off of the electronic ballast is triggered.
  • Fully electronic ballasts of the type mentioned are advantageously applicable universal devices for common AC mains voltages in a relatively wide tolerance range, a wide range of permissible network frequencies and are finally even suitable for DC power supply.
  • One of the main problems in the application of electronic ballasts is that different types of lamps in part also varying circuits, eg. B. also several fluorescent lamps are used, which requires a corresponding variety of types of these applications specifically adapted ballasts. It is therefore not easy to comply with this type of variety with as possible a single highly integrated circuit in which the drive and control circuit of the ballast is summarized.
  • As a compromise with partial waiver of a desired high degree of integration corresponding control inputs of the integrated circuit are adapted by externally connected components.
  • the ignition voltage can not be freely adjusted in height, as this is determined by a fixed, internally defined in the integrated circuit threshold.
  • the required for different applications adaptation within a given range of tolerance permissible ignition and / or preheating is to be achieved in the known electronic ballast at best by appropriate external circuitry of the integrated circuit and therefore only with a corresponding effort.
  • the present invention is therefore a subtask, in a further development of the above-mentioned method for operating at least one fluorescent lamp to specify a further embodiment, in addition to a reliable control of the load current even with aged fluorescent lamps in particular the possibility is opened to control such applications safely in which lamp types with critical ignition behavior are to be used.
  • the electronic ballast of the above-appreciated type such that it despite a corresponding degree of integration of its drive and control circuit and thus reduced effort for the external circuitry only by simple adaptation to a large extent reliable in a variety of applications can be used.
  • a subtask is achieved with the features described in the characterizing part of claim 1. Accordingly, the other subtask is solved in an electronic ballast of the type mentioned above with the features described in the characterizing part of claim 5.
  • the solutions according to the invention make it possible, with a simple measure, to extend the tolerance range of the electronic ballast with respect to the monitoring of the load current.
  • This property is particularly advantageous when the load circuit comprises a lamp circuit with a plurality of fluorescent lamps.
  • the load circuit comprises a lamp circuit with a plurality of fluorescent lamps.
  • the integrated circuit tolerance ranges can not be readily given wide enough, because then possibly critical operating conditions such.
  • B. the Zündunwillmaschine of or misfire in aged fluorescent lamps are no longer detected properly.
  • Another way to use the electronic ballast with a given integrated To equip control and regulating circuit and yet operate such critical lamp circuits so that would be, with effort to adapt the external circuitry of the integrated circuit to the particular application.
  • today electronic ballasts are products that have to be manufactured largely automated at high cost pressure, such a solution is uneconomical.
  • this problem is solved elegantly with a relatively simple circuit measure.
  • the load current signal to be monitored in the control and regulating circuit is superimposed with a direct current signal from an additional direct current source whose level can be set as a function of the respectively used lamp circuit. Since the preheating voltage, but in particular the ignition voltage in these difficult to handle applications are critical, it is sufficient to provide this overlay only for the beginning of the preheating of the ignition period.
  • the level adjustment of the additional DC power source by simple means and safely be achieved in that the level to be adjusted is derived internally from the current flow through the matching resistor, which is assigned as an external resistor to the current-dependent controlled oscillator and by dimensioning the blanking interval Half-bridge circuit is fixed.
  • a circuit adaptation to different lamp circuits in the load circuit is thus carried out by the appropriate dimensioning of a single ohmic resistance.
  • a further threshold is provided in the monitoring circuit, whose level is between those for the preheating threshold and the ignition threshold.
  • FIG. 1 shows an electronic ballast for operating at least one fluorescent lamp and the actual load circuit, here by way of example with only one fluorescent lamp.
  • the electronic ballast shown builds on an electronic ballast, which is already known in its basic structure and a plurality of circuit details from the aforementioned document EP-B-0801 881, to which reference can be made here.
  • Known circuit parts and their function, which are of minor importance in connection with the present invention are therefore described below only in summary and for reasons of completeness.
  • a rectifier bridge 2 and a boost converter 3 is connected, which has a charging inductor L1, a charging diode D1, a first power transistor V1 and a storage capacitor Co as the output stage.
  • the power transistor V1 is driven via a control and regulating circuit IC designed as an integrated circuit.
  • the boost converter 3 provides at its output a compared to rectified mains voltage
  • an inverter with a half-bridge circuit is provided, which is realized here in particular by two further, in series parallel to the output of the boost converter 3 other power transistors V2 and V3 and a bridge capacitor CB.
  • a load circuit 4 shown here with a further inductor L2, a fluorescent lamp FL and a firing capacitor Cz, connected.
  • control and regulating circuit IC All essential control and regulating functions of the electronic ballast are realized in the control and regulating circuit IC.
  • the control and regulating circuit IC in FIG. 1 is merely a module with external connections P1 to P24, to which external components are connected and, in addition, shown in detail in FIG. 2 in the form of a block diagram.
  • a power supply unit IPG is therefore shown schematically, which ensures proper starting of the functions of the control and regulating circuit IC and is controlled by the charge state of an externally connected charging capacitor Ccc.
  • the power supply of the control and regulating circuit IC is given via a connected to the bridge capacitor CB pump diode DB with another external charging capacitor Cp by a two-point controller TPR.
  • the power supply unit IPG generates an internal auxiliary voltage IC-BIAS for supplying the internal circuit units of the control and regulating circuit IC and also supplies a reference voltage Vref.
  • the control and regulating circuit IC it should only be noted, an arrangement PFC for controlling the power factor.
  • a drive circuit for the half-bridge circuit V2, V3 consists of a selection circuit SEL and driver circuits connected thereto HSD or LSD.
  • a high-frequency pulse sequence is supplied to a control input of the selection circuit SEL, the power transistors V2 and V3 of the half-bridge circuit switches via the driver circuits HSD and LSD alternatively in the manner of a flip-flop with a defined blanking interval.
  • This controlling pulse train provides a current dependent controlled oscillator CCO with three setting inputs which coincide with the external terminals P23, P24 and P3.
  • a first adjustment resistor RTL is connected, the dimensioning particular determines the blanking interval of the power transistors V2 and V3 of the half-bridge circuit.
  • a tuning capacitor Cf is connected to the terminal P23.
  • said external elements or the filter network are connected to ground or to a defined reference voltage (in the further description, this is always referred to as an example of ground).
  • the dimensioning of these external components determines the lower or upper limit frequency of the current-dependent controlled oscillator CCO and the size of said blanking interval.
  • a control signal is supplied to the current-dependent controlled oscillator CCO, which determines its instantaneous frequency.
  • This control signal is generated by a control operation amplifier OPR. This compares the internally generated reference voltage Vref with a second input voltage supplied via the external terminal P5, which corresponds to the mean value of the current flowing through the half-bridge circuit V2, V3.
  • the described oscillator circuit represents a closed loop for controlling the load current flowing in the half-bridge circuit. Increasing load current increases the output voltage of the control operation amplifier OPR, which in turn controls the oscillator CCO in the direction of a higher pulse repetition frequency. However, this frequency increase causes in turn a reduction of the load current. The same applies to the reverse direction with decreasing tendency of Load current.
  • the electronic ballast is also dimmable by a corresponding determination of the reference voltage Vref.
  • a monitoring function is implemented in the control and regulating circuit IC in order to control the lamp start, to monitor the state of the fluorescent lamp FL in steady-state operation and to recognize any disturbances which occur.
  • a monitoring circuit MON which continuously monitors the load current, d. H. monitored by the current flowing through the half-bridge circuit V2, V3, and on the other hand, a timer PST provided, which provides a time base for this monitoring process.
  • a first internal current source IT is connected via the external terminal P6 to a grounded further charging capacitor CT. It is activated when starting the electronic ballast and charges the external charging capacitor CT. In the process, a signal voltage rising linearly up to a final value is formed at the external connection P6, which signal signal is supplied to the control input of the timer PST and supplies the time base for this. For this purpose, this signal voltage is compared in the timer PST with predetermined threshold values.
  • the timer PST Upon reaching the respective threshold value, the timer PST each outputs a selection signal S1, S2, S3 or S4 and defines with their time sequence certain time periods for preheating, igniting, subsequent normal operation of the fluorescent lamp FL or for resetting its control in the event of errors, in particular in case of dropouts or permanent ignitability.
  • the meaning of the selection signals S1 to S4 generated by the timer PST is explained in connection with the function of the monitoring circuit MON.
  • the monitoring circuit MON has a signal input which is connected via the external terminal P7 and a series resistor to the low-level output of the half-bridge circuit V2, V3.
  • the input to the monitoring circuit MON about this input signal is thus a current flowing through the power transistor V3 current, ie also the load current proportional pulsed signal.
  • This signal is called DC bias the output signal superimposed on a further internal current source IM, which is temporarily activated by the selection signal S3 of the timer PST.
  • the level of the bias signal DC generated by this second internal current source IM is derived from the current flow through the variable resistor RTL of the current dependent controlled oscillator CCO.
  • IC internally via current mirror, a portion of the current flowing through the adjusting resistor RTL current of the other internal power source IM is supplied.
  • an adaptation of the monitoring function of the monitoring circuit MON to variants of the design of the load circuit 4, in particular specific lamp types or lamp circuits, can thus be achieved without an internal adaptation or additional external connections of the control and regulating circuit IC.
  • the control and regulating circuit IC is thus used without internal adjustments for a wide range of circuit alternatives of the load circuit 4, in particular, tolerances for the ignition current for certain types of lamps are better absorbed.
  • one of several predetermined threshold values for the load current to be monitored is activated in the monitoring circuit MON at specific periods at a lamp start and also during normal firing operation. As soon as the level of the input signal of the monitoring circuit MON reaches the currently activated threshold, it outputs an output pulse QM. Over time, this results in a sequence of short-term output pulses QM, with each of which control operations in other units of the control and regulating circuit IC are triggered.
  • a third internal current source ISC is provided, the output of which via the external Terminal P1 is connected to the already explained external low-pass filter.
  • the third internal current source ISC is set in the manner of a flip-flop by the output pulses QM of the monitoring circuit MON and reset by the selection circuit SEL.
  • the third internal current source ISC charges the external capacitor Cc of the low-pass filter. The charging of the external charging capacitor Cc proportionally, the current supplied to the controlled oscillator CCO at its control input via the external terminal P3 supplied input current If changes.
  • the function of the monitoring circuit MON is most clearly illustrated by the sequence control at a lamp start. If the electronic ballast is connected to the grid, as described, the control and regulating circuit IC is activated as soon as the switch-on threshold is reached. The current-dependent controlled oscillator CCO then starts with a predetermined lower limit frequency and thus controls the selection circuit SEL, which sets the half-bridge circuit V2, V3 via the driver circuits HSD and LSD. The first internal power source IT starts to charge the external charging capacitor CT and puts the timer PST into operation. The lamp starts with a pre-heating period ⁇ pt. In the monitoring circuit MON, a corresponding, relatively low threshold value Mp for the preheating current is activated.
  • the monitoring circuit MON outputs an output pulse QM each time this threshold value Mp is reached by a pulse of the load current. With these, in each case the selection circuit SEL is triggered and the third internal current source ISC is activated. Thus, the above-described in connection with the function of this power source ISC parent, ie second control circuit for the current control is set in motion. During this preheat period ⁇ pt, the output of a signal amplifier QPT is turned off. This Output can be used, for example, to control a preheat circuit or to set a DC bias on the control input of the monitoring circuit MON for free preheat voltage adjustment.
  • the linearly rising input voltage of the timer PST reaches a predetermined preheating level.
  • the preheat period ⁇ pt is completed and the timer PST generates the first selection signal S1, which is output to the monitoring circuit MON and the signal amplifier QPT.
  • the monitoring circuit MON so that a higher threshold value Mi for the ignition current of the fluorescent lamp FL is activated, an ignition period ⁇ it begins.
  • the timer PST generates another, the fourth selection signal S4, whose trailing edge coincides with the reaching of a maximum level of the input voltage of the timer PST.
  • the second internal current source IM is activated and further enabled a flip-flop-controlled switch OPRD.
  • the monitoring circuit MON monitors the input signal proportional to the load current supplied to this threshold and, dependent thereon, supplies the further output pulses QM1.
  • said switch OPRd is initially set and reset by the output signal of the selection circuit SEL, respectively.
  • ground potential is applied to the non-inverting input of the control operation amplifier OPR connected to the external terminal P5.
  • the fluorescent lamp FL fires within a predetermined time after only a few ignition attempts. Automatically then goes the peak value of the load current returns to a normal operating value and no longer reaches the threshold value Mi of the monitoring circuit MON, no further output pulses QM are generated.
  • the timer PST continues to run. Its increasing input voltage initially goes through a predetermined ignition level and finally reaches a maximum level, which initiates a reset of the timer PST. Upon reaching this maximum level, the timer generates the output signal S3, which activates a threshold Mo in the monitoring circuit MON, which is not reached by the rated load current during normal firing operation of the fluorescent lamp FL, so that no further output pulses QM are generated by it.
  • the third selection signal S3 the time allocated to the timer PST second internal power source IT is turned off.
  • the charging capacitor CT connected thereto begins to discharge, i. H. the input signal supplied to the timer PST drops to a constant level which is kept in the normal burning mode.
  • the timer PST generates another, the second selection signal S2. This is held until the input of the timer PST when falling back through the ignition level.
  • This pulse duration of the second selection signal S2 defines a switch-off period .DELTA.st following the ignition period .DELTA.it, in which the shutdown of the electronic ballast is prepared in the event of an error.
  • a shutdown unit with a counter CTR and a shutdown SDL is provided.
  • the counter CTR is reset by both the rising and the falling edge of the second selection signal S2.
  • the output pulses QM are supplied to the monitoring circuit MON as counting pulses. During normal startup, it reaches its final value after four counts, for example, and then activates the internal power source IT. In the further course, the leading edge of the second selection signal S2 resets the counter CTR and prepares the shutdown circuit SDL for preparatory release. Now count the number of futile attempts at ignition or the number of output pulses QM that occur now. If the counter CTR reaches its final value at a Ignoring the lamp, it activates the previously disconnected shutdown circuit SDL.
  • control and regulating circuit IC is finally also designed to adapt to changes in the load current in a relatively wide tolerance range. Such changes can especially in dimming in multi-lamp applications or even with critical lamp tolerances, eg. B. caused by aged, high-resistance lamp filaments occur. These cases can lead to the fact that the operation OPR operational amplifier no longer works within its defined control range.
  • This state is detected by a further comparator COMP which is connected with its non-inverting input to the external terminal P1 and whose inverting input is supplied with an internally generated comparison voltage Vcc ', which is clearly visible in relation to the voltage at the charging capacitor Ccc occurring in the normal operating state. for example, reduced by 25%.
  • the comparator COMP When such an operating state occurs, the comparator COMP outputs to the monitoring circuit MON a control signal with which a state is set there in which all reference levels Mp, Mi, Mdo and Mo are markedly lowered.
  • the monitoring circuit MON then works properly even at lower lamp currents.

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  • Circuit Arrangements For Discharge Lamps (AREA)
EP00104995A 1999-06-18 2000-03-09 Verfahren zum Betreiben mindestens einer Leuchtstofflampe sowie elektronisches Vorschaltgerät dafür Expired - Lifetime EP1061779B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE19928042A DE19928042A1 (de) 1999-06-18 1999-06-18 Verfahren zum Betreiben mindestens einer Leuchtstofflampe sowie elektronisches Vorschaltgerät dafür
DE19928042 1999-06-18

Publications (3)

Publication Number Publication Date
EP1061779A2 EP1061779A2 (de) 2000-12-20
EP1061779A3 EP1061779A3 (de) 2004-11-03
EP1061779B1 true EP1061779B1 (de) 2006-05-24

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EP00104995A Expired - Lifetime EP1061779B1 (de) 1999-06-18 2000-03-09 Verfahren zum Betreiben mindestens einer Leuchtstofflampe sowie elektronisches Vorschaltgerät dafür

Country Status (7)

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US (1) US6310447B1 (zh)
EP (1) EP1061779B1 (zh)
JP (1) JP4570734B2 (zh)
AT (1) ATE327653T1 (zh)
CA (1) CA2311891A1 (zh)
DE (2) DE19928042A1 (zh)
TW (1) TW477159B (zh)

Families Citing this family (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2002060228A1 (en) * 2001-01-24 2002-08-01 Stmicroelectronics S.R.L. Fault management method for electronic ballast
AUPR610801A0 (en) * 2001-07-04 2001-07-26 Briter Electronics Controlling apparatus
GB2383180B (en) * 2001-12-11 2005-05-04 Westinghouse Brake & Signal Signal lamps and apparatus
EP1935217A4 (en) * 2005-10-12 2009-11-04 Int Rectifier Corp INTEGRATED BALLAST CONTROL CIRCUIT WITH ADJUSTABLE INTENSITY
DE102008056814A1 (de) * 2008-11-11 2010-05-27 HÜCO Lightronic GmbH Elektronisches Vorschaltgerät, Beleuchtungsgerät und Verfahren zum Betrieb dieser
US11166645B2 (en) 2018-12-18 2021-11-09 Biosense Webster (Israel) Ltd. Visualizing lesions formed by thermal ablation in a magnetic resonance imaging (MRI) scan

Family Cites Families (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH01132096U (zh) * 1988-03-04 1989-09-07
ES2049790T3 (es) * 1989-10-09 1994-05-01 Siemens Ag Adaptador electronico.
TW266383B (en) * 1994-07-19 1995-12-21 Siemens Ag Method of starting at least one fluorescent lamp by an electronic ballast and the electronic ballast used therefor
US5550436A (en) * 1994-09-01 1996-08-27 International Rectifier Corporation MOS gate driver integrated circuit for ballast circuits
US5729096A (en) * 1996-07-24 1998-03-17 Motorola Inc. Inverter protection method and protection circuit for fluorescent lamp preheat ballasts
US6008593A (en) * 1997-02-12 1999-12-28 International Rectifier Corporation Closed-loop/dimming ballast controller integrated circuits
US5982110A (en) * 1997-04-10 1999-11-09 Philips Electronics North America Corporation Compact fluorescent lamp with overcurrent protection
JPH1167478A (ja) * 1997-08-13 1999-03-09 Matsushita Electric Works Ltd 放電灯点灯装置

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Publication number Publication date
DE50012802D1 (de) 2006-06-29
EP1061779A2 (de) 2000-12-20
JP4570734B2 (ja) 2010-10-27
ATE327653T1 (de) 2006-06-15
EP1061779A3 (de) 2004-11-03
DE19928042A1 (de) 2000-12-21
US6310447B1 (en) 2001-10-30
CA2311891A1 (en) 2000-12-18
TW477159B (en) 2002-02-21
JP2001023789A (ja) 2001-01-26

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