EP1061779A2 - Verfahren zum Betreiben mindestens einer Leuchtstofflampe sowie elektronisches Vorschaltgerät dafür - Google Patents
Verfahren zum Betreiben mindestens einer Leuchtstofflampe sowie elektronisches Vorschaltgerät dafür Download PDFInfo
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- EP1061779A2 EP1061779A2 EP00104995A EP00104995A EP1061779A2 EP 1061779 A2 EP1061779 A2 EP 1061779A2 EP 00104995 A EP00104995 A EP 00104995A EP 00104995 A EP00104995 A EP 00104995A EP 1061779 A2 EP1061779 A2 EP 1061779A2
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- circuit
- control
- δit
- load current
- load
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- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
- H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
- H05B41/295—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
- H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
- H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
Definitions
- the invention relates to a method for operating at least one Fluorescent lamp using an electronic ballast according to the preamble of claim 1 and a correspondingly trained electronic Ballast itself according to the preamble of claim 5.
- EP-B-0 801 881 describes such a method for operating at least one Fluorescent lamp known with the help of an electronic ballast, the one half-bridge circuit coupled to a rectifier circuit with two in series has mutually activated, alternatively activated power transistors.
- a load circuit is connected, the at least contains a fluorescent lamp and its load current is monitored.
- a control and regulating circuit is provided. This is with a monitoring circuit for continuous monitoring of the load current and with a high-frequency control circuit derived therefrom equipped for the power transistors.
- the monitoring circuit In each case predetermined, different reference levels for the one to be detected Load current is set or an automatic shutdown of the electronic Ballast prepared for a predetermined, limited period of time.
- the monitoring circuit compares the instantaneous value of the load current with that activated reference level and gives each time this reference level is reached an output pulse.
- These output pulses indicate in dependence of their occurrence or non-existence during a predetermined time by the time value transmitter Defined periods of normal or faulty conditions in the load circuit. With these output pulses, when the operating state is undisturbed, the regulated control circuit the lamp current is regulated depending on the time or in the event of a fault an already prepared automatic shutdown of the electronic ballast triggered.
- the ignition voltage can not be set freely in its height, as this by determines a fixed threshold defined internally in the integrated circuit is.
- the adjustment required in the frame for different applications of a still given tolerance range permissible ignition and / or preheating voltage is also at best in the known electronic ballast appropriate external wiring of the integrated circuit and therefore then can only be achieved with a corresponding effort.
- the present invention is therefore based on a subtask, in further training of the method mentioned at the beginning for operating at least one fluorescent lamp specify a further embodiment, with which in addition to a reliable Regulation of the load current, especially in the case of aged fluorescent lamps the possibility is opened of being able to safely master such applications, too which lamp types with critical ignition behavior are to be used.
- the present invention is based on another subtask, the electronic one Ballast of the type appreciated above such that it despite a corresponding degree of integration of its control and regulation circuit and thus reduced effort for external wiring only by simple Adaptation to a large extent reliably in a wide variety of applications can be used.
- the solutions according to the invention enable the Tolerance range of the electronic ballast with regard to monitoring to expand the load current.
- This property is particularly advantageous if if the load circuit comprises a lamp circuit with several fluorescent lamps. With such lamp circuits, but also with fluorescent lamps with critical Ignition behavior is difficult with a given integrated circuit Controlling the tolerance range safely. Tolerance ranges can be found in the integrated circuit should not be easily specified wide enough, because then, if necessary critical operating conditions, such as B. unwillingness to ignition or misfiring with aged fluorescent lamps can no longer be detected properly.
- a another way to integrate the electronic ballast with a given Equip control and regulating circuit and yet also critical lamp circuits to operate with it would be, with effort, the external wiring to adapt the integrated circuit to the respective application. Considering that electronic ballasts are products today, which must be largely automated in the face of high cost pressure such a solution is uneconomical.
- this problem is solved in an elegant manner with a relatively simple one Circuit measure solved.
- the one to be monitored in the control and regulating circuit Load current signal becomes a direct current signal from an additional direct current source superimposed, the level of which depends on the lamp circuit used in each case is adjustable. Since the preheating voltage, but especially the ignition voltage are critical in these difficult to control applications, it is sufficient to this overlay only for those beginning with the end of the preheating period To provide ignition period.
- the level adjustment is the additional DC source to achieve with simple means and surely by that the to be adjusted Level derived internally from the current flow through the matching resistor is assigned to the current-dependent controlled oscillator as an external resistor and by dimensioning the blanking gap of the half-bridge circuit is set. A circuit adaptation to different lamp circuits in the load circuit is therefore due to the appropriate dimensioning single ohmic resistance.
- FIG 1 is an electronic ballast for operating at least one Fluorescent lamp and the actual load circuit, here with just one example Fluorescent lamp, shown.
- the electronic ballast shown is based on an electronic ballast in its basic structure as well a plurality of circuit details already from the document mentioned above EP-B-0 801 881 is known, to which reference can be made here.
- Known circuit parts and their function in connection with the present Invention are of minor importance are therefore below only summarized and described for the sake of completeness.
- a high-frequency filter 1 and a rectifier bridge 2 are connected to AC voltage u ⁇ as well as a step-up converter 3 connected, the charging choke L1, a charging diode D1, a first power transistor V1 and a storage capacitor as an output stage Co owns.
- the power transistor V1 is integrated as one Circuit executed control and control circuit IC driven.
- the step-up converter 3 provides at its output a compared to rectified mains voltage increased stabilized DC voltage, the so-called intermediate circuit voltage etc.
- An inverter with a half-bridge circuit is also provided, which here in particular by two more, in series parallel to the output of the step-up converter 3 lying further power transistors V2 and V3 as well as a bridge capacitor CB is realized.
- V3 is a load circuit 4, shown here with a further choke L2, a fluorescent lamp FL and an ignition capacitor Cz, connected.
- control and regulating circuit IC All essential control and regulating functions of the electronic ballast are implemented in the control and regulating circuit IC.
- control and regulating circuit IC in Figure 1 only as a module with external connections P1 to P24, to which external components are connected and in FIG. 2 also shown in more detail in the form of a block diagram.
- a defined power supply for the control and regulating circuit is in practical use IC of considerable importance, but in the present case it can already be assumed to be known.
- a power supply unit is therefore simplified in FIG IPG schematically shown that the functions start properly of the control and regulating circuit IC and, moreover, by the state of charge an externally connected charging capacitor Ccc is controlled.
- the Power supply unit IPG generates an internal auxiliary voltage IC-BIAS for supply of the internal circuit units of the control and regulating circuit IC and supplies a reference voltage Vref.
- the control and regulating circuit IC also contains it should only be pointed out an arrangement PFC for controlling the power factor.
- control and regulating functions of the control and regulating circuit IC are also on already known. So there is a control circuit for the half-bridge circuit V2, V3 from a selection circuit SEL and driver circuits connected to it HSD or LSD. A high frequency pulse train is at a control input the selection circuit SEL supplied via the driver circuits HSD or LSD the power transistors V2 and V3 of the half-bridge circuit according to Art of a flip-flop alternatively turns on with a defined blanking interval.
- This controlling pulse sequence is supplied by a current-dependent controlled oscillator CCO with three setting inputs that correspond to the external connections P23, P24 and P3.
- a first setting resistor RTL is connected to connection P23, its dimensioning in particular the blanking gap of the power transistors Defines V2 and V3 of the half-bridge circuit.
- At the other external connection P24 is an adjustable capacitor Cf.
- the third connection of the oscillator CCO, with connected to the external connection P3, is connected to a high-resistance filter network, in particular formed by ohmic resistors Rf and Rfmin and another Setting capacitor Cc, connected.
- the filter network is connected to ground or to a defined reference voltage (In the rest of the description, here is always an example of mass spoken).
- the dimensioning of these external components defines the lower or upper limit frequency of the current-dependent controlled oscillator CCO and the size of the blanking interval mentioned. This is achieved via the high-resistance filter network current-controlled oscillator CCO fed a control signal that its Instantaneous frequency determined.
- This control signal is used with a control operational amplifier OPR generated. This compares the internally generated reference voltage Vref with a second input voltage supplied via the external connection P5, the average of the current flowing through the half-bridge circuit V2, V3 corresponds.
- the oscillator circuit described provides a closed control loop for regulation of the load current flowing in the half-bridge circuit. Rising Load current increases the output voltage of the control operational amplifier OPR what again the oscillator CCO towards a higher pulse repetition frequency controls. However, this frequency increase in turn causes a reduction in the load current. The same applies to the reverse direction when the tendency is falling Load current.
- the electronic ballast is through an appropriate definition the reference voltage Vref also dimmable.
- a monitoring function is implemented in the control and regulating circuit IC, to control the lamp start, the status of the fluorescent lamp in stationary operation Monitor FL and detect any malfunctions that may occur.
- a monitoring circuit MON which continuously monitors the load current, d. H. the current flowing through the half-bridge circuit V2, V3, monitored and on the other hand
- a timer PST is provided, which is a time base for this monitoring process delivers.
- a first internal power source IT is connected to one via the external connection P6 Grounded additional charging capacitor CT connected. It will start up of the electronic ballast activates and charges the external charging capacitor CT on.
- a linear up to a final value is formed at the external connection P6 increasing signal voltage from the control input of the time transmitter PST is supplied and provides the time base for this. To do this, this signal voltage compared in the time value generator PST with predetermined threshold values.
- the time value transmitter PST gives a selection signal S1, S2, S3 or S4 and defines certain periods with their chronological sequence for preheating, ignition, then normal operation of the FL fluorescent lamp or to reset their control when errors occur, especially when Misfiring or permanent unwillingness to ignite.
- the meaning of the from the time value transmitter PST generated selection signals S1 to S4 is related to the function the monitoring circuit MON explained.
- the monitoring circuit MON has a signal input which is via the external Terminal P7 and a series resistor at the low level Output of the half-bridge circuit V2, V3 is connected. That about the Monitoring circuit MON input signal is thus a through the current flowing through the power transistor V3, i. H. also proportional to the load current pulsed signal. This signal becomes the output signal as a DC bias another internal current source IM superimposed by the selection signal S3 of the time transmitter PST is temporarily activated.
- the level of this second internal current source IM generated bias signal DC is from Current flow through the setting resistor RTL of the current-dependent controlled oscillator CCO derived. For this purpose, IC internally via current mirror, part of the through the setting resistance RTL flowing current of the other internal current source IM fed.
- this external setting resistor RTL can thus be used without an internal adjustment or additional external connections of the control and Control circuit IC an adaptation of the monitoring function of the monitoring circuit MON of variants of the design of the load circuit 4, in particular certain Reach lamp types or lamp circuits. In other words, is it with this measure despite the predetermined response thresholds of the monitoring circuit MON for preheating or ignition voltage possible, this monitoring function for the individual application via the dimensioning of the RTL setting resistance specifically.
- the control and regulating circuit IC is therefore without internal adjustments for a wide range of circuit alternatives of the load circuit 4 can be used, in particular tolerances for the It is better to absorb ignition current with certain lamp types.
- MON is in the monitoring circuit at certain periods at lamp start and also in normal burning operation one of several predefined threshold values for the load current to be monitored activated. As soon as the level of the input signal of the monitoring circuit MON reaches the currently activated threshold value, this gives an output pulse QM from. In the course of time, this results in a sequence of brief output pulses QM, with which control processes in other units of the Control and regulating circuit IC are triggered.
- a third internal current source ISC is provided, the output of which is via the external Port P1 is connected to the external low-pass filter already explained.
- the third internal current source ISC is in the manner of a flip-flop in each case by the output pulses QM of the monitoring circuit MON set or by the selection circuit SEL reset.
- the third internal current source ISC thus charges the external capacitor Cc of the low-pass filter. Charging the external charging capacitor Cc proportional, the current-controlled oscillator changes CCO fed to its control input via the external connection P3 Input current If.
- This second control loop is the current control described in the introduction overriding for stationary operation, it limits and regulates the load current when the lamp starts and when malfunctions are detected.
- the function of the monitoring circuit MON is clearest to illustrate using the sequence control when starting a lamp. Will that electronic ballast connected to the network, the control and is described Control circuit IC activated as soon as the switch-on threshold is reached. The current dependent The controlled oscillator CCO then starts with a predetermined lower limit frequency and thus controls the selection circuit SEL, which via the driver circuits HSD and LSD put the half-bridge circuit V2, V3 into operation. The first internal Current source IT begins to charge the external charging capacitor CT and sets PST timer in operation. The lamp start begins with a preheating period ⁇ pt. A corresponding, relatively lower one is in the monitoring circuit MON Threshold Mp activated for the preheating current.
- the monitoring circuit MON gives each time this threshold value Mp is reached by a pulse of Load current from an output pulse QM.
- the selection circuit is used with these SEL triggered and the third internal power source ISC activated. So that is the higher-level, described in connection with the function of this current source ISC, d. H. second control loop for current control started. During this Preheating period ⁇ pt the output of a signal amplifier QPT is switched off.
- This Output can e.g. for controlling a preheating circuit or for setting a DC bias at the control input of the monitoring circuit MON, for free preheating voltage setting can be used.
- the linearly increasing input voltage of the time value transmitter PST reaches a predetermined preheating level.
- the preheating period .DELTA.pt is completed and the time value generator PST generates the first selection signal S1, which is output to the monitoring circuit MON and the signal amplifier QPT.
- a higher threshold value Mi for the ignition current of the fluorescent lamp FL is thus activated in the monitoring circuit MON, and an ignition period ⁇ it begins.
- the time transmitter PST At approximately the same time, preferably immediately at the beginning of the ignition period ⁇ it, the time transmitter PST generates another, the fourth selection signal S4, the trailing edge of which coincides with the reaching of a maximum level of the input voltage of the time transmitter PST.
- the second internal current source IM is activated and a switch OPRd controlled in the manner of a flip-flop is also released.
- the monitoring circuit MON monitors the input signal fed to it, which is proportional to the load current, at this threshold and, depending on this, supplies the further output pulses QM1.
- the switch OPRd is first set and reset by the output signal of the selection circuit SEL.
- ground potential is applied to the non-inverting input of the control operational amplifier OPR which is connected to the external connection P5. In this way, the limitation of the load current through the control operational amplifier OPR is overridden during the duration of the ignition period ⁇ it, ie the ignition voltage is not limited.
- the fluorescent lamp FL only ignites within a predetermined time few ignition attempts.
- the peak value of the load current then goes automatically to a normal operating value and thereby reaches the threshold value Mi MON monitoring circuit no longer, there are no further output pulses QM generated.
- the time transmitter PST continues to run. It goes through its rising input voltage first a predetermined ignition level and finally reaches a maximum Level that initiates a reset of the timer PST. With reaching of this maximum level, the time transmitter generates the output signal S3, on the one hand in the monitoring circuit MON activated a threshold value Mo, which in normal burning operation of the fluorescent lamp FL from the rated load current is not is reached, so no further output pulses QM are generated by it. On the other hand, with the third selection signal S3, the time transmitter PST assigned second internal power source IT switched off. The connected to it Charging capacitor CT begins to discharge, i. H. that fed to the time value transmitter PST Input signal drops to a constant level that is normal Burning operation is held.
- the time value generator PST generates another, the second selection signal S2. This is held until the input signal of the time transmitter PST falls again passes through the ignition level.
- This pulse duration of the second selection signal S2 defines a switch-off period ⁇ st following the ignition period ⁇ it in which in the event of a fault, the switching off of the electronic ballast is prepared.
- a shutdown unit with a counter CTR is required to perform this function and a shutdown circuit SDL.
- the counter CTR is both by the rising and falling edge of the second selection signal S2 reset. It outputs the output pulses QM of the monitoring circuit MON as Counting pulses supplied. In the normal starting process, it reaches after, for example four counts and then activates the internal power source IT. in the the leading edge of the second selection signal S2 sets the counter CTR back and enables the SDL shutdown circuit in preparation. Now that is Number of unsuccessful ignition attempts or the number of output pulses now occurring QM counted. If the counter CTR reaches its end value at one lamp unwilling to ignite, it activates the preparatively activated shutdown circuit SDL.
- the control and regulating circuit IC is designed to conform to a relatively wide tolerance range Adapt changes in the load current. Such changes can in particular in the dimming state for multi-lamp applications or also for critical ones Lamp tolerances, e.g. B. caused by aged, high-resistance lamp filaments, occur. These cases can lead to the rule operational amplifier OPR no longer works within its defined control range. That state is detected by a further comparator COMP, which with its non-inverting Input is connected to the external port P1 and its inverting Input an internally generated reference voltage Vcc 'is supplied compared to the voltage occurring in the normal operating state on the charging capacitor Ccc is significantly reduced, for example by 25%. Such occurs Operating state, the comparator COMP gives the monitoring circuit MON a control signal with which a state is set there in which all reference levels Mp, Mi, Mdo and Mo can be significantly reduced. The monitoring circuit MON therefore works perfectly even with lower lamp currents.
- Lamp tolerances e.g. B. caused by aged, high-resi
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- Circuit Arrangements For Discharge Lamps (AREA)
Abstract
Description
Claims (8)
- Verfahren zum Betreiben mindestens einer Leuchtstofflampe (FL) durch ein elektronisches Vorschaltgerät mit einem integrierten Steuer- und Regelkreis (IC) zum Regeln des Laststromes in einem über eine Halbbbrückenschaltung (V2, V3) angeschlossenen Lastkreis (4) mit der mindestens einen Leuchtstofflampe (FL) mittels einer hochfrequent geregelten Ansteuerschaltung (CCO, SEL, HSD, LSD) der Halbbbrückenschaltung, wobei in dem Steuer- und Regelkreisbei jedem Lampenstart bzw. einer Störung ein Zeitwertgeber (PST, IT, CT) zum Erzeugen von Auswahlsignalen (S1, S2, S3, S4) gestartet wird, die in ihrer Abfolge vorbestimmte Zeiträume (Δpt, Δit, Δst, Δot), beispielsweise eine Vorheizperiode (Δpt) bzw. eine Zündperiode (Δit) definieren,mit den Auswahlsignalen in einer Überwachungsschaltung (MON) für den Laststrom jeweils unterschiedliche vorgegebene Referenzpegel (Mp, Mi, Mdo bzw. Mo) aktiviert werden,durch die Überwachungsschaltung, sobald der Momentanwert des impulsförmigen Laststromes den aktivierten Referenzpegel erreicht, Steuerimpulse (QM) abgegeben werden,die in Abhängigkeit von ihrem Auftreten oder Ausbleiben während des aktuellen Zeitraumes (Δpt, Δit, Δst, bzw. Δot) einen normalen Zustand bzw. eine Störung im Lastkreis kennzeichnen und im Normalzustand als Regler-Istwerte der Ansteuerschaltung (CCO, ISC, SEL, HSD, LSD) zugeführt werden bzw. bei einer Störung ein automatisches Abschalten des elektronischen Vorschaltgerätes auslösen,
- Verfahren nach Anspruch 1, dadurch gekennzeichnet, daß das Gleichstromsignal (DC), das dem zu detektierenden Stromsignal überlagert wird, von einer im Steuer- und Regelkreis (IC) intern vorgesehenen Gleichstromquelle (IM) erzeugt wird, die für den Zeitraum der Zündperiode (Δit) durch ein weiteres vom Zeitwertgeber (PST, IT, CT) abgegebenes Auswahlsignal (S4) im aktivierten Zustand gehalten wird.
- Verfahren nach Anspruch 2, dadurch gekennzeichnet, daß der Pegel der internen Gleichstromquelle (IM) vom Stromfluß durch einen Widerstand (RTL) eingestellt wird, der extern an die hochfrequent geregelte Ansteuerschaltung (CCO, SEL, HSD, LSD) der Halbbrückenschaltung (V2, V3) angeschlossen ist und eine Austastlücke in der Halbbrückenschaltung bestimmt.
- Verfahren nach einem der Ansprüche 1 bis 3, dadurch gekennzeichnet, daß die über die Ansteuerschaltung (CCO, SEL, HSD, LSD) und die daran angeschlossene Halbbrückenschaltung (V2, V3) bewirkte Regelung des Laststromes während der Zündperiode (Δit) bis zum tatsächlichen Zündzeitpunkt der mindestens einen Leuchtstofflampe (FL) deaktiviert wird,
- Elektronisches Vorschaltgerät zum Betreiben mindestens einer Leuchtstofflampe (FL) mit einem als integrierter Schaltkreis ausgebildeten Steuer- und Regelkreis (IC), an den über eine Halbbrückenschaltung (V2, V3) ein Lastkreis mit der mindestens einen Leuchtstofflampe zum Regeln des Laststromes angeschlossen ist, wobei in dem Steuer- und Regelkreiseine hochfrequent geregelte Ansteuerschaltung (CCO, SEL, HSD, LSD) für die Halbbrückenschaltung (V2, V3),ein bei jedem Lampenstart bzw. einer Störung erneut zu startender Zeitwertgeber (PST, IT, CT) zum Erzeugen von Auswahlsignalen (S1, S2, S3), die in ihrer Abfolge vorbestimmte Zeiträume (Δpt, Δit, Δst, Δot), beispielsweise eine Vorheizperiode (Δpt) bzw. eine Zündperiode (Δit) definieren,eine an die Halbbrückenschaltung angekoppelte Überwachungsschaltung (MON) für den Laststrom, die als ein Schwellwertkomparator mit mehreren, individuell jeweils durch eines der Auswahlsignale aktivierten Referenzpegeln (Mp, Mi, Mdo, Mo) ausgebildet ist und jeweils einen Steuerimpuls (QM) erzeugt, sobald der impulsförmige Laststrom den momentan aktivierten Referenzpegel erreicht,
vorgesehen ist, wobei diese Steuerimpulse in Abhängigkeit von ihrem Auftreten oder Ausbleiben während des aktuellen Zeitraumes (Δpt, Δit, Δst, bzw. Δot) einen normalen Zustand bzw. eine Störung im Lastkreis kennzeichnen und im Normalzustand als Regler-Istwerte der Ansteuerschaltung (CCO, ISC, SEL, HSD, LSD) zugeführt werden bzw. bei einer Störung ein automatisches Abschalten des elektronischen Vorschaltgerätes auslösen, - Elektronisches Vorschaltgerät nach Anspruch 5, bei dem extern an die Ansteuerschaltung (CCO, SEL, HSD, LSD) für die Halbbrückenschaltung(V2, V3) ein ohmscher Widerstand (RTL) angeschlossen ist, durch den die Austastlücke dieser Leistungstransistoren festgelegt ist, dadurch gekennzeichnet, daß der Pegel der internen Gleichstromquelle (IM) vom Stromfluß durch diesen Widerstand (RTL) abgeleitet ist.
- Elektronisches Vorschaltgerät nach einem der Ansprüche 5 oder 6, dadurch gekennzeichnet, daß im Steuer- und Regelkreis (IC) ferner ein Sperrschalter (OPRd) vorgesehen ist, der den Regelkreis der Ansteuerschaltung (CCO, SEL, HSD, LSD) und damit eine Regelung des Laststromes über an diese angeschlossene Halbbrückenschaltung (V2, V3) während der Zündperiode (Δit) bis zum tatsächlichen Zündzeitpunkt der mindestens einen Leuchtstofflampe (FL) deaktiviert.
- Elektronisches Vorschaltgerät nach Anspruch 7, dadurch gekennzeichnet, daß die als Schwellwertkomparator ausgebildete Überwachungsschaltung (MON) neben den Referenzpegeln (Mp, Mi) für den Laststrom während der Vorheizperiode (Δpt) bzw. während der Zündperiode (Δit) mit einem weiteren Referenzpegel (Mdo) ausgestattet ist, dessen Pegel nach der Beziehung Mp < Mdo < Mi festgelegt ist und damit die Überwachungsschaltung, sobald das ihrem Eingang zugeführte, vom Laststrom abgeleitete Signal diesen weiteren Referenzpegel (Mop) überschreitet, jeweils einen weiteren Steuerimpuls (QM1) erzeugt, der dem Sperrschalter (OPRd) als Auslöseimpuls zugeführt ist.
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
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DE19928042 | 1999-06-18 | ||
DE19928042A DE19928042A1 (de) | 1999-06-18 | 1999-06-18 | Verfahren zum Betreiben mindestens einer Leuchtstofflampe sowie elektronisches Vorschaltgerät dafür |
Publications (3)
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EP1061779A2 true EP1061779A2 (de) | 2000-12-20 |
EP1061779A3 EP1061779A3 (de) | 2004-11-03 |
EP1061779B1 EP1061779B1 (de) | 2006-05-24 |
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EP00104995A Expired - Lifetime EP1061779B1 (de) | 1999-06-18 | 2000-03-09 | Verfahren zum Betreiben mindestens einer Leuchtstofflampe sowie elektronisches Vorschaltgerät dafür |
Country Status (7)
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US (1) | US6310447B1 (de) |
EP (1) | EP1061779B1 (de) |
JP (1) | JP4570734B2 (de) |
AT (1) | ATE327653T1 (de) |
CA (1) | CA2311891A1 (de) |
DE (2) | DE19928042A1 (de) |
TW (1) | TW477159B (de) |
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AUPR610801A0 (en) * | 2001-07-04 | 2001-07-26 | Briter Electronics | Controlling apparatus |
GB2408834B (en) * | 2001-12-11 | 2005-07-20 | Westinghouse Brake & Signal | Signal lamps and apparatus |
DE102008056814A1 (de) * | 2008-11-11 | 2010-05-27 | HÜCO Lightronic GmbH | Elektronisches Vorschaltgerät, Beleuchtungsgerät und Verfahren zum Betrieb dieser |
US11166645B2 (en) | 2018-12-18 | 2021-11-09 | Biosense Webster (Israel) Ltd. | Visualizing lesions formed by thermal ablation in a magnetic resonance imaging (MRI) scan |
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EP0422255B1 (de) * | 1989-10-09 | 1994-03-02 | Siemens Aktiengesellschaft | Elektronisches Vorschaltgerät |
US5550436A (en) * | 1994-09-01 | 1996-08-27 | International Rectifier Corporation | MOS gate driver integrated circuit for ballast circuits |
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JPH1167478A (ja) * | 1997-08-13 | 1999-03-09 | Matsushita Electric Works Ltd | 放電灯点灯装置 |
-
1999
- 1999-06-18 DE DE19928042A patent/DE19928042A1/de not_active Withdrawn
-
2000
- 2000-03-09 EP EP00104995A patent/EP1061779B1/de not_active Expired - Lifetime
- 2000-03-09 AT AT00104995T patent/ATE327653T1/de not_active IP Right Cessation
- 2000-03-09 DE DE50012802T patent/DE50012802D1/de not_active Expired - Lifetime
- 2000-04-19 TW TW089107345A patent/TW477159B/zh not_active IP Right Cessation
- 2000-06-14 US US09/593,381 patent/US6310447B1/en not_active Expired - Lifetime
- 2000-06-15 JP JP2000179503A patent/JP4570734B2/ja not_active Expired - Fee Related
- 2000-06-16 CA CA002311891A patent/CA2311891A1/en not_active Abandoned
Patent Citations (3)
Publication number | Priority date | Publication date | Assignee | Title |
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EP0801881B1 (de) * | 1994-07-19 | 1998-05-20 | Siemens Aktiengesellschaft | Verfahren zum betreiben mindestens einer leuchtstofflampe mit einem elektronischen vorschaltgerät sowie vorschaltgerät dafür |
DE19805733A1 (de) * | 1997-02-12 | 1998-08-20 | Int Rectifier Corp | Integrierte Treiberschaltung |
WO1998046052A2 (en) * | 1997-04-10 | 1998-10-15 | Koninklijke Philips Electronics N.V. | Ballast for compact fluorescent lamp with current protection |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
EP1935217A2 (de) * | 2005-10-12 | 2008-06-25 | International Rectifier Corporation | Integrierte schaltung für eine dimmbare ballaststeuerung |
EP1935217A4 (de) * | 2005-10-12 | 2009-11-04 | Int Rectifier Corp | Integrierte schaltung für eine dimmbare ballaststeuerung |
Also Published As
Publication number | Publication date |
---|---|
EP1061779B1 (de) | 2006-05-24 |
JP4570734B2 (ja) | 2010-10-27 |
JP2001023789A (ja) | 2001-01-26 |
DE50012802D1 (de) | 2006-06-29 |
US6310447B1 (en) | 2001-10-30 |
ATE327653T1 (de) | 2006-06-15 |
EP1061779A3 (de) | 2004-11-03 |
CA2311891A1 (en) | 2000-12-18 |
TW477159B (en) | 2002-02-21 |
DE19928042A1 (de) | 2000-12-21 |
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