EP0674102B1 - Wechselstromzündung mit optimierter elektronischer Schaltung - Google Patents

Wechselstromzündung mit optimierter elektronischer Schaltung Download PDF

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Publication number
EP0674102B1
EP0674102B1 EP95102930A EP95102930A EP0674102B1 EP 0674102 B1 EP0674102 B1 EP 0674102B1 EP 95102930 A EP95102930 A EP 95102930A EP 95102930 A EP95102930 A EP 95102930A EP 0674102 B1 EP0674102 B1 EP 0674102B1
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EP
European Patent Office
Prior art keywords
semiconductor switch
ignition
circuit
voltage
ignition system
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP95102930A
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German (de)
English (en)
French (fr)
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EP0674102A2 (de
EP0674102A3 (de
Inventor
Michael Daetz
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Volkswagen AG
Mercedes Benz Group AG
Original Assignee
Daug Deutsche Automobil Gmbh
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Application filed by Daug Deutsche Automobil Gmbh filed Critical Daug Deutsche Automobil Gmbh
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Publication of EP0674102A3 publication Critical patent/EP0674102A3/de
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Classifications

    • F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F02—COMBUSTION ENGINES; HOT-GAS OR COMBUSTION-PRODUCT ENGINE PLANTS
    • F02P—IGNITION, OTHER THAN COMPRESSION IGNITION, FOR INTERNAL-COMBUSTION ENGINES; TESTING OF IGNITION TIMING IN COMPRESSION-IGNITION ENGINES
    • F02P3/00—Other installations
    • F02P3/02—Other installations having inductive energy storage, e.g. arrangements of induction coils
    • F02P3/04—Layout of circuits
    • F02P3/055—Layout of circuits with protective means to prevent damage to the circuit, e.g. semiconductor devices or the ignition coil
    • F02P3/0552—Opening or closing the primary coil circuit with semiconductor devices
    • F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F02—COMBUSTION ENGINES; HOT-GAS OR COMBUSTION-PRODUCT ENGINE PLANTS
    • F02P—IGNITION, OTHER THAN COMPRESSION IGNITION, FOR INTERNAL-COMBUSTION ENGINES; TESTING OF IGNITION TIMING IN COMPRESSION-IGNITION ENGINES
    • F02P15/00—Electric spark ignition having characteristics not provided for in, or of interest apart from, groups F02P1/00 - F02P13/00 and combined with layout of ignition circuits
    • F02P15/10—Electric spark ignition having characteristics not provided for in, or of interest apart from, groups F02P1/00 - F02P13/00 and combined with layout of ignition circuits having continuous electric sparks

Definitions

  • the invention relates to an AC ignition system with at least one ignition output stage according to the preamble of patent claim 1.
  • Such an AC ignition system is known from DE-OS-3 928 726 and the subsequently published EP-A-0 596 471, and has the advantage over conventional ignition systems, for example so-called transistor ignitions with static high-voltage distribution, that small and thus inexpensive Ignition coils can be used. This enables the ignition point to be reached quickly in the ⁇ s range. Furthermore, according to the above. Publications ensures the optimum ignition in that it remains switched on for the entire burning time, regardless of the speed, during which it generates a bipolar spark current.
  • FIG. 1 Such an AC ignition system known from the above-mentioned documents is shown in FIG. 1.
  • reference number Z denotes an ignition output stage, which has an ignition coil Tr with a primary and secondary coil, a semiconductor switch T connected in series with the primary coil and an oscillating circuit capacitor C and an energy recovery diode D, which are also arranged in series with the primary winding.
  • a current measuring resistor R1 for detecting the actual value of the primary coil current is provided in series with the semiconductor switch T.
  • a control and regulating circuit 1 takes over the control of the semiconductor switch T via its control electrode, for which purpose the voltage drop across the resistor R1 and the voltage U T occurring at the semiconductor switch T are supplied via the circuit node A.
  • the control and regulating circuit 1 is supplied with a control signal containing the ignition signal via its connection U st .
  • a switched-mode power supply (not shown in FIG. 1) generates an operating voltage U B of 180 V, which is applied to the primary coil of the ignition coil Tr becomes.
  • the switched-mode power supply in turn, is powered by an on-board battery.
  • the ignition output stage Z is operated in current mode, i. H. the semiconductor switch T is turned on until a certain current through the primary coil is reached. At this time, the semiconductor switch T turns off, so that the energy stored in the primary coil can charge the capacitor C. This leads to an approximately sinusoidal curve of the voltage applied to the semiconductor switch T. The negative half-wave of the oscillation is limited by diode D to small voltage amplitudes. During this phase of the current flow through the diode D, the semiconductor switch T should be switched on again. At this point in time, the switch-on losses are also very low, since the voltage applied to the semiconductor switch has almost the value zero.
  • the actual value of the current flowing through the primary winding is usually measured via the voltage drop across the resistor R1. After reaching the desired value of the current, the semiconductor switch T is switched off, with the result that the voltage across the resistor R1 drops very quickly. Various measures are known to prevent the semiconductor switch from being switched on again immediately.
  • One of the known measures consists in evaluating the voltage U T present at the semiconductor switch T. According to FIG. 1, this is done by connecting point A of semiconductor switch T with the primary winding of ignition coil Tr to control and regulating circuit 1 and evaluating it there.
  • this solution has the disadvantage that it can only be prevented from being switched on again when the voltage U T is greater than the supply voltage U B. Therefore, in order to prevent vibrations for the period of time until the voltage U T has reached the value of the supply voltage U B , an additional lock, for. B. can be used via a timer. Such an additional lock must also be provided if the voltage U T at the semiconductor switch T falls below the value of the supply voltage U B again in order to achieve the above-mentioned advantage of switching at a voltage value of almost zero.
  • the disadvantage of such a timer that can be implemented in a simple manner is that that the switch-off threshold of the primary current is influenced. If multiple primaries are present, is also disadvantageous in that then the detection of the voltages U T generated at the semiconductor switches T depending on the primary circuit must be made at least once, even if the evaluation of the primary currents is done only once for the entire ignition system.
  • Another known solution uses a monostable multivibrator to prevent the semiconductor switch T from being switched on again for a defined period of time.
  • This solution with a defined time delay has the disadvantage that the time delay to be selected is, on the one hand, a function of the selected primary current and, on the other hand, also depends on whether or not the breakdown of the spark gap has already occurred on the secondary side of the ignition coil.
  • the tolerances of all time-determining components are also included in the time delay to be selected. Therefore, safe operation of the power stage cannot be ensured in all cases with this solution.
  • the object of the present invention is to provide an AC ignition system of the type mentioned at the outset, which has a simple circuit for controlling the semiconductor switch and with which a safe operation of the ignition system is ensured.
  • the resonant circuit capacitor - as is known from the above-mentioned documents - can be arranged parallel to the semiconductor switch.
  • a particularly advantageous embodiment is obtained when the resonant circuit capacitor is connected in parallel to the primary coil of the ignition coil.
  • the voltage load on the capacitor is thereby reduced by approximately 20%, so that a more cost-effective component can then be used.
  • an alternating current ignition system has a plurality of ignition output stages, all ignition output stages each containing an energy recovery diode.
  • the diodes are connected to form a wired-or circuit in order to be able to lead their diode currents to a single resistor, the voltage drop of which then serves as a trigger signal for switching the semiconductor switch on again.
  • the evaluation of the diode current is advantageously carried out only once for the entire system and not for each individual channel.
  • a clamping circuit for limiting the voltage applied to the semiconductor switch, which is constructed from a voltage divider and a comparator connected downstream of it.
  • the voltage divider is connected directly to the circuit node connecting the semiconductor switch to the primary coil; the output of the comparator, on the other hand, directly controls the control electrode of the semiconductor switch.
  • Such a clamping circuit can reliably prevent the maximum permissible voltages at the semiconductor switch, the energy recovery diode and the resonant circuit capacitor from being exceeded. Because without such a clamping circuit, correspondingly high safety distances from the maximum permissible values would have to be maintained to compensate for tolerances, with a negative cost consequence with regard to the components used.
  • the clamping circuit has the effect that the voltage U T at the semiconductor switch is limited to a value which is only slightly less than the maximum permissible value. As a result, the components used can be used close to their load limit.
  • Such a clamp circuit has the advantage over the usual use of Zener diodes that little chip area is consumed when the circuit is implemented in integrated circuit technology, since a large number of Zener voltages occur in the kV range in the case of the high voltages which occur during AC ignition. Diodes would be required, so that this would lead to a high chip area consumption.
  • bipolar transistors In ignition systems, it is known to use bipolar transistors, power MOS field-effect transistors or IGBT transistors (isolated gate bipolar transistors) as semiconductor switches.
  • IGBT transistors isolated gate bipolar transistors
  • An advantageous embodiment of the invention is also achieved with a MOS-controlled thyristor (MCT) as a semiconductor switch.
  • MCT thyristors MOS-controlled thyristors
  • the circuit diagram of an alternating current ignition system according to FIG. 2 shows, compared to that according to FIG. 1, a resistor R2 connected in series with the energy recovery diode D.
  • the current through this diode D begins to flow in the negative half-wave of the voltage oscillation generated by the capacitor C and the primary coil of the ignition coil Tr.
  • the voltage drop which then arises at this resistor R2 is fed to the control and regulating circuit 1, so that this voltage signal can serve as a trigger signal for switching the semiconductor switch T on again. Since only small voltages are present at the semiconductor switch T at this time, the switching on can take place without electrical losses.
  • the current is then taken over by the semiconductor switch T at the zero crossing of the oscillation.
  • the value of the resistor R2 is measured with a low resistance, so that the voltage drop across it is sufficient to control an electronic switch, for example a bipolar transistor. Compared to the circuit according to FIG. 1, the line between the semiconductor switch T circuit nodes connecting the primary coil and the control circuit 1 are eliminated.
  • the embodiment of Figure 3 differs from that of Figure 2 once in that the resonant circuit capacitor C is connected in parallel to the primary coil of the ignition coil Tr and also in that a MOS-controlled thyristor (MCT) is used as the semiconductor switch T.
  • MCT MOS-controlled thyristor
  • Such an MCT thyristor combines the advantageous properties of the thyristors, such as high dielectric strength, low forward losses and high specific current carrying capacity, with the ability to switch off the power semiconductors used to date, such as bipolar transistors, power MOS field-effect transistors or IGBT transistors.
  • the advantage that is achieved with the parallel connection of the resonant circuit capacitor C to the primary coil is that the voltage load on this capacitor is reduced by approximately 20%, so that a less expensive component can be used.
  • the voltage drop across the resistor R1 is still fed to the control and regulating circuit 1 in order to detect the actual value of the primary coil current.
  • the circuit according to FIG. 4 shows an AC ignition system with four ignition output stages Z1 to Z4.
  • Each of these ignition output stages contains an ignition coil Tr1 to Tr4, in each case a resonant circuit capacitor C1 to C4 connected in parallel to the primary coil, a semiconductor switch T1 to T4 each connected in series with the primary coil and a recovery diode D1 to D4 connected in parallel to the semiconductor switch.
  • diodes D1 to D4 are each connected with their cathode to the circuit node connecting the semiconductor switch to the primary coil, the anodes of which are led to a single resistor R2, which in turn is at reference potential.
  • a corresponding wired-or circuit is also implemented for the source electrodes of the semiconductor switches T1 to T4 by means of a single resistor R1, the voltage drop of which serves to determine the actual value of the primary coil current for all ignition output stages Z1 to Z4.
  • the resonant circuit capacitors C1 to C4 can also be connected in parallel to the semiconductor switches T1 to T4 in accordance with the reference symbols C1 'to C4' instead of in parallel with the primary coils.
  • FIG. 5 shows a circuit arrangement for an AC ignition system according to FIG. 2 with an oscillating circuit capacitance C 'arranged parallel to the semiconductor switch T, which can also be arranged parallel to the primary coil according to FIG. 3 (see reference symbol C).
  • this FIG. 5 contains a clamping circuit 2 for voltage limitation at the semiconductor switch T.
  • This clamping circuit 2 prevents the maximum permissible voltage at the semiconductor switch T of the diode D and the resonant circuit capacitor C or C 'from being exceeded. Without such a clamping circuit, correspondingly high safety distances from the maximum permissible values would have to be maintained to compensate for tolerances.
  • the clamp circuit 2 causes, for example, the voltage generated across the semiconductor switch T U T is limited to a value which is only slightly lower than the maximum permissible value.
  • the expensive components, that is to say the semiconductor switch T, the resonant circuit capacitor C or C ′ and the energy recovery diode D can thus be used close to their load limits.
  • the clamping circuit 2 shown in FIG. 5 is constructed with a voltage divider R4 / R5 and a comparator K connected downstream.
  • the voltage divider R4 / R5 is connected to the connection point A, which connects the semiconductor switch T to the primary coil, whereas the output of the comparator K on the one hand directly to the control electrode of the semiconductor switch T and on the other hand via a resistor R6 to the output of the control and regulating circuit 1 is connected.
  • An accurate and temperature-stable reference voltage source U ref serves as a comparison standard for limiting the voltage U T generated at the semiconductor switch T by supplying it to the non-inverting input of the comparator K.
  • the tap of the voltage divider R4 / R5 is present at the inverting input of the comparator K.
  • the voltage U T generated at the semiconductor switch T is divided down by this voltage divider R4 / R5 and compared with the reference voltage U ref by the comparator circuit K.
  • the output of the comparator K controls the semiconductor switch T, whereby a high accuracy and long-term constancy of the limiting voltage is achieved.
  • FIG. 6 A circuit design of the clamp circuit according to FIG. 5 is shown in FIG. 6, where the comparator K is constructed with an npn transistor T5 and a pnp transistor T6.
  • the base electrode of the transistor T5 is connected to the voltage divider R4 / R5, while its emitter electrode is connected to the reference voltage source U ref via a resistor R7 and its collector electrode is led to the base electrode of the transistor T6.
  • the base electrode of transistor T6 is connected on the one hand to the reference potential via a resistor R8 and on the other hand to the emitter electrode of transistor T6 via a resistor R9.
  • the emitter electrode of the transistor T6 is connected to the battery voltage U Bat .
  • the collector electrode of transistor T6 forms the output of the comparator.
  • the base voltage of the transistor T5 rises to a value which is greater than the sum of its base-emitter voltage and the reference voltage U ref , this transistor T5 becomes conductive.
  • the collector current of the transistor T5 can drive the transistor T6, which amplifies this current and thus drives the semiconductor switch T.
  • the resistor circuit with the resistors R7 to R9 is designed so that a quick response without over- and undershoots is achieved.
  • this clamping circuit 2 according to FIG. 6 offers the advantage of a small chip area consumption compared to the usual use of Zener diodes. Because using Zener diodes would be in the kV range due to the high voltages that occur with AC ignition very many zener diodes required. A corresponding implementation in integrated circuit technology with these Zener diodes would require a large chip area.
  • An MCT thyristor can also be provided for the semiconductor switch T in the AC ignition systems according to FIGS. 4 and 5.
  • a clamping circuit 2 according to FIG. 5 or 6 can be provided for all ignition output stages Z1 to Z4.

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  • Engineering & Computer Science (AREA)
  • Chemical & Material Sciences (AREA)
  • Combustion & Propulsion (AREA)
  • Mechanical Engineering (AREA)
  • General Engineering & Computer Science (AREA)
  • Ignition Installations For Internal Combustion Engines (AREA)
  • Thyristor Switches And Gates (AREA)
EP95102930A 1994-03-23 1995-03-02 Wechselstromzündung mit optimierter elektronischer Schaltung Expired - Lifetime EP0674102B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE4409984 1994-03-23
DE4409984A DE4409984B4 (de) 1994-03-23 1994-03-23 Wechselstromzündung mit optimierter elektronischer Schaltung

Publications (3)

Publication Number Publication Date
EP0674102A2 EP0674102A2 (de) 1995-09-27
EP0674102A3 EP0674102A3 (de) 1996-01-10
EP0674102B1 true EP0674102B1 (de) 1997-11-12

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ID=6513598

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Application Number Title Priority Date Filing Date
EP95102930A Expired - Lifetime EP0674102B1 (de) 1994-03-23 1995-03-02 Wechselstromzündung mit optimierter elektronischer Schaltung

Country Status (5)

Country Link
US (1) US5506478A (ja)
EP (1) EP0674102B1 (ja)
JP (1) JP3834761B2 (ja)
DE (2) DE4409984B4 (ja)
ES (1) ES2113132T3 (ja)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2988233A1 (fr) * 2012-03-16 2013-09-20 Renault Sa Allumage radiofrequence de moteur de vehicule automobile

Families Citing this family (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE19539915B4 (de) * 1995-10-27 2007-06-28 Elan Schaltelemente Gmbh & Co. Kg Verfahren zur Überwachung wie Stillstands- und/oder Einrichtdrehzahlüberwachung eines Antriebs, insbesondere hochdynamischen Servoantriebs, sowie Lastrelais insbesondere zur Verwendung bei einem entsprechenden Verfahren
DE19700179C2 (de) * 1997-01-04 1999-12-30 Bosch Gmbh Robert Zündsystem für einen Verbrennungsmotor
DE19953334C2 (de) * 1999-11-05 2002-05-08 Siemens Ag Fernauslesbare Identifikationsmarke und Verfahren zum Betrieb mehrerer solcher Identifikationsmarken
US6899092B2 (en) * 2002-07-27 2005-05-31 Ulf Arens System and method for increasing spark current to spark plugs
US7929266B2 (en) * 2007-12-19 2011-04-19 Freescale Semiconductor, Inc. Electronic device operable to protect a power transistor when used in conjunction with a transformer
JP2009185690A (ja) * 2008-02-06 2009-08-20 Honda Motor Co Ltd 内燃機関用トランジスタ式点火装置
US7944678B2 (en) * 2008-09-11 2011-05-17 Robertshaw Controls Company Low voltage power supply for spark igniter and flame sense
ITUB20151983A1 (it) * 2015-07-08 2017-01-08 Eldor Corp Spa Sistema di accensione elettronica per un motore endotermico e metodo di pilotaggio dello stesso
AT518968B1 (de) 2016-07-08 2019-05-15 Ge Jenbacher Gmbh & Co Og Steuervorrichtung für eine Vielzahl von Aktuatoren einer Brennkraftmaschine

Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0596471A2 (de) * 1992-11-04 1994-05-11 VOGT electronic AG Wechselstromzündsystem für Verbrennungskraftmaschinen mit Regelung der Zündenergie

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DE34787C (de) * J. DARLING in Glasgow, Lanark, Nordbritannien Seiten-Kuppelung für Eisenbahnfahrzeuge
US3394689A (en) * 1966-08-25 1968-07-30 Laurence W. Bell Resonant ignition system
IT1009972B (it) * 1973-04-27 1976-12-20 British Leyland Uk Ltd Bobina di accensione
US3945362A (en) * 1973-09-17 1976-03-23 General Motors Corporation Internal combustion engine ignition system
FR2465894A1 (fr) * 1979-09-21 1981-03-27 Psa Grpt Int Eco Rech Develop Dispositif electronique de commande d'une bobine d'allumage pour moteur a combustion interne
EP0098407A3 (de) * 1980-02-21 1984-04-04 Siemens Aktiengesellschaft Zündsystem für Brennkraftmaschinen
FR2510199A1 (fr) * 1981-07-22 1983-01-28 Siemens Sa Systeme d'allumage pour des moteurs a combustion interne
JPS60209667A (ja) * 1984-04-02 1985-10-22 Nippon Denso Co Ltd 内燃機関用点火装置
DE3928726A1 (de) * 1989-08-30 1991-03-07 Vogt Electronic Ag Zuendsystem mit stromkontrollierter halbleiterschaltung
DE4409985A1 (de) * 1994-03-23 1995-09-28 Daug Deutsche Automobilgesells Wechselstromzündung mit optimierter elektronischer Schaltung

Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0596471A2 (de) * 1992-11-04 1994-05-11 VOGT electronic AG Wechselstromzündsystem für Verbrennungskraftmaschinen mit Regelung der Zündenergie

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2988233A1 (fr) * 2012-03-16 2013-09-20 Renault Sa Allumage radiofrequence de moteur de vehicule automobile

Also Published As

Publication number Publication date
JPH07279803A (ja) 1995-10-27
DE59500964D1 (de) 1997-12-18
US5506478A (en) 1996-04-09
EP0674102A2 (de) 1995-09-27
DE4409984B4 (de) 2004-05-06
ES2113132T3 (es) 1998-04-16
JP3834761B2 (ja) 2006-10-18
EP0674102A3 (de) 1996-01-10
DE4409984A1 (de) 1995-09-28

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