CN104901432B - 无线电力发射中的自适应阻抗调谐 - Google Patents
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- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
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Abstract
本申请涉及无线电力发射中的自适应阻抗调谐。示范性实施例是针对无线电力。无线电力接收器包括接收天线，所述接收天线用于在由在谐振频率下操作的发射天线产生的耦合模式区中与近场辐射耦合。所述接收天线在耦合到所述近场辐射时产生RF信号，且整流器将所述RF信号转换成DC输入信号。耦合到所述DC输入信号的直流‑直流DC‑DC转换器产生DC输出信号。脉冲调制器产生到所述DC‑DC转换器的脉宽调制信号，以通过响应于所述DC输入信号的电压、所述DC输入信号的电流、所述DC输出信号的电压和所述DC输出信号的电流中的至少一者而修改所述脉宽调制信号的工作循环来调整所述无线电力接收器的DC阻抗。
Description
本申请为发明名称为“无线电力发射中的自适应阻抗调谐”的原中国发明专利申请的分案申请。原申请的中国申请号为201080016833.7；原申请的申请日为2010年3月22号，其国际申请号为PCT/US2010/028189。
根据35U.S.C.§119主张优先权
本申请案根据35U.S.C.§119(e)主张以下各申请案的优先权：
2009年3月20日申请的标题为“无线电力阻抗控制(WIRELESS POWER IMPEDANCECONTROL)”的美国临时专利申请案61/162,157，和
2009年5月7日申请的标题为“基于DC的自适应调谐(DC-BASED ADAPTIVETUNING)”的美国临时专利申请案61/176,468。
技术领域
本发明大体上涉及无线电力传递，且更具体来说，涉及与自适应地调谐接收器装置中的阻抗以改进无线电力传递有关的装置、系统和方法。
背景技术
通常，每一电池供电装置(例如，无线电子装置)需要其自身的充电器和电源，所述电源通常为交流电(AC)电源引出线。当许多装置需要充电时，此类有线配置变得使用不便。
正在开发在发射器与耦合到待充电的电子装置的接收器之间使用空中或无线电力发射的方法。一般将此些方法分为两个种类。一类是基于在发射天线与待充电的装置上的接收天线之间的平面波辐射(还称作远场辐射)的耦合，接收天线收集所辐射的电力且将其整流以用于对电池进行充电。天线一般具有谐振长度以便改进耦合效率。此方法遭遇以下事实：电力耦合随天线之间的距离而快速衰减。因此，在合理距离(例如，小于1到2米)上的充电变得困难。另外，由于发射系统辐射平面波，因此如果未经由滤波进行适当控制，则无意的辐射可干扰其它系统。
用于无线能量发射技术的其它方法是基于嵌入于(例如)“充电”垫或表面中的发射天线与嵌入于待充电的电子装置中的接收天线(加上整流电路)之间的感应耦合。此方法具有发射天线与接收天线之间的间距必须非常靠近(例如，千分之几米内)的缺点。虽然此方法确实具有同时对同一区域中的多个装置充电的能力，但此区域通常非常小且需要用户将装置准确地定位到特定区域中。
在无线电力传递系统中，归因于无线电力发射过程中发生的损耗，效率较为重要。由于无线电力发射通常比有线传递效率低，因此在无线电力传递环境中效率受到更多关注。
结果，当试图将电力提供到一个或一个以上无线充电装置时，需要适应发射天线与接收天线之间的耦合的改变以优化或以其它方式调整向耦合到接收天线的接收器装置递送的电力的方法和设备。
发明内容
在一个新颖方面中，提供一种无线电力接收器。所述接收器包含天线，其包含具有谐振电路阻抗的谐振电路，所述天线经配置以从无线电力发射器接收无线电力信号；整流器，其耦合到天线，所述整流器经配置以将所述无线电力信号转换成直流输入信号，所述直流输入信号具有电压信号和电流信号；直流-直流转换器，其具有直流阻抗，所述直流-直流转换器经配置以至少部分地基于所述直流输入信号而产生直流输出信号，且经配置以至少部分地基于控制信号而调整所述直流阻抗，所述谐振电路阻抗响应于所述直流-直流转换器的所述直流阻抗的调整；以及电路，其经配置以至少部分地基于所述直流输入信号的所述电压信号或所述电流信号中的一者而调整所述控制信号。
在另一新颖方面中，提供一种无线地接收功率的方法。所述方法包括在无线电力接收器处接收来自无线电力发射器的无线电力信号，所述无线电力接收器包括具有谐振电路阻抗的谐振电路；将所述无线电力信号整流成直流输入信号；将所述直流输入信号转换成直流输出信号；以及部分基于所述直流输入信号来调整所述直流输出信号的功率输出，以修改所述谐振电路阻抗并调整所述无线电力接收器的接收带宽。
在又一新颖方面中，提供一种无线电力接收器。所述接收器包含用于从无线电力发射器接收无线电力信号的装置，该接收装置具有谐振阻抗；用于将所述无线电力信号整流成直流输入信号的装置；用于将所述直流输入信号转换成直流输出信号的装置；以及用于修改所述接收装置的交流阻抗的装置，其包含用于至少部分地基于所述直流输入信号来调整所述用于至少部分地基于所述直流输入信号将所述直流输入信号转换成直流输出信号的装置的输入直流阻抗以修改所述谐振阻抗的装置。
附图说明
图1展示无线电力传递系统的简化方框图。
图2展示无线电力传递系统的简化示意图。
图3展示用于在本发明的示范性实施例中使用的环形天线的示意图。
图4为根据本发明的一示范性实施例的发射器的简化方框图。
图5为根据本发明的一示范性实施例的接收器的简化方框图。
图6展示发射电路和接收电路的示意图，其展示其间的耦合和可调整的DC负载。
图7A到图7B展示史密斯图表，其说明响应于接收器装置处的DC阻抗的改变而产生的耦合线圈对的输入阻抗的改变。
图8A到图8B展示振幅曲线，其展示耦合线圈对之间的响应于接收器装置处的DC阻抗的改变的经改进耦合。
图9A到图9B展示接收器装置的简化示意图，其说明用于调整接收器装置处的DC阻抗的示范性实施例。
图10A到图10D展示接收器装置的简化示意图，其说明用于使用脉宽调制转换器来调整接收器装置处的DC阻抗的示范性实施例。
图11说明在调整接收器装置处的DC阻抗时可使用的各种输入和输出参数。
具体实施方式
在本文中使用词语“示范性”以指“充当一实例、例子或说明”。本文中描述为“示范性”的任何实施例没有必要被解释为比其它实施例优选或有利。
下文结合附图所陈述的详细描述意欲作为对本发明的示范性实施例的描述，且无意表示可实践本发明的仅有实施例。在整个此描述中所使用的术语“示范性”是指“用作一实例、例子或说明”，且应没有必要被解释为比其它示范性实施例优选或有利。所述详细描述出于提供对本发明的示范性实施例的彻底理解的目的而包括特定细节。所属领域的技术人员将容易明白，可在无这些特定细节的情况下实践本发明的示范性实施例。在一些例子中，以方框图形式展示众所周知的结构和装置，以便避免使本文中所呈现的示范性实施例的新颖性模糊不清。
在本文中使用词语“无线电力”以指在不使用物理电磁导体的情况下在从发射器到接收器之间发射的与电场、磁场、电磁场或其它物相关联的任何形式的能量。
图1说明根据本发明的各种示范性实施例的无线发射或充电系统100。将输入电力102提供到发射器104以用于产生用于提供能量传递的辐射场106。接收器108耦合到辐射场106，且产生输出电力110以供耦合到输出电力110的装置(未图示)存储或消耗。发射器104与接收器108两者相隔一距离112。在一个示范性实施例中，根据相互谐振关系来配置发射器104与接收器108，且当接收器108位于辐射场106的“近场”中时，当接收器108的谐振频率与发射器104的谐振频率非常接近时，发射器104与接收器108之间的发射损耗为最小。
发射器104进一步包括用于提供用于能量发射的装置的发射天线114，且接收器108进一步包括用于提供用于能量接收的装置的接收天线118。根据应用和将与其相关联的装置来设计发射天线和接收天线的大小。如所陈述，通过将发射天线的近场中的大部分能量耦合到接收天线而非以电磁波形式将大部分能量传播到远场而进行有效能量传递。当处于此近场中时，可在发射天线114与接收天线118之间形成耦合模式。天线114和118周围的可发生此近场耦合的区域在本文中称作耦合模式区。
图2展示无线电力传递系统的简化示意图。发射器104包括振荡器122、功率放大器124以及滤波器和匹配电路126。所述振荡器经配置以产生所要频率，所述所要频率可响应于调整信号123来调整。振荡器信号可由功率放大器124以响应于控制信号125的放大量来放大。可包括滤波器和匹配电路126以滤除谐波或其它非所要的频率且使发射器104的阻抗与发射天线114匹配。
接收器108可包括匹配电路132以及整流器和切换电路134以产生DC电力输出来对电池136(如图2中所展示)进行充电或向耦合到接收器的装置(未图示)供电。可包括匹配电路132以使接收器108的阻抗与接收天线118匹配。接收器108与发射器104可在单独通信信道119(例如，蓝牙、zigbee、蜂窝式等)上通信。
如图3中所说明，示范性实施例中所使用的天线可经配置为“环形”天线150，其在本文中还可称作“磁性”天线。环形天线可经配置以包括空气芯或物理芯(例如，铁氧体芯)。空气芯环形天线可能更可容许放置于所述芯附近的外来物理装置。此外，空气芯环形天线允许其它组件放置于芯区域内。另外，空气芯环可更容易实现接收天线118(图2)在发射天线114(图2)的平面内的放置，在所述平面中，发射天线114(图2)的耦合模式区可更强大。
如所陈述，在发射器104与接收器108之间的匹配或几乎匹配的谐振期间发生发射器104与接收器108之间的有效能量传递。然而，甚至当发射器104与接收器108之间的谐振不匹配时，还可以较低效率传递能量。通过将来自发射天线的近场的能量耦合到驻留于建立了此近场的邻域中的接收天线而非将能量从发射天线传播到自由空间中而发生能量的传递。
环形天线或磁性天线的谐振频率是基于电感和电容。环形天线中的电感一般仅为由所述环形产生的电感，而一般将电容添加到环形天线的电感以在所要谐振频率下产生谐振结构。作为非限制性实例，可将电容器152和电容器154添加到天线以产生产生谐振信号156的谐振电路。因此，对于较大直径的环形天线来说，诱发谐振所需的电容的大小随着环形天线的直径或电感增加而减小。此外，随着环形天线或磁性天线的直径增加，近场的有效能量传递区域增加。当然，其它谐振电路是可能的。作为另一非限制性实例，电容器可并联地放置于环形天线的两个端子之间。另外，所属领域的技术人员将认识到，对于发射天线，谐振信号156可为到环形天线150的输入。
本发明的示范性实施例包括在处于彼此的近场中的两个天线之间耦合电力。如所陈述，近场为在天线周围的存在电磁场但可能并不远离所述天线传播或辐射的区域。所述电磁场通常被限于所述天线的物理体积附近的体积。在本发明的示范性实施例中，磁型天线(例如，单匝环形天线和多匝环形天线)用于发射(Tx)天线系统与接收(Rx)天线系统两者，这是因为与电型天线(例如，小型偶极天线)的电近场相比，磁型天线的磁近场振幅往往较高。此允许所述对天线之间的潜在较高耦合。此外，还预期“电”天线(例如，偶极天线和单极天线)或磁性天线与电天线的组合。
Tx天线可在足够低的频率下且在天线大小足够大的情况下操作，以在显著大于早先所提及的远场和电感性方法所允许的距离的距离下实现到小型接收天线的良好耦合(例如，>-4dB)。如果发射天线的大小经正确设计，则当将主机装置上的接收天线放置于受驱动发射环形天线的耦合模式区内(即，在近场中)时，可实现高耦合水平(例如，-1到-4dB)。
图4为根据本发明的示范性实施例的发射器200的简化方框图。发射器200包括发射电路202和发射天线204。通常，发射电路202通过提供导致产生围绕发射天线204的近场能量的振荡信号来将RF电力提供到发射天线204。举例来说，发射器200可在13.56MHz ISM频带下操作。
示范性发射电路202包括：固定阻抗匹配电路206，其用于将发射电路202的阻抗(例如，50欧姆)与发射天线204匹配；以及低通滤波器(LPF)208，其经配置以将谐波发射减少到防止耦合到接收器108(图1)的装置的自干扰的水平。匹配电路的其它示范性实施例可包括电感器和变压器。低通滤波器的其它示范性实施例可包括不同滤波器拓扑(包括(但不限于)使特定频率衰减同时使其它频率通过的陷波滤波器)，且可包括自适应阻抗匹配，其可基于可测量的发射度量(例如，到天线的输出功率或由功率放大器汲取的DC电流)而变化。发射电路202进一步包括功率放大器210，其经配置以驱动如由振荡器212(本文中还称作信号产生器)确定的RF信号。发射电路可包含离散装置或电路，或者可包含集成组合件。来自发射天线204的示范性RF功率输出可为约2.5到8.0瓦。
发射电路202进一步包括控制器214，控制器214用于在针对特定接收器的发射阶段(或工作循环)期间启用振荡器212，以用于调整所述振荡器的频率，且用于调整输出功率水平来实施用于经由相邻装置所附接的接收器与相邻装置交互的通信协议。控制器214还用于确定在发射天线204处的归因于耦合模式区的改变而引起的阻抗改变，耦合模式区的改变是归因于放置于其中的接收器。
发射电路202可进一步包括负载感测电路216，其用于检测在由发射天线204产生的近场附近的有效接收器的存在或不存在。举例来说，负载感测电路216监视流动到功率放大器210的电流，所述电流受在由发射天线204产生的近场附近的有效接收器的存在或不存在影响。由控制器214监视对功率放大器210上的加载的改变的检测，以用于确定是否启用振荡器212来用于发射能量以与有效接收器通信。
可将发射天线204实施为天线带，其具有经选择以使电阻性损耗保持较低的厚度、宽度和金属类型。在常规实施方案中，发射天线204可一般经配置以与较大结构(例如，桌子、垫子、灯或其它较不便携的配置)相关联。因此，发射天线204一般将不需要“若干匝”以便具有实用尺寸。发射天线204的示范性实施方案可为“电学上较小的”(即，波长的分数)且经调谐以通过使用电容器界定谐振频率而在较低的可用频率下谐振。在发射天线204相对于接收天线来说在直径上或边长上(如果为正方形环)可能较大(例如，0.50米)的示范性应用中，发射天线204将不一定需要大量匝来获得合理电容，以便使发射天线在所要频率下谐振。。
发射器200可搜集和追踪关于可与发射器200相关联的接收器装置的行踪和状态的信息。因此，发射器电路202可包括连接到控制器214(在本文中还称作处理器)的存在检测器280、封闭式检测器290，或其组合。控制器214可响应于来自存在检测器280和封闭式检测器290的存在信号而调整由放大器210递送的功率的量。发射器可经由许多电源接收电力，所述电源例如为用以转换存在于建筑物中的常规AC电力的AC-DC转换器(未图示)、用以将常规DC电源转换成适合于发射器200的电压的DC-DC转换器(未图示)，或发射器可直接从常规DC电源(未图示)接收电力。
作为一非限制性实例，存在检测器280可为运动检测器，其用以感测插入到发射器的覆盖区域中的待充电的装置的初始存在。在检测后，可开启发射器且可使用由装置接收的RF电力来以预定方式切换接收器装置上的开关，其又导致发射器的驱动点阻抗的改变。
作为另一非限制性实例，存在检测器280可为检测器，其能够(例如)通过红外线检测、运动检测或其它合适手段来检测人类。在一些示范性实施例中，可能存在限制发射天线可在特定频率下发射的功率的量的规章。在一些情况下，这些规章有意保护人类免受电磁辐射影响。然而，可能存在发射天线放置于人类未占用的或人类不经常占用的区域(例如，车库、厂区、车间，等)中的环境。如果这些环境没有人类，则可能可准许将发射天线的功率输出增加到正常功率约束规章以上。换句话说，控制器214可响应于人类存在而将发射天线204的功率输出调整去往管制水平或更低水平，且当人类在距发射天线204的电磁场管制距离之外时，将发射天线204的功率输出调整去往高于管制水平的水平。此外，存在检测器280可为能够检测放置于发射天线的区域中的对象的检测器。当不打算接收无线电力且可能会被磁场损坏的对象放置于发射天线附近时，此检测可用于减少或停止电力输出。
作为一非限制性实例，封闭式检测器290(在本文中还可称作封闭式隔间检测器或封闭式空间检测器)可为例如感测开关的装置，以用于确定外罩何时处于闭合或打开状态中。当发射器在处于封闭状态的外罩中时，可增加发射器的功率水平。
在示范性实施例中，可使用发射器200借以不会无限地保持开启的方法。在此情况下，发射器200可经编程以在用户确定的时间量后关闭。此特征防止发射器200(尤其是功率放大器210)在其周边的无线装置充满后长时间运行。此事件可能归因于用以检测从中继器或接收线圈发送的指示装置充满的信号的电路的故障。为了防止发射器200在另一装置放置于其周边时自动关闭，可仅在检测到其周边缺少运动的设定周期后启动发射器200自动关闭特征。用户可能够确定不活动时间间隔，且在需要时改变所述不活动时间间隔。作为一非限制性实例，所述时间间隔可比在假定特定类型的无线装置最初完全放电的情况下充满所述装置所需的时间间隔长。
图5为根据本发明的示范性实施例的接收器300的简化方框图。接收器300包括接收电路302和接收天线304。接收器300进一步耦合到装置350以用于将所接收的电力提供到装置350。应注意，将接收器300说明为在装置350外部，但其可集成到装置350中。通常，能量无线地传播到接收天线304且接着经由接收电路302而耦合到装置350。
接收天线304经调谐以在与发射天线204(图4)的频率相同的频率下或接近相同的频率下谐振。接收天线304可与发射天线204类似地设计尺寸，或可基于相关联装置350的尺寸来不同地设计大小。举例来说，装置350可为具有比所述发射天线204的直径或长度小的直径或长度尺寸的便携式电子装置。在此种实例中，可将接收天线304实施为多匝天线，以便减小调谐电容器(未图示)的电容值且增加接收天线的阻抗。举例来说，接收天线304可放置于装置350的实质性圆周周围，以便使天线直径最大化并减少接收天线的环匝(即，线圈)的数目和线圈间电容。
接收电路302提供与接收天线304的阻抗匹配。接收电路302包括电力转换电路306，其用于将所接收的RF能源转换成供装置350使用的充电电力。电力转换电路306包括RF-DC转换器308且还可包括DC-DC转换器310。RF-DC转换器308将在接收天线304处所接收的RF能量信号整流成非交变电力，而DC-DC转换器310将经整流的RF能量信号转换成与装置350兼容的能量电位(例如，电压)。预期各种RF-DC转换器，包括部分和全整流器、调节器、桥接器、倍增器以及线性和切换转换器。
接收电路302可进一步包括切换电路312，以用于将接收天线304连接到电力转换电路306或者用于断开电力转换电路306。将接收天线304与电力转换电路306断开不仅中止对装置350的充电，而且还改变发射器200(图2)所“看到”的“负载”，其可用以“遮盖”接收器而不被发射器看到。
如上文所揭示，发射器200包括负载感测电路216，负载感测电路216检测提供到发射器功率放大器210的偏置电流的波动。因此，发射器200具有用于确定接收器何时存在于发射器的近场中的机制。
当多个接收器300存在于发射器的近场中时，可能需要对一个或一个以上接收器的加载和卸载进行时间多路复用以使其它接收器能够更有效地耦合到发射器。还可遮盖一接收器以便消除到其它附近接收器的耦合或减少附近发射器上的加载。接收器的此“卸载”在本文中还称为“遮盖”。此外，如下文更完全地解释，由接收器300控制且由发射器200检测的卸载与加载之间的此切换提供从接收器300到发射器200的通信机制。另外，一协议可与所述切换相关联，所述协议使得能够将消息从接收器300发送到发射器200。举例来说，切换速度可为约100微秒。
在一示范性实施例中，发射器与接收器之间的通信涉及装置感测和充电控制机制而非常规双向通信。换句话说，发射器使用所发射信号的开/关键控，以调整近场中的能量是否可用。接收器将这些能量改变解译为来自发射器的消息。从接收器侧，接收器使用接收天线的调谐与解谐来调整正从近场接受多少电力。发射器可检测来自近场的所使用的电力的此差异，且将这些改变解译为来自接收器的消息。
接收电路302可进一步包括用以识别所接收的能量波动的信令检测器和信标电路314，所述能量波动可对应于从发射器到接收器的信息性信令。此外，信令和信标电路314还可用以检测减少的RF信号能量(即，信标信号)的发射并将所述减少的RF信号能量整流成标称电力，以用于唤醒接收电路302内的未供电或电力耗尽的电路，以便配置接收电路302来用于无线充电。
接收电路302进一步包括处理器316，以用于协调本文中所描述的接收器300的处理(包括对本文中所描述的切换电路312的控制)。还可在其它事件(包括检测到将充电电力提供到装置350的外部有线充电源(例如，壁式/USB电力))发生后即刻发生对接收器300的遮盖。除了控制对接收器的遮盖外，处理器316还可监视信标电路314以确定信标状态并提取从发射器发送的消息。处理器316还可调整DC-DC转换器310以获得改进的性能。
在一些示范性实施例中，接收电路320可以(例如)所要功率电平、最大功率电平、所要电流电平、最大电流电平、所要电压电平和最大电压电平的形式将功率要求用信号发送到发射器。基于这些电平和从发射器接收的实际功率量，处理器316可调整DC-DC转换器310的操作以按调整电流电平、调整电压电平或其组合的形式来调节其输出。
本发明的示范性实施例是针对电路和调整机制，其允许以可补偿发射天线与接收天线之间的耦合效应的改变的方式调整端接接收器装置的接收天线的负载阻抗。
用于调整负载阻抗的电流方案是基于RF组件的使用。这些RF组件包括基于以下各者的调谐器：可切换固定电容器和电感器、电压可变电容器(例如，铁电、微机电系统(MEMS)和变容二极管)。可切换固定电容器和电感器方法可能具有过多的欧姆损耗而对于充电系统是不实用的。基于铁电装置和MEMS电压可变电容器的可变调谐器此时可能在商业上不可行。基于变容二极管的调谐器可能不能处置无线电力应用中所预期的RF电力。
如上文所描述，无线充电系统通常包括发射天线(即，发射耦合线圈)，所述发射天线将RF能量发射到一个或一个以上接收天线(即，接收耦合线圈)，所述一个或一个以上接收天线嵌入于待充电或以其它方式供应有电力的接收器装置中。对所接收到的能量进行整流、调节，并将其递送到装置的电池或其它操作电路。这些天线通常在低频率下操作，其中所述天线在电学上为小型的以便以磁性方式耦合而不辐射电力。
当两个线圈谐振时(即，当两者均调谐到用以将电力从一个天线传递到另一天线的频率时)，这些小型天线可实现较佳的耦合效率。遗憾的是，尽管有效电力传递为任何无线电力传递方案的重要方面，但使用小型且以谐振方式耦合的天线的副作用在于：所得带宽有时相当小，从而使天线易受去谐和效率可能易大幅损耗。使用小型松耦合谐振天线的另一问题在于：在接收天线相对于发射天线在周围移动(例如，在充电垫上的不同位置处)时，或当待充电的多个装置彼此靠近地放置于充电垫上时，两个天线之间的相互耦合将变化。这些放置变化将改变发射线圈与接收线圈之间的耦合且导致在发射天线处所看到的阻抗的变化，从而导致充电系统中发射天线与接收天线之间的低效电力传递。通过改变呈现给接收天线的RF负载电阻，这些问题中的许多可得以校正或至少在很大程度上得以减少。
在改变RF负载电阻以便影响发射放大器所看到的阻抗的改变的过程中，众所周知，视在发射天线和接收天线处使用的匹配电路而定，电源所看到的此阻抗可以电阻方式、以电抗方式或其组合来变化。为最大化系统的效率，最好仅改变实值(即，电阻性值)且使此输入阻抗的电抗值尽可能保持恒定。尽管有可能补偿电抗性改变，但此可能极大地增加整个系统的复杂性。可展示，存在一个匹配电路，其可在电阻性负载变化的任何范围内满足最大电力传递的目标。所述匹配电路可为经调谐(谐振)变压器，其仅为用以传递电力的谐振发射天线和谐振接收天线的延伸部分。在以下论述中，假定使用此形式的匹配电路。
图6展示发射电路和接收电路的示意图，其展示了其间的耦合和可调整的DC负载450。如图6中所展示，充电系统405可由耦合线圈变压器模型430表征，其中发射器电子器件连接到主线圈432(即，发射天线)，且接收器侧上的整流器/调节器电子器件连接到次线圈434(即，接收天线)。
驱动器410在所要谐振频率(例如，约13.56MHz)下产生振荡信号。作为一个实例，此驱动器41可配置为如图6中所说明的E类驱动器。低通匹配电路420对来自驱动器410的信号进行滤波且使所述信号与耦合线圈变压器模型430的发射天线432阻抗匹配。
经由近场辐射将能量传递到耦合线圈变压器模型430的接收天线434。耦合到接收天线434的振荡信号耦合到阻抗匹配和整流器电路440，以为接收天线434提供AC阻抗匹配且将所述振荡信号整流成实质上DC信号。DC-DC转换器450将来自整流器440的DC信号转换成可由接收器装置(未图示)上的电路使用的DC输出。DC-DC转换器450还经配置以调整整流器440所看到的DC阻抗，其又调整去往整流器440的输入的总AC阻抗。结果，在DC-DC转换器450的输入处的DC阻抗的改变可产生与接收天线434的阻抗的较佳匹配，和接收天线434与发射天线432之间的较佳相互耦合。
变压器模型430的自感(Ltx和Lrx)、互感(m)和损耗电阻可从天线对的所测量或所模拟的耦合特性导出。
可展示，给定互感(m)和电阻性损耗(发射天线和接收天线分别为R1和R2)，对于接收天线，存在将最大化电力传递效率的最佳负载。此最佳负载可被界定为：
Reff＝R1*[1+(Ω*m)2/(R1*R2)]5。
通常，Reff可在1欧姆到20欧姆的范围中。通过使用DC负载控制，由于互感(m)因上文所描述的原因而变化，可将接收线圈434所看到的RF负载设定为其最有效值。
控制RF负载的另一使用在于：可使用负载的变化来控制递送到接收器装置的电力。此可能以一定的效率为代价，但使得在服务处于各种充电状态下的无线装置的混合物时能够最大程度地使用可用电力。
控制RF负载的又一使用在于：可使用负载的变化来加宽传递功能的带宽，其结果取决于极低阻抗或电抗性阻抗的发射功率放大器410(典型为无线改变放大器)与发射天线432之间的匹配网络420。如果输入匹配电路包括第三经调谐电感(未图示)(其与TX天线432相互耦合)，则此带宽调整可在互感(m)和负载变化较大的范围内最佳地工作。在此情况下，如果功率放大器具有极低的源阻抗，则带宽将随着RF负载电阻增加而线性地增加。
现有无线充电系统看似无关于带宽，因为FCC所允许的信号带宽相当小。如之前所陈述，改变负载以加宽带宽可使效率从其最大值略有减小，但当可能需要增加的带宽时，此可用于维持功能性充电系统。虽然在需要高效率的无线充电过程中不是实质上合意的选项，但此带宽扩展效应可应用于效率并不重要的短程通信系统中。
使用与发射天线432相互耦合的低电感提供优于较普遍的被动匹配的显著系统优点。此输入串联经调谐的DC-DC转换器450引起第二阻抗反转，第一阻抗反转是在发射天线与接收天线(432与434)之间。结果，当负载阻抗增加时，输入阻抗增加。此仅通过升高接收器的负载阻抗来允许负载“遮盖”接收器使发射器看不到接收器。此效应可重新陈述为使输入电导为负载电导的线性函数。
在无此遮盖特征的情况下，来自接收器的负载将会呈现短路以便进行遮盖，其使用例如上文参看图5所论述的元件312等机构。结果，不存在接收器装置的充电垫将表现为经高度调谐的短路而非开路。此外，当存在多个未经遮盖的负载时，发射天线432的总输入电导将为接收天线434的个别电导的总和，且将根据其相对值来分配电力。
经调谐输入变压器匹配的又一优点在于：所得输入/输出导纳在中心(谐振)频率下为实数，且相对于频率是“平”顶的。因此，电路参数的一阶变化对电力传递过程的影响较小。
图7A到图7B展示史密斯图表，其说明响应于接收器装置处的DC阻抗的改变而产生的耦合线圈对(不添加电感匹配)的输入阻抗的改变。在图7A和图7B中，加粗圆510和520分别指示恒定电阻圆。
参看图7A和图6，在DC-DC转换器450的输入处约10.2欧姆的DC阻抗Rdc产生发射天线432处约50欧姆的复合输入阻抗，和极小的电抗。参看图7B和图6，在DC-DC转换器450的输入处约80欧姆的DC阻抗Rdc产生发射天线432处远小于50欧姆的复合输入阻抗，和极小的电抗。
图8A和图8B展示振幅曲线(分别为530和540)，其展示耦合线圈对之间的响应于接收器装置处的DC阻抗的改变的经改进耦合。在图8A中，中心频率13.56MHz处的振幅为约-4.886dB。在调整DC-DC转换器450(图6)的输入阻抗之后，中心频率13.56MHz处的振幅改进到约-3.225dB，从而产生接收天线与发射天线之间的较佳耦合，其使得更多电力被传递到接收天线。
图9A到图9B展示接收器装置的简化示意图，其说明用于调整接收器装置处的DC阻抗的示范性实施例。在图9A和图9B两者中，接收天线304对包括电容器C1和C2的示范性阻抗匹配电路320进行馈送。来自阻抗匹配电路320的输出对包括二极管D1和D2以及电容器C3的简单整流器330(作为一个实例)进行馈送，以用于将RF频率转换成DC电压。当然，预期许多其它阻抗匹配电路320和整流器330处于本发明的实施例的范围内。DC-DC转换器350将来自整流器的DC输入信号340转换成适合于由接收器装置(未图示)使用的DC输出信号370。
图9A说明一种用于维持无线电力发射系统中的最佳功率点阻抗的简单设备。比较器348比较DC输入信号340与参考电压345，所述参考电压345经选择以使得对于给定预期功率，由发射器看到的阻抗将产生耦合到DC输出信号370的最大量的功率。比较器348的输出361向DC-DC转换器350馈送一信号以指示DC-DC转换器350应增加还是减小其输入DC阻抗。在使用切换DC-DC转换器350的实施例中，比较器的此输出361可被转换成脉宽调制(PWM)信号，所述PWM信号调整所述输入DC阻抗(如下文所解释)。此输入电压反馈电路通过随着电压增加而增加PWM脉宽来调节输入DC阻抗，因此减小阻抗和电压。
图9B说明一种用于维持无线电力发射系统中的最佳功率点阻抗的略微更复杂的设备。在图9B中，可包括电流传感器344，且可使用多路复用器346来切换在任何给定时间由处理器360对DC输入信号340处的电压还是电流进行取样。在此系统中，测量DC输入信号340的电压(Vr)和电流(Ir)，且到DC-DC转换器350的PWM信号362可在预先允许的范围内变化。处理器360可确定对于PWM信号362来说哪一脉宽产生最大功率(即，电流乘以电压)，所述最大功率指示最佳DC输入阻抗。所确定的此脉宽可用于将最佳量的电力传递到DC输出信号370的操作。此取样和调整过程可在需要时随时重复，以追踪改变的耦合比、发射功率或发射阻抗。
如早先所陈述，为了从具有有限输出电阻或阻抗的源获得最大外部功率，接收器的电阻或阻抗应与电源的电阻或阻抗相同。在许多情况下，需要操作无线电力系统以便最大化所接收到的功率，以便最佳地使用有限的RF电源。
此最大化的功率传递并非总是与最大效率相同。在许多情况下，操作在较高(而非相等)的阻抗或电阻下的负载以便增加系统的效率可为有利的。然而，在任一情况下，维持接收器处的特定阻抗对于调节在发射器与接收器之间传递的功率的量可为有用的。
在简单无线电力系统中，可能不存在对输入阻抗的控制；输出负载(通常为电池或无线装置)可能为系统的阻抗的仅有驱动器。此导致次最佳的发射器/接收器阻抗匹配，和随之的电力传递、效率或其组合的损耗。
DC阻抗由(电压/电流)界定。因此，在任何给定电流和所要阻抗下，存在：所要电压＝(电流*所要阻抗)。通过PWM转换器，可通过提供反馈项而实现此所要电压(且因而实现所要阻抗)，所述反馈项比较输入电压与(电流*所要阻抗)项，且向上或向下调整脉宽以维持那个项。
图10A到图10D展示接收器装置的简化示意图，其说明用于使用脉宽调制转换器来调整接收器装置处的DC阻抗的示范性实施例。在图10A到图10D中，共同元件包括对阻抗匹配电路320进行馈送的接收天线304。来自阻抗匹配电路320的输出对简单整流器(其简单地展示为二极管D3)进行馈送。当然，预期许多其它阻抗匹配电路320和整流器处于本发明的实施例的范围内。DC-DC转换器350将来自整流器的DC输入信号340转换成适合于由接收器装置(未图示)使用的DC输出信号370。处理器360对DC输入信号340、DC输出信号270或其组合的参数进行取样，且产生用于DC-DC转换器350的PWM信号362。
DC-DC转换器350为切换模式转换器，其中PWM信号362控制开关S1以周期性地对滤波电路进行充电，所述滤波电路包括二极管D4、电感器L1和电容器C4。所属领域的技术人员将认识到DC-DC转换器350为降压式转换器，其将DC输入信号340上的电压转换成DC输出信号370上的较低电压。尽管未图示，但所属领域的技术人员还将认识到，切换模式DC-DC转换器350还可实施为升压式转换器，以产生电压高于DC输入信号340上的电压的DC输出信号370。
在大多数情况下，对调节无线电力接收器的输出电压的要求将最为重要。举例来说，对于电池充电，不超过最大输出电流或最大输出电压常常最为关键。这意味着输出电压控制项常常将支配PWM信号362的脉宽的控制规则。
然而，在许多情况下，电池将在定额小于其最大定额的情况下接受电力。作为一实例，在定额小于锂离子电池的额定容量的情况下对锂离子电池进行充电期间，电压将在最大电池电压以下，且电流可受可从无线电力系统得到的最大功率限制。在这些情况期间，二次阻抗-控制项在调整PWM信号的脉宽以便控制DC阻抗方面将变得处于支配地位。
本发明的示范性实施例通过在切换模式DC-DC转换器350中使用反馈项以有效地模拟接收器中的稳态DC电阻来提供DC阻抗控制。换句话说，通过调整去往达切换模式DC-DC转换器350的PWM信号362的频率或工作循环以模拟给定DC阻抗来控制DC阻抗。
通过由处理器360对DC输入信号340、DC输出信号370或其组合的一个或一个以上特性进行取样来产生对系统的反馈。处理器360接着使用此经取样的信息(有可能连同其它信息，例如DC-DC转换器350的预期功率传递和效率)来调整PWM信号362，此调整DC输入信号和DC输出信号以闭合反馈环路。
参考如图10A到10D所说明的四个不同示范性实施例来论述所取样的内容和产生PWM信号的参数的方式的个别差异。
在图10A中，处理器360对DC输入信号340的电压、DC输入信号340的电流、DC输出信号370的电压和DC输出信号370的电流进行取样。
在一些实施例中，可在DC输入信号340与处理器360之间使用电压传感器342。类似地，可在DC输出信号370与处理器360之间使用电压传感器372。在其它实施例中，可不需要电压传感器342和372，且处理器460可直接对DC输入信号340和DC输出信号370上的电压进行取样。
在一些实施例中，可在DC输入信号340与处理器360之间使用电流传感器344。类似地，可在DC输出信号370与处理器360之间使用电流传感器374。在其它实施例中，可不需要电流传感器344和374，且处理器360可直接对DC输入信号340和DC输出信号370上的电流进行取样。
通过对DC输入信号340和DC输出信号370两者的电流和电压测量，处理器360可确定电力转换系统所需的所有参数。DC输入信号340上的输入功率可确定为输入电压乘以输入电流。DC输出信号370上的输出功率可确定为输出电压乘以输出电流。DC-DC转换器350的效率可确定为输出功率与输入功率之间的差。DC输入信号340的DC阻抗可确定为输入电压除以输入电流。
处理器360可周期性地对所有输入进行取样(例如，约每秒一次，或其它合适周期)，以确定那个时间的功率输出。作为响应，处理器360可改变PWM信号362的工作循环，其将改变DC输入信号340的DC阻抗。举例来说，PWM信号362上的窄脉宽允许输入电压保持相对高且允许输入电流保持相对低，其导致DC输入信号340的较高DC阻抗。相反地，PWM信号362上的较宽脉宽允许从DC输入信号340汲取更多的电流，从而产生DC输入信号340的较低输入电压和较低DC阻抗。
周期性取样和调整产生可找到DC输入信号340的最佳DC阻抗(且因而找到DC输出信号370的最佳功率)的反馈环路。下文参看图11来论述寻找这些值的细节。
在图10B中，处理器360对DC输入信号340的电压、DC输出信号370的电压和DC输出信号370的电流进行取样。如上文参看图10A所解释，电压传感器342、电压传感器372和电流传感器374可视实施例而包括于其相应信号与处理器360之间。
如同图10A，在图10B中，DC输出信号370上的输出功率可确定为输出电压乘以输出电流。在许多情况下，将已知DC-DC转换器350的效率，且其在所要操作范围内相对恒定。因此，处理器360可基于输出功率和对DC-DC转换器350的当前操作点处的效率的估计来估计DC输入信号340的输入功率。通过所估计的输入功率和所测量的输入电压，可确定DC输入信号340的DC阻抗。再次，周期性取样和调整产生可找到DC输入信号340的最佳DC阻抗(且因而找到DC输出信号370的最佳功率)的反馈环路。
在图10C中，处理器360对DC输入信号340的电压和DC输入信号340的电流进行取样。如上文参看图10A所解释，电压传感器342和电流传感器344可视实施例而包括于DC输入信号340与处理器360之间。
在图10C中，DC输入信号340上的输入功率可确定为输入电压乘以输入电流，且DC输入信号340的DC阻抗可确定为输入电压除以输入电流。如同图10B，在图10C中，将已知DC-DC转换器350的效率，且其在所要操作范围内相对恒定。因此，处理器360可基于输入功率和对DC-DC转换器350的当前操作点处的效率的估计来估计DC输出信号370上的输出功率。再次，周期性取样和调整产生可找到DC输入信号340的最佳DC阻抗(且因而找到DC输出信号370的最佳功率)的反馈环路。
在图10D中，处理器360仅对DC输入信号340的电压进行取样。如上文参看图10A所解释，电压传感器342可视实施例而包括于DC输入信号340与处理器360之间。
在图10D中，可就预期经由接收天线和整流器接收且在DC输入信号上递送的功率的量作出预定估计。使用此预定估计，可相对于输入电压确定DC输入信号340的DC阻抗。如同图10B，在图10C中，将已知DC-DC转换器350的效率，且其在所要操作范围内相对恒定。因此，处理器360可基于所述预定输入功率估计和对DC-DC转换器350的当前操作点处的效率的估计来估计DC输出信号370上的输出功率。再次，周期性取样和调整产生可找到DC输入信号340的最佳DC阻抗(且因而找到DC输出信号370的最佳功率)的反馈环路。
所述预定功率估计可为编程于接收器装置中的固定值，或可从发射器装置传送到接收器装置，所述发射器装置可具有用于确定所发射的电力中将有多少电力耦合到那个特定接收器装置的装置。
图11说明在调整接收器装置处的DC阻抗时可使用的各种输入和输出参数。此图表表示具有特定源阻抗的系统，但其中允许负载电阻器在较广范围内变化。此负载电阻器可表示为图6的DC-DC转换器450的可变电阻器。或者，所述负载电阻器可由图9A到图10D中所展示的到DC-DC转换器350的DC输入信号340的DC阻抗表示。
在图11中，在1:1的电源-负载耦合的情况下通过信号来驱动50欧姆的源阻抗。线620展示通过负载电阻器的电流。注意，随着负载阻抗增加，电流归因于欧姆定律而减小。线610展示负载电阻器上的电压。注意，随着负载阻抗增加，电压还按照电阻分压器等分而增加。
针对负载电阻器的电流和电压的这两个数据集给出负载电阻器上的功率(如由线640展示)。注意，功率在某一负载阻抗处达到峰值。在此情况(1:1的负载耦合)下，在负载阻抗等于或接近源阻抗时，此最大功率点出现。如果耦合不同，则峰值功率点还可能有所偏移。
线650表示PWM设定(在100外)，其与输出阻抗成相反关系。此为大多数降压式转换器所展现的函数。如可看到，存在一个理想的PWM设定，其最大化由负载电阻器接收到的功率。参考本文中所论述的示范性实施例而使用的无线电力阻抗控制方案试图发现并维持此理想PWM设定。
当然，如早先所陈述，最佳功率传递并非总是必要的。使用上文在图6和图9A到图10D中所论述的本发明的实施例，可有效地使DC输入信号340的DC阻抗(且因而使接收天线的AC阻抗)与最佳功率传递去谐，以限制在DC输出信号370上递送的功率的量。在接收器装置不可接受可从DC-DC转换器350递送的最大功率的情况下，此功率限制可为有用的。此对减小的功率的需要的一些非限制性实例可出现在接收器装置中的电池接近完全充电或DC-DC转换器350可递送比电池的额定容量更多的电力时。
所属领域的技术人员应理解，可使用多种不同技术和技艺中的任一者来表示信息和信号。举例来说，可通过电压、电流、电磁波、磁场或磁性粒子、光场或光学粒子或其任何组合来表示可在整个上述描述中所参考的数据、指令、命令、信息、信号、位、符号和码片。
所属领域的技术人员应进一步了解，结合本文中所揭示的示范性实施例而描述的各种说明性逻辑块、模块、电路和算法步骤可实施为电子硬件、计算机软件或两者的组合。为了清楚地说明硬件与软件的此互换性，上文已大体上在其功能性方面描述了各种说明性组件、块、模块、电路和步骤。将此功能性实施为硬件还是软件视特定应用和强加于整个系统的设计约束而定。所属领域的技术人员可针对每一特定应用以不同方式实施所描述的功能性，但此些实施决策不应被解释为会导致偏离本发明的示范性实施例的范围。
可用通用处理器、数字信号处理器(DSP)、专用集成电路(ASIC)、现场可编程门阵列(FPGA)或其它可编程逻辑装置、离散门或晶体管逻辑、离散硬件组件或其经设计以执行本文中所描述的功能的任何组合来实施或执行结合本文中所揭示的示范性实施例而描述的各种说明性逻辑块、模块和电路。通用处理器可为微处理器，但在替代方案中，处理器可为任何常规的处理器、控制器、微控制器或状态机。还可将处理器实施为计算装置的组合，例如，DSP与微处理器的组合、多个微处理器、结合DSP核心的一个或一个以上微处理器，或任何其它此类配置。
结合本文中所揭示的示范性实施例而描述的方法或算法的步骤可直接以硬件、以由处理器执行的软件模块，或以所述两者的组合来体现。软件模块可驻留于随机存取存储器(RAM)、快闪存储器、只读存储器(ROM)、电可编程ROM(EPROM)、电可擦除可编程ROM(EEPROM)、寄存器、硬盘、可装卸磁盘、CD-ROM或此项技术中已知的任何其它形式的存储媒体中。将示范性存储媒体耦合到处理器，以使得所述处理器可从所述存储媒体读取信息，并可将信息写入到所述存储媒体。在替代方案中，存储媒体可与处理器成一体式。处理器和存储媒体可驻留于ASIC中。ASIC可驻留于用户终端中。在替代方案中，处理器和存储媒体可作为离散组件而驻留于用户终端中。
在一个或一个以上示范性实施例中，可以硬件、软件、固件或其任何组合来实施所描述的功能。如果以软件来实施，则可将所述功能作为一个或一个以上指令或代码而存储于计算机可读媒体上或经由计算机可读媒体进行传输。计算机可读媒体包括计算机存储媒体与通信媒体两者，通信媒体包括促进将计算机程序从一处传递到另一处的任何媒体。存储媒体可为可由计算机存取的任何可用媒体。以实例且非限制的方式，此计算机可读媒体可包含RAM、ROM、EEPROM、CD-ROM或其它光盘存储装置、磁盘存储装置或其它磁性存储装置，或可用于以指令或数据结构的形式载运或存储所要程序代码且可由计算机存取的任何其它媒体。而且，适当地将任何连接称为计算机可读媒体。举例来说，如果使用同轴电缆、光纤电缆、双绞线、数字订户线(DSL)或例如红外线、无线电和微波等无线技术从网站、服务器或其它远程源传输软件，则同轴电缆、光纤电缆、双绞线、DSL或例如红外线、无线电和微波等无线技术包括在媒体的定义中。如本文中所使用，磁盘和光盘包括压缩光盘(CD)、激光光盘、光盘、数字多功能光盘(DVD)、软盘和蓝光光盘，其中磁盘通常以磁方式再现数据，而光盘用激光以光学方式再现数据。上述各者的组合也应包括在计算机可读媒体的范围内。
提供对所揭示的示范性实施例的先前描述以使得所属领域的技术人员能够制作或使用本发明。所属领域的技术人员将明白对这些示范性实施例的各种修改，且可在不偏离本发明的精神或范围的情况下将本文中所界定的一般原理应用于其它实施例。因此，本发明无意限于本文中所展示的实施例，而是将赋予本发明与本文中所揭示的原理和新颖特征一致的最广范围。
Claims (21)
1.一种无线电力接收器，其包含：
天线，其包含具有谐振电路阻抗的谐振电路，所述天线经配置以从无线电力发射器接收无线电力信号；
整流器，其耦合到天线，所述整流器经配置以将所述无线电力信号转换成直流输入信号，所述直流输入信号具有电压信号和电流信号；
直流-直流转换器，其具有直流阻抗，所述直流-直流转换器经配置以基于所述直流输入信号而产生直流输出信号，且经配置以基于控制信号而调整所述直流阻抗，所述谐振电路阻抗响应于所述直流-直流转换器的所述直流阻抗的调整；以及
电路，其经配置以基于所述直流输入信号的所述电压信号或所述电流信号中的一者而调整所述控制信号。
2.根据权利要求1所述的无线电力接收器，其中所述直流-直流转换器进一步经配置以基于所述直流输入信号来调整所述直流输出信号的功率输出。
3.根据权利要求1所述的无线电力接收器，其中所述电路包含脉冲调制器。
4.根据权利要求3所述的无线电力接收器，其中所述脉冲调制器经配置以基于所述直流输出信号的电压和所述直流输出信号的电流中的一者来调整所述控制信号。
5.根据权利要求1所述的无线电力接收器，其中所述电路包含比较器，所述比较器经配置以基于所述直流输入信号的所述电压信号与参考信号的比较而产生所述控制信号。
6.根据权利要求3所述的无线电力接收器，其中所述脉冲调制器进一步包括处理器，所述处理器经配置以：
接收所述直流输入信号；
对所述直流输入信号的值进行取样以获得值；以及
基于经取样的值来调整所述控制信号的工作循环，所述谐振电路阻抗响应于所述控制信号的所述工作循环的调整。
7.根据权利要求6所述的无线电力接收器，其中所述处理器进一步经配置以对所述直流输入信号的电压、所述直流输入信号的电流、所述直流输出信号的电压、或所述直流输出信号的电流中的至少一者进行取样。
8.根据权利要求1所述的无线电力接收器，其中所述电路包括处理器，所述处理器经配置以：
接收所述直流输入信号；以及
对所述直流输入信号进行取样以获得一个值，其中所述控制信号调整基于来自所述直流输入信号的经取样的值，以将所述直流输出信号上的功率输出减小到一功率电平，所述功率电平小于经配置以接收所述直流输出信号的可充电装置所允许的最大功率电平。
9.根据权利要求1所述的无线电力接收器，其中所述直流-直流转换器包含降压式转换器或升压式转换器，所述降压式转换器或所述升压式转换器经配置以接收所述直流输入信号、所述控制信号并输出所述直流输出信号。
10.根据权利要求1所述的无线电力接收器，其中所述电路进一步经配置以基于所述谐振电路阻抗来调整所述无线电力接收器的接收带宽。
11.一种无线地接收功率的方法，其包含：
在无线电力接收器处接收来自无线电力发射器的无线电力信号，所述无线电力接收器包括具有谐振电路阻抗的谐振电路；
将所述无线电力信号整流成直流输入信号；
将所述直流输入信号转换成直流输出信号；以及
基于所述直流输入信号来调整所述直流输出信号的功率输出，以修改所述谐振电路阻抗并调整所述无线电力接收器的接收带宽。
12.根据权利要求11所述的方法，其中调整所述直流输出信号的所述功率输出进一步包含基于所述直流输入信号的电压和所述直流输入信号的电流中的一者或多者来调整所述直流输出信号的所述功率输出。
13.根据权利要求11所述的方法，其中调整所述直流输出信号的所述功率输出进一步包含基于所述直流输入信号的电压、所述直流输出信号的电压和所述直流输出信号的电流中的一者或多者来调整所述直流输出信号的所述功率输出。
14.根据权利要求11所述的方法，其中调整所述直流输出信号的所述功率输出进一步包含基于所述直流输入信号的电压、所述直流输入信号的电流、所述直流输出信号的电压和所述直流输出信号的电流中的一者或多者来调整所述直流输出信号的所述功率输出。
15.根据权利要求11所述的方法，其中调整所述直流输出信号的所述功率输出基于所述直流输入信号与电压参考信号的比较。
16.一种无线电力接收器，其包含：
用于从无线电力发射器接收无线电力信号的装置，该用于从无线电力发射器接收无线电力信号的装置具有谐振阻抗；
用于将所述无线电力信号整流成直流输入信号的装置；
用于将所述直流输入信号转换成直流输出信号的装置；以及
用于修改所述接收装置的交流阻抗的装置，其包含用于基于所述直流输入信号来调整所述用于基于所述直流输入信号将所述直流输入信号转换成直流输出信号的装置的输入直流阻抗以修改所述谐振阻抗的装置。
17.根据权利要求16所述的无线电力接收器，其中用于调整用于将所述直流输入信号转换成直流输出信号的装置的输入直流阻抗的装置进一步包含用于基于所述直流输入信号的电压和所述直流输入信号的电流中的一者或多者来调整来自所述用于将所述直流输入信号转换成直流输出信号的装置的所述直流输出信号的功率输出的装置。
18.根据权利要求16所述的无线电力接收器，其中用于调整用于将所述直流输入信号转换成直流输出信号的装置的输入直流阻抗的装置进一步包含用于基于所述直流输入信号的电压、所述直流输入信号的电流、所述直流输出信号的电压和所述直流输出信号的电流中的一者或多者来调整来自所述用于将所述直流输入信号转换成直流输出信号的装置的所述直流输出信号的功率输出的装置。
19.根据权利要求16所述的无线电力接收器，其中用于调整用于将所述直流输入信号转换成直流输出信号的装置的输入直流阻抗的装置进一步包含用于基于所述直流输入信号的电压、所述直流输入信号的电流、所述直流输出信号的电压和所述直流输出信号的电流中的一者或多者来调整来自所述用于将所述直流输入信号转换成直流输出信号的装置的所述直流输出信号的功率输出的装置。
20.根据权利要求16所述的无线电力接收器，其进一步包含用于比较所述直流输入信号与电压参考信号以确定一值的装置，用于调整用于将所述直流输入信号转换成直流输出信号的装置的输入直流阻抗的装置经配置以基于所述值来调整所述用于转换的装置的直流阻抗。
21.根据权利要求16所述的无线电力接收器，进一步包含用于调整所述谐振阻抗的接收带宽的装置。
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| US20100277003A1 (en) | 2010-11-04 |
| JP2015019576A (ja) | 2015-01-29 |
| EP2409378A1 (en) | 2012-01-25 |
| KR101631198B1 (ko) | 2016-06-16 |
| JP5728612B2 (ja) | 2015-06-03 |
| TW201106572A (en) | 2011-02-16 |
| ES2553138T3 (es) | 2015-12-04 |
| US8796887B2 (en) | 2014-08-05 |
| EP2988428B1 (en) | 2018-10-24 |
| JP2012521737A (ja) | 2012-09-13 |
| HUE042668T2 (hu) | 2019-07-29 |
| US20130113299A1 (en) | 2013-05-09 |
| CN104901432A (zh) | 2015-09-09 |
| CN102396132B (zh) | 2015-06-03 |
| KR101714335B1 (ko) | 2017-03-08 |
| JP5612069B2 (ja) | 2014-10-22 |
| ES2705081T3 (es) | 2019-03-21 |
| EP2988428A1 (en) | 2016-02-24 |
| US8338991B2 (en) | 2012-12-25 |
| KR20110134912A (ko) | 2011-12-15 |
| US20140070621A9 (en) | 2014-03-13 |
| WO2010108191A1 (en) | 2010-09-23 |
| KR20160071478A (ko) | 2016-06-21 |
| EP2409378B1 (en) | 2015-09-09 |
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