CN102342007A - 用于功率转换器的控制器 - Google Patents

用于功率转换器的控制器 Download PDF

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CN102342007A
CN102342007A CN2010800104354A CN201080010435A CN102342007A CN 102342007 A CN102342007 A CN 102342007A CN 2010800104354 A CN2010800104354 A CN 2010800104354A CN 201080010435 A CN201080010435 A CN 201080010435A CN 102342007 A CN102342007 A CN 102342007A
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switch
synchronous rectifier
controller
conducting
coupled
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CN102342007B (zh
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P·加里蒂
Z·杨
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Maypark Holdings Ltd.
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Flextronics International USA Inc
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)

Abstract

一种用于具有变压器(T1)的功率转换器的控制器，该变压器具有耦合到功率开关SW的初级绕组和耦合到同步整流器开关SR的次级绕组。在一个实施例中，控制器包括：第一控制器(310)，配置成控制功率开关SW的导通；以及第一延迟电路(320)，配置成延迟对功率开关SW的导通的启动。控制器也包括：第二控制器(340)，配置成根据在同步整流器开关SR的两个端子之间的电压差来控制同步整流器开关SR的导通；以及第二延迟电路(350)，配置成延迟对同步整流器开关SR的导通的启动。控制器还包括：关闭电路(360)，配置成在启动功率开关SW的导通之前基本上禁用同步整流器开关SR的导通。

Description

用于功率转换器的控制器
本申请要求于2009年1月19日提交的、标题为“Controller for aSynchronous Rectifier Switch and Power Converter Employing theSame”的第61/145,654号美国临时申请的权益，该申请在此通过引用全文并入本文。
技术领域
本发明总体涉及功率电子器件，并且更具体地涉及用于功率转换器的控制器及其操作方法。
背景技术
切换模式的功率转换器(也称为“功率转换器”或者“调控器”)是将输入电压波形转换成指定输出电压波形的功率供应或者功率处理电路。DC-DC功率转换器将直流(“dc”)输入电压转换成dc输出电压。与功率转换器关联的控制器通过控制其中运用的功率开关的导通时段来管理其操作。一般而言，控制器在反馈回路配置(也称为“控制回路”或者“闭合控制回路”)中耦合于功率转换器的输入与输出之间。
通常，控制器测量功率转换器的输出特性(例如输出电压、输出电流或者输出电压和输出电流的组合)，并且基于输出特性修改功率转换器的功率开关的占空比。占空比是由功率开关的导通时段对其切换时段所表示的比值。因此，如果功率开关导通持续半个切换时段，则功率开关的占空比将为0.5(或者50％)。此外，由于用于系统(诸如由功率转换器供电的微处理器)的电压或者电流动态改变(例如由于微处理器上的计算负荷改变)，控制器应当被配置成动态增加或者减少其中的功率开关的占空比以将诸如输出电压之类的输出特性维持于所需值。
为了产生dc输出电压，功率转换器经常运用二极管以对在变压器的次级绕组两端产生的交流(“ac”)电压进行整流。功率转换器也可以运用二极管来提供电流路径以提供诸如输出滤波器电感器之类的电感器中的电流的连续性。为电感器电流连续性提供电流路径的前述二极管常称为“续流(freewheeling)二极管”。整流和续流器件可能由于在二极管两端的前向电压降(尤其在产生五伏或者更少输出电压的功率转换器中)而在功率转换器中引入功率损耗部件。具有相对低的前向电压降的肖特基二极管经常运用于低电压功率转换器应用中以减少二极管前向电压降。然而，诸如肖特基二极管之类的无源整流器件通常不能实现少于约0.35伏的前向电压降、由此限制dc-dc功率转换器的转换效率。
为了实现可接受的效率水平，提供低输出电压(例如1伏)的dc-dc功率转换器经常运用具有少于约0.1伏的前向电压降的整流器件。为了提供这样进一步的功率损耗减少，提供电阻性电压降的有源半导体开关(诸如金属氧化物半导体场效应晶体管(“MOSFET”))常用来取代二极管。然而，必须与ac电压(例如在变压器的次级绕组两端产生的ac电压)的周期波形同步地将有源半导体开关周期性地驱动成导通和非导通模式或者状态。有源半导体开关可以由此避免无源整流器件中固有的较高前向电压降。用有源半导体开关取代二极管而产生的设计问题在于需要为其提供如下驱动信号，该驱动信号与功率转换器的操作准确同步以控制有源半导体开关的导通和非导通模式或者状态，并且该驱动信号避免与其它有源半导体开关有导通重叠。在功率转换器中的取代二极管的有源半导体开关一般称为“同步整流器”或者“同步整流器开关”。
于2000年5月9日向Jansen授权的标题为“Circuit Simulating aDiode”的第6,060,943号美国专利和于2002年10月22日向Jansen授权的标题为“Circuit Simulating a Diode”的第6,469,564号美国专利涉及如下电路，这些电路执行二极管的功能以在一个方向上导通电流而前向电压降为低、但是在另一方向上阻止电流以产生改进的整流功能，这两篇专利在此都通过引用结合于本文中。当在电路的指定正极端子的电压高于在指定负极端子的电压时，前向电流流动。当在这些指定端子的电压的极性反转时，电流中断。
在本领域中已知大量更多电路设计技术为同步整流器提供驱动信号。例如，于1994年4月12日向Rozman授权的标题为“Low LossSynchronous Rectifier for Application to Clamped-Mode PowerConverters”的第5,303,138号美国专利公开了应用于功率转换器的有源钳位的同步整流器的栅极可以由变压器的次级绕组的端子驱动，该专利在此通过引用结合于本文中。于2001年9月11日向Jacobs等人授权的标题为“Drive Compensation Circuit for Synchronous Rectifierand Method of Operating the Same”的第6,288,920号美国专利中描述的那样，运用与变压器的次级绕组串联耦合的二极管和电容器的驱动电路被构造成驱动同步整流器的栅极，该专利在此通过引用结合于本文中。如于2004年12月14日向Perry授权的标题为“SynchronousRectifier Drive Circuit and Power Supply Including Same”的第6,831,847号美国专利中描述的那样，用于同步整流器的驱动电路由接通开关、关断开关、电荷泵和脉冲变换器形成，该专利在此通过引用结合于本文中。
此外，Marty Brown的“Power Supply Cookbook”第二版中描述了同步整流器设计技术，该文献在此通过引用结合于本文中。如Brown在其中的第3.6.2节中描述的那样，图(a)和图(c)示出了由如图(a)中那样的具有直接连接的初级侧切换电路并且借助图(c)中的变压器驱动的同步整流器。Brown的图(b)示出了由变压器的输出电压直接驱动的同步整流器。因此，如在参考文献中描述的那样，包括有源钳位的具体功率转换拓扑可以被用来驱动用作同步整流器的有源半导体开关的控制端子，或者附加变压器绕组可以用于相同目的。
然而，这些方法中的每种方法提供对同步整流器在诸多应用中的使用进行限制或者以别的方式对其不利的效率和/或成本约束。因而，在本领域中需要的是一种避免现有技术中的缺陷的用于功率转换器中的同步整流器的控制器和有关方法。
发明内容
主要通过本发明的有利实施例来解决或者避免这些和其它问题并且主要通过这些实施例来实现技术优点，这些实施例包括一种用于具有变压器的功率转换器的控制器，该变压器具有耦合到功率开关的初级绕组和耦合到同步整流器开关的次级绕组。在一个实施例中，控制器包括：第一控制器，配置成控制功率开关的导通；以及第一延迟电路，配置成延迟对功率开关的导通的启动。控制器还包括：第二控制器，配置成根据在同步整流器开关的两个端子之间的电压差来控制同步整流器开关的导通；以及第二延迟电路，配置成延迟对同步整流器开关的导通的启动。控制器还包括：关闭电路(shutdown circuit)，配置成在启动功率开关的导通之前基本上禁用同步整流器开关的导通。
前文已经相当广义地概括本发明的特征和技术优点以便可以更好地理解下文对本发明的具体描述。下文将描述形成本发明权利要求主题的本发明附加特征和优点。本领域技术人员应当理解，可以容易使用公开的概念和具体实施例作为用于修改或者设计用于实现本发明相同目的的其它结构或者过程的基础。本领域技术人员也应当认识到，这样的等效构造并不脱离如在所附权利要求书中阐述的本发明的精神实质和范围。
附图说明
为了更完整理解本发明，现在参照与以下附图结合的下文描述：
图1图示了提供本发明应用环境的回扫功率转换器的部分的一个实施例的示意图；
图2图示了如下图解，这些图解示范了根据本发明原理的回扫功率转换器的操作特性；
图3和图4图示了如下回扫功率转换器的实施例的示意图，这些回扫功率转换器包括根据本发明原理构造的用于同步整流器的控制器；并且
图5图示了可与根据本发明原理构造的控制器一起运用的关闭电路的一个实施例的示意图。
在不同图中的对应标号和符号除非另有指明则一般指代对应部分并且可以在第一实例之后不重新加以描述以求简洁。绘制附图以图示示例实施例的相关方面。
具体实施方式
下文具体讨论本示例实施例的实现和运用。然而应当理解，本发明提供可以在广泛的各种具体背景中实施的许多可应用的发明概念。所讨论的具体实施例仅举例说明用于实现和运用本发明的具体方式而不限制本发明的范围。
将在具体背景(即如下功率转换器及其操作方法，该功率转换器包括构造成在导通时段基本上无重叠的情况下操作的功率开关和同步整流器开关)中参照示例实施例描述本发明。尽管将在功率转换器的环境中描述本发明的原理，但是可以从诸如功率放大器或者电机控制器之类的控制器中受益的任何应用也在本发明的广义范围内。
回扫功率转换器拓扑由于它的简易和低成本而经常运用于诸如用于笔记本个人计算机的低功率应用中。在功率转换器的变压器的次级侧上的整流二极管的前向电压降造成大量功率损耗，这使得难以满足高功率转换效率目标，诸如ENERGY STAR EPA 4.0效率标准。可以通过将本发明的原理应用于回扫功率转换器以及其它转换器拓扑来缓解前述限制。
现在参照图1，图示了提供本发明应用环境的回扫功率转换器的部分的一个实施例的示意图。为了减少功率损耗，同步整流器开关SR(例如有源半导体开关，诸如MOSFET开关)已经被用来取代在这一功率转换器拓扑中的变压器的次级侧上通常使用的整流二极管。功率转换器的功率链包括在其输入端耦合到提供输入电压Vin的dc输入电源的功率开关SW。dc输入电源在输入电压Vin向匝数比为n∶1的变压器T1供应输入功率。变压器T1具有NP个初级匝和NS个次级匝，其中在考虑所得占空比和对功率链部件的应力时选择初级匝和次级匝以提供输出电压Vout。功率开关SW(例如n沟道MOSFET)由如下控制器(诸如脉宽调制控制器(未示出))控制，该控制器在占空比为D而切换频率为fs时控制功率开关SW导通。占空比D由脉宽调制控制器调节以调控功率转换器的输出特性，诸如输出电压、输出电流或者二者的组合。在变压器T1的次级绕组上出现的ac电压由经过输出滤波器电容器Cout耦合到输出的同步整流器SR整流以产生输出电压Vout。
在功率开关SW导通时占空比D的第一部分期间，流过变压器T1的初级绕组的初级电流Ipri随着电流从输入流过功率开关SW和变压器T1的磁化电感而增加。在占空比的互补部分(一般与功率开关SW的互补占空比“1-D”共存)期间，功率开关SW响应于栅极驱动信号VGSSW而转变成非导通状态，并且耦合到输出滤波器电容器Cout的同步整流器开关SR响应于栅极驱动信号VGSSR而被启用以导通。同步整流器开关SR提供用于维持在变压器T1的磁化电感中流动的电流连续性的路径。在占空比的互补部分1-D期间，流过变压器T1的磁化电感的电流减少。一般而言，在占空比D的第一部分期间，可以调节功率开关SW和同步整流器开关SR的占空比以维持对功率转换器的输出电压Vout的调控。然而本领域技术人员应当理解，用于功率开关SW和同步整流器开关SR的导通时段或者导通可以隔开少量时间间隔以免其间交叉导通并且有益于减少与功率转换器关联的功率切换损耗。如图1中所示，功率开关SW和同步整流器开关SR均包括分别表示为二极管DSW和DSR的体二极管以及分别表示为电容器CSW和CSR的寄生的源极到漏极电容。
现在参照图2，图示了如下图解，这些图解示范了根据本发明原理的回扫功率转换器的操作特性。继续参照图1，这些图图示了分别与功率开关SW和同步整流器开关SR关联的栅极驱动波形VGSSW、VGSSR、在变压器T1的初级绕组中的初级电流Ipri以及在变压器T1的次级绕组中的次级电流Isec。为了防止功率开关SW的电流击穿条件(即为了防止其中功率开关SW和同步整流器开关SR同时启用以导通的条件)，开关的导通时段或者导通理想地不应重叠。如图2中所示，为了避免功率开关SW和同步整流器开关SR的同时导通，在回扫功率转换器的功率开关SR的关断瞬间与同步整流器开关SR的接通瞬间之间以及在功率开关SW的关断瞬间与同步整流器开关SR的接通瞬间之间引入栅极驱动波形VGSSW、VGSSR中的明显时间延迟TP1、TP2(例如图中的交叉影线区所示的50纳秒)。
已经开发若干种商用集成电路(“IC”)驱动器以应用于回扫功率转换器中的同步整流器。典型同步整流器集成电路驱动器包括瑞士日内瓦STMicroelectronics生产的STSR3IC驱动器、加利福尼亚州埃尔塞贡多International Rectifier生产的IR1167 IC驱动器、荷兰RoyalPhilips Electronics生产的TEA1761 IC驱动器和其它驱动器。同步整流器集成电路驱动器不仅比用分立部件构造的电路更昂贵而且引入更多电路缺陷、因此不能满足笔记本计算机市场和其它应用的高性能和低成本要求。例如，STSR3IC驱动器能够产生仅高达5.5伏(“V”)的栅极驱动电压。因而，受驱动的同步整流器MOSFET的实际栅极电压仅能够高达5.0V，这不足以充分减少同步整流器开关的接通电阻。因而，相比于在恰当驱动同步整流器开关情形下的潜在功率损耗减少，同步整流器中的功率损耗未充分减少。
同步整流器开关SR的关断信号通常不生成于回扫功率转换器的初级侧上而是按照变压器T1的次级绕组的电压随时间的改变速率来产生。因此，在关断同步整流器开关SR与接通功率开关SW之间未提供受控制的时间延迟。因而，回扫功率转换器未高效操作并且可能在连续导通模式中产生击穿。虽然IR1167和TEA 1761 IC驱动器可以产生与STSR3 IC驱动器类似的高达20V的栅极电压，但是两个同步整流器集成电路驱动器依赖于变压器T1的次级绕组对触发同步整流器开关SR的关断的随时间的改变速率。因此，为了回扫功率转换器的可靠操作而包括同步整流器开关SR，重要的是从变压器T1的初级侧为同步整流器开关SR提供关断信号，从而可以恰当控制与同步整流器开关SR关联的导通延迟。
因此，用现有技术的用于同步整流器的驱动器构造的回扫功率转换器将不提供充分可靠性，并且可能在连续导通模式中产生大量击穿电流。由于同步整流器开关SR的接通和关断均由在变压器的次级侧上的电压生成，所以遭遇这些限制。在变压器T1的次级侧上产生的电压未提供在初级侧功率开关SW的关断瞬间与次级侧同步整流器开关SR的接通瞬间之间的合理控制的空载时间。
现在参照图3，图示了回扫功率转换器的一个实施例的示意图，该回扫功率转换器包括根据本发明原理构造的用于同步整流器的控制器。dc输入电源在输入电压Vin向耦合到第一开关或者功率开关SW(例如n沟道MOSFET)的变压器T1供应输入功率。在变压器T1的次级侧上，第二开关或者同步整流器开关SR(例如n沟道MOSFET)对在变压器T1的次级绕组的ac电压进行整流，并且所得波形由输出滤波器电容器Cout滤波。电阻器RLOAD表示耦合到回扫功率转换器的输出端子的负载。包括电容器C3、电阻器R3和二极管D1的重置电路为变压器T1提供耗散重置功能。
如图3中所示，第一控制器或者脉宽调制控制器310(称为“PWM”)产生或者生成用于控制功率开关SW的占空比或者导通的控制信号或者波形。脉宽调制控制器310产生的波形由第一延迟电路或者功率开关延迟电路320延迟(称为“SW接通延迟”)，该电路的输出耦合到栅极驱动器330(称为“栅极驱动器”)以驱动功率开关SW的栅极。换而言之，功率开关延迟电路320被配置成延迟对功率开关SW的导通的启动。包括接通延迟功能以免功率开关SW和同步整流器开关SR的交叉导通。从初级偏置电压源(称为“VCC_pri”)向脉宽调制控制器310、功率开关延迟电路320和栅极驱动器330供电。
同步整流器开关SR的导通由感测同步整流器开关SR的切换端子两端的电压的第二控制器或者同步整流器控制器340控制(称为“SR控制”)。当在节点A的电压低于在节点K的电压时(称为“输入感测”)，同步整流器控制器340禁用同步整流器开关SR的导通。当在节点(或者端子)A的电压高于在节点(或者端子)K的电压时，禁用导通。第二延迟电路或者同步整流器延迟电路350(称为“SR接通延迟”)延迟用于同步整流器开关SR的控制信号以免与功率开关SW交叉导通。换而言之，同步整流器延迟电路被配置成延迟对同步整流器开关SR的导通的启动。从次级偏置电压源(称为“VCC_sec”)向同步整流器控制器340供电。在一个备选实施例中，如可能需要的那样，可以运用电压降电路机构(诸如齐纳二极管或者线性调控器)从回扫功率转换器的输出端子向同步整流器控制器340供电。此外，包括关闭电路360(称为“关闭”)以向同步整流器控制器340提供先行信号(anticipatory signal)，从而可以在将功率开关SW的导通启动或者启用之前将同步整流器开关SR的导通禁用。
这里为回扫功率转换器引入的同步整流器控制过程提供一种用于基本上消除在其初级侧上的功率开关SW与在其次级侧上的同步整流器开关SR之间的交叉导通的机制。在关断初级开关SW之后，同步整流器开关SR的输入感测从高电势摆向低电势，并且同步整流器开关SR的体二极管导通。检测到输入感测的向下斜度，这触发时间延迟电路(例如同步整流器延迟电路350)。在某一编程时间延迟之后产生控制信号并且该控制信号接通同步整流器开关SR。
当脉宽调制控制器310生成用于接通功率开关SW的信号时，这一信号跨越在变压器T1的初级侧与次级侧之间的边界以关断在变压器T1的次级侧上的同步整流器开关SR。然后，在可编程时间延迟之后，与功率开关延迟电路320结合的脉宽调制控制器310与栅极驱动器330结合接通功率开关SW。
现在参照图4，图示了回扫功率转换器的一个实施例的示意图，该回扫功率转换器包括根据本发明原理构造的用于同步整流器的控制器。回扫功率转换器包括第一延迟电路或者初级侧功率开关延迟电路410，该电路包括二极管D2、电阻器R2和电容器C1。回扫功率转换器还包括关闭电路420，该电路包括电阻器R5、R6、R7、电容器C2和开关Q3(例如n沟道MOSFET)。回扫功率转换器还包括第二延迟电路，该电路包括同步整流器延迟电容器C4。同步整流器控制器430由电阻器R8、R9、电容器C5、二极管D3、D4、D5和npn双极晶体管Q1、Q2形成，该同步整流器控制器430耦合到同步整流器开关SR。
在操作中，次级侧同步整流器开关SR首先关断，并且在短暂时间延迟之后，初级侧功率开关SW开始接通。初级侧功率开关SW首先关断，并且在延迟之后，次级侧同步整流器开关SR开始接通。可以通过改变功率开关延迟电路410和同步整流器延迟电容器C4中的部件参数值对延迟时间进行编程。
图4中所示同步整流器控制器430包括由双极晶体管Q2形成的放大器，该双极晶体管Q2的集电极耦合到次级偏置电压源(称为“VCC_sec”)。当同步整流器开关SR的体二极管(未示出)前向偏置时，节点K的电压相对于耦合到次级电路接地的节点A的电压变为负。在节点K的负电压经过二极管D5耦合到双极晶体管Q2的基极，这关断该晶体管。由此在双极晶体管Q2的集电极产生的正电压反向偏置二极管D4，并且正电压经过双极晶体管Q1耦合到同步整流器开关SR的栅极从而接通它。
当同步整流器开关SR的体二极管反向偏置时，出现逆操作，其中同步整流器开关SR的栅极的电压由电路减少至充分低的电压以禁用它的导通。同步整流器延迟电容器C4提供用于延迟对同步整流器开关SR的接通的机制。关闭电路420耦合到双极晶体管Q1以在变压器T1的初级侧上与功率开关延迟电路410和栅极驱动器450配合将脉宽调制控制器440(称为“PWM”)启用以在功率开关SW中启用导通之前，禁用同步整流器开关SR的导通。
现在参照图5，图示了根据本发明原理构造的关闭电路或者同步整流器关闭电路510的一个实施例的示意图，该电路包括电阻器R10、R11、电容器C20、变压器T2和n沟道MOSFET Q3。关闭电路510分别图示了初级和次级接地端子gndpri、gndsec，这些端子示出了变压器T2的初级和次级侧的分离。在关闭电路510中包括电容器C20以防止dc偏置电流在变压器T2中流动。关闭电路510是图4中所示关闭电路420的如下备选，该备选运用变压器T2以跨越初级到次级隔离边界而不是图4中所示电容器C2。
因此，已经介绍在连续导通模式中与如下文阐述的电路元件一起可操作的功率转换器，诸如回扫功率转换器。功率转换器包括用于功率开关的初级侧接通延迟电路(也称为“第一延迟电路或者功率开关延迟电路”)、用于同步整流器开关的次级侧接通延迟电路(也称为“第二延迟电路或者同步整流器延迟电路”)和用于初级侧上的同步整流器开关的关闭电路(从初级侧启动它的动作)。可以有利地在功率转换器中在初级侧接通延迟电路之后包括驱动器(例如栅极驱动器)。
在初级侧上的栅极驱动器可以由分立部件形成，这些部件包括在串联等级(totem-pole)布置中连接的两个晶体管。取而代之，可以运用商用集成电路驱动器。如果输出电压少于例如10V，则可以从功率转换器的输出电压端子直接获得功率转换器的次级侧上的用于同步整流器的偏置电压源。如果输出电压高于例如10V，则可以经过齐纳二极管和电阻器从功率转换器的输出电压端子获得偏置电压源。也可以从诸如线性调控器之类的独立偏置电压供应电路获得次级侧上的偏置电压源。
在一个实施例中，用于功率转换器的控制器包括：第一控制器，配置成控制第一开关(例如金属氧化物半导体场效应晶体管)的导通；以及第一延迟电路(例如并联耦合到二极管的电阻器和与之串联耦合的电容器)，配置成延迟对第一开关的导通的启动。控制器还包括：第二控制器(例如多个电阻器、电容器和开关或者放大器和开关)，配置成根据在第二开关(例如金属氧化物半导体场效应晶体管)的两个端子之间的电压差来控制它的导通；以及第二延迟电路(例如电容器)，配置成延迟对第二开关的导通的启动。控制器的关闭电路(例如耦合到第一控制器的电容器或者变压器和耦合到第二控制器的开关)被配置成在启动第一开关的导通之前基本上禁用第二开关的导通。如这里描述的那样，控制器的部分(包括第一和第二控制器)耦合到偏置电压源。
本领域技术人员应当理解，仅出于示例目的而提出一种包括同步整流器的功率转换器及其有关操作方法的前述实施例。此外，各种其它功率转换器拓扑(诸如前向功率转换器和单端初级电感器功率转换器拓扑)也在本发明的广义范围内。尽管已经在功率转换器的环境中描述一种包括同步整流器的功率转换器，但是同步整流器也可以应用于其它系统，诸如但不限于功率放大器和电极控制器。
为了更好地理解功率转换器，参见纽约州纽约市Van NostrandReinhold公司的Rudolph P.Severns和Gordon Bloom的“ModernDC-to-DC Power Switch-mode Power Converter Circuits”(1985)和J.G.Kassakian、M.F.Schlecht和G.C.Verghese的“Principles of PowerElectronics”Addison-Wesley(1991)。前述参考文献通过引用整体结合于此。
另外，虽然已经具体描述本发明及其优点，但是应当理解可以对其进行各种改变、替换和变更而不脱离如所附权利要求书限定的本发明精神实质和范围。例如，可以用不同方法实施并且用其它过程取代上文讨论的诸多过程或者其组合。
另外，本申请的范围并不限于在说明书中描述的过程、机器、制造产品、物质组成、装置、方法和步骤的具体实施例。如本领域普通技术人员将根据本发明的公开内容容易理解的那样，可以根据本发明利用执行与这里描述的对应实施例基本上相同的功能或者实现基本上相同的结果的、当前存在或者以后将开发的过程、机器、制造产品、物质组成、装置、方法或者步骤。因而，所附权利要求书旨在于在它们的范围内包括这样的过程、机器、制造产品、物质组成、装置、方法或者步骤。

Claims (20)

1.一种可与具有变压器的功率转换器一起运用的控制器，所述变压器具有耦合到功率开关的初级绕组和耦合到同步整流器开关的次级绕组，所述控制器包括：
第一控制器，配置成控制所述功率开关的导通；
第一延迟电路，配置成延迟对所述功率开关的所述导通的启动；
第二控制器，配置成根据在所述同步整流器开关的两个端子之间的电压差来控制所述同步整流器开关的导通；
第二延迟电路，配置成延迟对所述同步整流器开关的所述导通的启动；以及
关闭电路，配置成在对所述功率开关的所述导通的所述启动之前基本上禁用所述同步整流器开关的所述导通。
2.根据权利要求1所述的控制器，其中所述第二控制器被配置成在所述同步整流器开关的一个端子的电压随着所述同步整流器开关的体二极管导通而变成高于所述同步整流器开关的另一端子的电压时启用所述同步整流器开关的所述导通。
3.根据权利要求1所述的控制器，其中所述第一控制器为脉宽调制控制器。
4.根据权利要求1所述的控制器，其中所述第二控制器包括耦合到所述同步整流器开关的放大器和开关。
5.根据权利要求1所述的控制器，其中所述第一延迟电路包括并联耦合到二极管的电阻器和与之串联耦合的电容器，并且所述第二延迟电路包括电容器。
6.根据权利要求1所述的控制器，其中所述关闭电路包括耦合到所述第一控制器的电容器和耦合到所述第二控制器的开关。
7.根据权利要求1所述的控制器，其中所述关闭电路包括耦合到所述第一控制器的变压器和耦合到所述第二控制器的开关。
8.根据权利要求1所述的控制器，其中所述第二控制器的部分耦合到偏置电压源。
9.一种操作可与具有变压器的功率转换器一起运用的控制器的方法，所述变压器具有耦合到功率开关的初级绕组和耦合到同步整流器开关的次级绕组，所述方法包括：
控制所述功率开关的导通；
延迟对所述功率开关的所述导通的启动；
根据在所述同步整流器开关的两个端子之间的电压差来控制所述同步整流器开关的导通；
延迟对所述同步整流器开关的所述导通的启动；以及
在对所述功率开关的所述导通的启动之前基本上禁用所述同步整流器开关的所述导通。
10.根据权利要求9所述的方法，其中所述延迟对所述功率开关的所述导通的所述启动包括延迟用于所述功率开关的控制信号。
11.根据权利要求9所述的方法，其中所述控制所述同步整流器开关的所述导通包括在所述同步整流器开关的一个端子的电压随着所述同步整流器开关的体二极管导通而变成高于所述同步整流器开关的另一端子的电压时启用所述同步整流器开关的所述导通。
12.根据权利要求9所述的方法，其中所述基本上禁用所述同步整流器开关的所述导通包括提供先行信号使得在启动所述功率开关的导通之前禁用所述同步整流器开关的所述导通。
13.一种功率转换器，包括：
变压器，具有初级绕组和次级绕组；
功率开关，耦合到所述初级绕组；
同步整流器开关，耦合到所述次级绕组；以及
控制器，包括：
第一控制器，配置成控制所述功率开关的导通，
第一延迟电路，配置成延迟对所述功率开关的所述导通的启动，
第二控制器，配置成根据在所述同步整流器开关的两个端子之间的电压差来控制所述同步整流器开关的导通，
第二延迟电路，配置成延迟对所述同步整流器开关的所述导通的启动，以及
关闭电路，配置成在对所述功率开关的所述导通的所述启动之前基本上禁用所述同步整流器开关的所述导通。
14.根据权利要求13所述的功率转换器，其中所述第二控制器被配置成在所述同步整流器开关的一个端子的电压随着所述同步整流器开关的体二极管导通而变成高于所述同步整流器开关的另一端子的电压时启用所述同步整流器开关的所述导通。
15.根据权利要求13所述的功率转换器，其中所述第一控制器是脉宽调制控制器，并且所述第一延迟电路包括并联耦合到二极管的电阻器和与之串联耦合的电容器。
16.根据权利要求13所述的功率转换器，其中所述第二控制器包括耦合到所述同步整流器开关的放大器和开关，并且所述第二延迟电路包括电容器。
17.根据权利要求13所述的功率转换器，其中所述关闭电路包括耦合到所述第一控制器的电容器和变压器之一以及耦合到所述第二控制器的开关。
18.根据权利要求13所述的功率转换器，其中所述第二控制器的部分耦合到偏置电压源。
19.根据权利要求13所述的功率转换器，其中所述功率转换器在连续导通模式中可操作。
20.根据权利要求13所述的功率转换器，还包括：重置电路，其包括电容器、电阻器和二极管，所述重置电路被配置成针对耦合到所述功率开关和所述同步整流器开关的变压器提供耗散重置功能。
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