WO2021109305A1 - 一种llc谐振变换器谐振腔切换装置以及控制方法 - Google Patents

一种llc谐振变换器谐振腔切换装置以及控制方法 Download PDF

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WO2021109305A1
WO2021109305A1 PCT/CN2019/130569 CN2019130569W WO2021109305A1 WO 2021109305 A1 WO2021109305 A1 WO 2021109305A1 CN 2019130569 W CN2019130569 W CN 2019130569W WO 2021109305 A1 WO2021109305 A1 WO 2021109305A1
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resonant cavity
resonant
input
output
switching device
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PCT/CN2019/130569
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English (en)
French (fr)
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杨得秋
张军明
徐德鸿
王泽峰
胡长生
梅营
金佑燮
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浙江大学
乐金电子研发中心(上海)有限公司
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/44—Conversion of dc power input into dc power output with intermediate conversion into ac by combination of static with dynamic converters; by combination of dynamo-electric with other dynamic or static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the invention relates to a resonant cavity switching device and a control method of an LLC resonant converter, and belongs to the technical field of circuits.
  • LLC resonant converter is a high-efficiency converter with soft-switching characteristics. It adopts a transformer isolation structure and is widely used in high-power applications where isolated output is required.
  • the LLC resonant converter has two resonant frequencies, one is the resonant frequency f 0 when the resonant capacitor and the resonant inductor work in series, and the formula is
  • the other resonant frequency is the resonant frequency f p when the resonant capacitor and the resonant inductance plus the magnetizing inductance work in series, and the formula is
  • the LLC resonant converter adjusts the output voltage by changing the operating frequency f s of the circuit.
  • the circuit works at the resonant frequency f 0 , its voltage gain is 1, and when it works at the under-resonant frequency (f s ⁇ f 0 )
  • the voltage gain is greater than 1, and the voltage gain is less than 1 when working at an over-resonant frequency (f s >f 0 ).
  • the operating frequency cannot be lower than f p , otherwise the LLC resonant converter will enter the capacitive region and lose the zero voltage turn-on, resulting in greater switching loss, so the converter should work near the resonant frequency And ensure that f s > f p .
  • the transformer's magnetizing inductance participates in resonance, which will cause the primary current circulating, resulting in circulating current loss.
  • the circulating current loss is mainly magnetic loss, and the greater the voltage gain, the greater the operating frequency. Low, the greater the circulating current loss in the circuit, the lower the efficiency.
  • the rectifier diode on the secondary side of the converter will enter a hard shutdown mode, there will be reverse recovery loss, and the efficiency will also decrease.
  • a too low operating frequency may cause the excitation inductance current to be too large, and the circulating energy is large and the loss is large; when working in the buck mode, it is limited by the circuit parameters (such as resonant inductance and excitation inductance).
  • the ratio of the voltage reduction to the operating frequency is not linear, and the output voltage reduction range is also limited.
  • the voltage change adaptation range of the LLC resonant converter is limited, that is, the ratio of (maximum input * maximum output) to (minimum input * minimum output) needs to be Smaller, too large voltage variation range will cause the performance of LLC converter to deteriorate sharply, or even fail to work normally. Therefore, it has always been a research hotspot of LLC converters, such as widening the voltage change adaptation range of LLC resonant converters.
  • An LLC resonant converter resonant cavity switching device and control method are designed.
  • This LLC resonant converter resonant cavity switching device and control strategy have the following functions: The device changes the resonant cavity parameters of the converter, and changes the resonant frequency of the circuit through the change of the resonant parameters, thereby achieving the effect of increasing the gain range and expanding the voltage variation adaption range of the LLC converter.
  • an LLC resonant converter resonant cavity switching device which includes an input voltage, an input switching network (or called an input inverter bridge), a first resonant cavity, and a second resonant cavity.
  • Resonant cavity, switching device, first output rectification filter device and second output rectification filter device Its characteristics are:
  • the input voltage is usually a DC voltage, which also becomes a DC bus, which is coupled to the input switch network.
  • the magnitude of the input voltage is variable, and can also be constant.
  • the input switch network coupled with the input voltage, whose function is to invert the direct current into a high-frequency square wave alternating current, as the input of the resonant network.
  • the first resonant cavity, the resonant cavity includes a resonant capacitor, a resonant inductor, and an isolation transformer. Its function is to pass a high-frequency square wave AC through the resonant cavity, couple the input energy to the output side of the transformer, and pass the resonance
  • the resonance of the network realizes the soft switching of the switches in the input switching network (or called zero-voltage turn-on) and reduces the switching loss.
  • the resonant cavity has an input port and an output port, the input port receives the output signal of the input switch network, and the output port is connected to a corresponding output rectifier device.
  • the switching device whose function is to provide two modes of on and off.
  • the switching device is connected in series between one end of the series input of the first resonant cavity and one end of the output of the input switch network. In the ON mode, the input of the first resonant cavity is coupled to the output of the input switch network.
  • a second resonant cavity the resonant cavity includes a resonant capacitor, a resonant inductor, and an isolation transformer, and the second resonant cavity is coupled to both ends of the switching device. In the on mode of the switching device, it is bypassed. In the off mode of the switching device, the second resonant cavity is connected in series with the first resonant cavity and is commonly coupled to the output end of the input switch network.
  • the first output rectifying device and the second output rectifying device respectively have an input port and an output port.
  • the input ports are respectively coupled to the output port of the first resonant cavity and the output port of the second resonant cavity, and receive the corresponding resonance.
  • the output signal of the cavity, and a DC output signal is obtained.
  • the output ports of the first output rectifying device and the second output rectifying device are connected in parallel and coupled to the load
  • the switching control strategy of the resonant cavity of LLC resonant converter of the present invention is as follows:
  • the design of the resonant cavity parameters of the LLC resonant converter is relatively fixed, and the design of the transformer turns ratio (the turns ratio in this article refers to the number of primary and secondary turns of the transformer Ratio) basically determines the voltage gain range of the converter.
  • the gain variation range is usually within 2 times.
  • the turns ratio is usually selected at the ratio of rated input to rated output, so that the converter has a higher working efficiency most of the time and has a certain voltage variation range adaptability, such as the voltage conversion range within 2 times . But in some applications, the voltage change is very wide.
  • the design of the transformer becomes very difficult.
  • the design of a large transformer turns ratio cannot take into account the high input voltage; the design of a transformer whose turns ratio is too small cannot take into account the low input voltage.
  • the resonant cavity in the LLC resonant converter is divided into two, the switching device is connected in series to the first resonant cavity, and the second resonant cavity is connected in parallel with the switching device.
  • the switching device and control method of the resonant cavity of LLC resonant converter of the present invention In order to ensure the normal operation of the circuit before and after switching, the switching device should be able to ensure that the current can pass in both forward and reverse directions in the on state, and in the off state. Ensure that it can withstand at least half of the peak value of the input voltage.
  • Fig. 1 is a block diagram of an embodiment of the present invention
  • FIG. 1 Input switch network embodiment.
  • Fig. 3 is a schematic diagram of an embodiment of a resonant cavity
  • FIG. 4 Schematic diagram and embodiment of a switching device
  • Fig. 5 is an embodiment of the output rectifying device
  • Fig. 6 is an embodiment of the present invention.
  • the current can flow bidirectionally, and when in the off state, it can withstand at least more than half of the input voltage.
  • Fig. 1 shows an implementation of an LLC resonant converter resonant cavity switching device and control strategy of the present invention. It includes an input power supply, an input switching network, a resonant cavity A, a resonant cavity B, a switching device, and an output rectifying device A And output rectifier B.
  • the input switch network coupled with the input power source is used to invert the input power source into a high frequency square wave alternating current of the required frequency.
  • the resonant cavity A connected to the input switch network includes resonant capacitors, resonant inductances, and isolation transformers. Its function is to pass high-frequency square wave AC through the resonant cavity to couple the input energy to the output side of the transformer and pass through the resonant network.
  • the resonance of the input switch network realizes the soft switching of the switches in the input switch network (or called zero-voltage turn-on) and reduces the switching loss.
  • the resonant cavity has an input port and an output port, the input port receives the output signal of the input switch network, and the output port is connected to a corresponding output rectifier device.
  • One input end of the resonant cavity A is connected in series with the switching device, and the other end of the switching device is coupled to one output end of the input switch network, and the other input end of the resonant cavity A is coupled to the other output end of the input switch network .
  • Resonant cavity B is similar to resonant cavity A, including resonant capacitors, resonant inductors, and isolation transformers, with similar functions.
  • the input end of the resonant cavity B is connected to both ends of the switching device, that is, in parallel with the switching device.
  • the switching device provides two modes of on and off under the action of the control signal.
  • the output rectifying device A and the output rectifying device B are respectively coupled to the output ends of the resonant cavity A and the resonant cavity B, and their function is to rectify the output signal transmitted by the resonant cavity to obtain a corresponding DC output.
  • the resonant cavity B in the on mode, the resonant cavity B is bypassed by the switching device; in the off mode, the input end of the resonant cavity B and the input end of the resonant cavity A are coupled to the input switch network in series.
  • the input voltage can also be obtained by AC input rectification, for example, a commercial power rectifier obtains a DC voltage with a varying amplitude.
  • a commercial power rectifier obtains a DC voltage with a varying amplitude.
  • an alternating current with a frequency of 50/60 Hz and an effective voltage value of 80-265V is rectified into a direct current.
  • the most traditional implementation is diode rectification, plus a suitable electric filter, such as a capacitor or an LC filter.
  • Figure 2 shows a schematic diagram of the input switch network.
  • Figure 2 shows a full-bridge structure and two half-bridge structures, namely, half-bridge structure-1 and half-bridge structure-2.
  • the switches of the switch network shown in the figure can be metal oxide semiconductor field effect transistors (MOSFET), bipolar transistors (BJT) or insulated gate transistors (IGBT).
  • MOSFET metal oxide semiconductor field effect transistors
  • BJT bipolar transistors
  • IGBT insulated gate transistors
  • the diagonal switches are turned on alternately, turning the DC input voltage into a high-frequency AC square wave signal.
  • FIG. 3 shows a schematic diagram of an embodiment of the resonant cavity A or the resonant cavity B.
  • the resonant cavity usually consists of a resonant capacitor Cr, a resonant inductance Lr, a transformer T, and the magnetizing inductance Lm of the transformer T.
  • the resonant inductor Lr can be an independent inductor.
  • the resonant inductance can be the leakage inductance of the transformer, which is integrated with the transformer itself and is not physically visible.
  • the magnetizing inductance of the transformer itself is fully integrated with the transformer, not an independent inductor.
  • the resonant capacitor can be connected in series to any input end of the resonant cavity (as shown in Mode 1 and Mode 2).
  • the resonant capacitor can be integrated into the filter capacitor.
  • two capacitors in the half-bridge structure-2 can be used as resonant capacitors.
  • the input end of the resonant cavity is usually coupled to the output end of the input switch network, receives the output signal of the switch network, and transmits power to the other side (secondary side) of the transformer to achieve isolated transmission of energy.
  • the soft switching of the switches in the input switch network or referred to as zero voltage turn-on
  • the soft turn-off of the switches in the output rectifier device are realized to reduce the switching loss.
  • the switching device is a controlled switch, including two states of on and off, and usually includes an input terminal, an output terminal and a control terminal, as shown in Figure 4(A).
  • the control terminal controls the switching device to be in an on or off state based on the control signal.
  • the switching device may be a relay in one embodiment. In another embodiment, it can also be implemented based on semiconductor switches, such as using two back-to-back MOSFETs, as shown in FIG. 4(B). In an embodiment using a MOSFET, if the control terminal voltage is higher than the turn-on threshold of the MOSFET, the switching device is turned on, and if it is lower than the turn-on threshold, it is turned off.
  • MOSFET if the control terminal voltage is higher than the turn-on threshold of the MOSFET, the switching device is turned on, and if it is lower than the turn-on threshold, it is turned off.
  • Fig. 5 shows an embodiment of the output rectification device, that is, the full-bridge rectification mode, which uses 4 diodes to rectify the high frequency AC signal on the output side of the transformer into a DC output.
  • the rectifier device may also include a filter device, such as a capacitor filter.
  • a filter device such as a capacitor filter.
  • the rectifier device can have various implementations, such as full-wave rectification, voltage doubler rectification, and other structures, which will not be repeated here.
  • diode rectification can be used
  • MOSFET can also be used to implement synchronous rectification, or a hybrid rectification method composed of a mixture of diodes and MOSFETs.
  • the high-frequency output AC of the transformer is rectified into a DC signal, which does not affect the essence of the present invention.
  • the input voltage can be divided into two gears, one gear is a low-voltage gear ranging from 100V to 200V, and the other gear is a high-voltage gear ranging from 200V to 400V.
  • the switching device is turned on. At this time, only the resonant cavity A participates in resonance, and the resonant cavity B is short-circuited.
  • the input voltage is doubled compared to the low voltage range.
  • the switching device is turned off, and the two resonant cavities are connected in series and participate in resonance at the same time. Assuming that the parameters of the resonant cavity A and B are the same, the two resonant cavities have the same parameters.
  • the voltages are equal, each is half of the input power voltage, so the voltages at both ends of the transformers of the two resonant cavities are also the same, and because the output terminals of the output rectifiers A and B connected to the rear stages of the resonant cavity A and B are connected in parallel, the high voltage is in
  • the load voltage after the switching device is turned off is equivalent to the load voltage when the low-voltage switch device is turned on.
  • Fig. 6 is an implementation schematic diagram of a specific LLC resonant converter with a switching device constructed based on the above description.
  • the present invention adopts an LLC resonant converter resonant cavity switching device and control strategy.
  • the resonant cavity of the LLC resonant converter is changed by the switching device, which solves the shortcomings of the small gain range of the LLC resonant converter. Enlarging the range of input and output voltage changes also ensures the safety and reliability of the device's work.

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Abstract

本发明公开了一种LLC谐振变换器谐振腔切换装置以及控制方法。它包括：输入整流滤波器，输入逆变桥，第一谐振腔，第二谐振腔，切换装置，第一输出整流滤波装置和第二输出整流滤波装置。本发明的电路可通过切换装置使LLC变换器工作在不同的谐振腔下，当切换装置开通时，仅第一谐振腔参与谐振，因此只有第一输出整流桥可进行功率传输；而当切换开关关断时，第一和第二谐振腔串联工作一起谐振，此时第一输出整流桥和第二输出整流桥同时进行功率传输，在两谐振腔参数相同的情况下可使输出功率增大一倍，这拓宽了LLC变换器的增益范围，解决了LLC谐振变换器无法在宽增益范围下工作的问题。

Description

一种LLC谐振变换器谐振腔切换装置以及控制方法 技术领域
本发明涉及一种LLC谐振变换器谐振腔切换装置以及控制方法，属于电路技术领域。
背景技术
LLC谐振变换器是一种具有软开关特性的高效率变换器，采用变压器隔离结构，广泛应用于高功率需要隔离输出的场合下。
LLC谐振变换器有两个谐振频率，一个是谐振电容和谐振电感串联工作时的谐振频率f 0，其公式为
Figure PCTCN2019130569-appb-000001
另一个谐振频率为谐振电容和谐振电感加励磁电感串联工作时的谐振频率f p，其公式为
Figure PCTCN2019130569-appb-000002
显然有f 0＞f p。
对于一个固定的谐振腔，LLC谐振变换器通过改变电路的工作频率f s来调节输出电压，电路工作谐振频率f 0时其电压增益为1，工作在欠谐振频率(f s＜f 0)时电压增益大于1，工作在过谐振频率(f s＞f 0)时电压增益小于1。
为保证原边开关管的软开关，工作频率不能低于f p，否则LLC谐振变换器将进入容性区而丢失零电压开通，造成较大的开关损耗，因此变换器应工作在谐振频率附近且保证f s＞f p。
当工作频率f s低于谐振频率f 0时，变压器励磁电感参与谐振，这将会造成了原边电流环流，从而导致环流损耗，环流损耗主要是磁损，且电压增益越大其工作频率越低，电路中的环流损耗就越大，效率越低。
当工作频率f s高于谐振频率f 0时，变换器副边的整流二极管会进入硬关断模式，存在反向恢复损耗，效率也会下降。
电路工作在升压模式时，过低的工作频率可能会导致励磁电感电流过大，循环能量很大导致损耗很大；工作在降压模式时，受限于电路参数(如谐振电感和励磁电感的比值)，电压的降低与工作频率不是线性关系，输出电压降低范围也受限。
因此，对于一个固定谐振腔的LLC变换器，在合理的参数设计条件下，LLC谐振变换器的电压变化适应范围有限，即(最大输入*最大输出)与(最小输入*最小输出)的比值需要较小，过大的电压变化范围会导致LLC变换器的性能急剧变差，甚至无法正常工作。因此，如拓宽LLC谐振变换器的电压变化适应范围一直是LLC变换器的一个研究热点。
发明内容
本发明要解决的技术问题是现有技术存在的上述问题，设计一种LLC谐振变换器谐振腔切换装置以及控制方法，这种LLC谐振变换器谐振腔切换装置及控制策略具有以下功能：通过切换装置改变变换器的谐振腔参数，并通过谐振参数的变化来改变电路的谐振频率，进而达到增大增益范围的效果，扩大LLC变换器的电压变化适应范围。
为解决上述技术问题，本发明采用的技术方案是：一种LLC谐振变换器谐振腔切换装置，它包括输入电压，输入开关网络(或者称为输入逆变桥)，第一谐振腔，第二谐振腔，切换装置，第一输出整流滤波装置和第二输出整流滤波装置。其特征是，包括：
(1)输入电压通常为一直流电压，也成为直流母线，与输入开关网络耦接。所述输入电压幅度大小可变，也可以恒定不变。
(2)与输入电压耦接的输入开关网络，其作用是将直流电逆变为高频的方波交流电，作为谐振网络的输入。
(3)第一谐振腔，所述谐振腔包括谐振电容、谐振电感、隔离变压器，其作用是将高频方波交流通过谐振腔的作用，将输入能量耦合到变压器的输出侧，并且通过谐振网络的谐振，实现输入开关网络中开关的软开关(或者称为零电压开通)，减小开关损耗。所述谐振腔有一个输入端口和一个输出端口，所述输入端口接收输入开关网络的输出信号，所述输出端口与相应的输出整流装置。
(4)切换装置，其作用是提供导通和关断两种模式，所述切换装置串联在所述第一谐振腔串联输入的一端和所述输入开关网络的输出的一端之间，在导通模式下，将第一谐振腔的输入耦接至输入开关网络的输出。
(5)第二谐振腔，所述谐振腔包括谐振电容、谐振电感、隔离变压器，所述第二谐振腔耦接至切换装置的两端。在所述切换装置导通模式下被旁路，在所述切换装置关断模式下，所述第二谐振腔与所述第一谐振腔相串联，共同耦接到输入开关网络的输出端。
(5)第一输出整流装置和第二输出整流装置，分别具有一个输入端口和一个输出端口，输入端口分别耦接至第一谐振腔的输出端口与第二谐振腔的输出端口，接受相应谐振腔的输出信号，并得到一个直流输出信号。所述第一输出整流装置和第二输出整流装置的输出端口并联，与负载相耦合
本发明的一种LLC谐振变换器谐振腔切换控制策略，该方法如下：
为了得到较好的变换效率，在开关频率确定后，LLC谐振变换器的谐振腔参数设计相对较为固定，变压器匝比的设计(本文中匝比指代变压器原边匝数和副边匝数的比)基本上决定了变换器的电压增益范围，按照折算到输入侧，增益变化范围通常在2倍以内。在一般情况下，匝比通常选择在额定输入与额定输出的比值，使得变换器在大部分时间内工作效率较高的点，具备一定的电压变化范围适应能力，如电压变换范围在2倍以内。但在一些应用场合，电压的变换很宽。在一些应用中，我们假设输出电压不变，输入电压的最大和最小值变化超过4，甚至更高。因此，变压器的设计变得非常困难，大的变压器匝比设计无法兼顾高 输入电压；过小的变压器匝比设计无法兼顾低输入电压。为了适应更宽的电压变化范围，将LLC谐振变换器中的谐振腔分为两个，将切换装置串联在第一谐振腔上，并将第二谐振腔与切换装置并联，当切换装置导通时仅有第一谐振腔工作，第二谐振腔被短路；当切换装置断开时，第一谐振腔和第二谐振腔串联，当谐振参数相同时两谐振腔各分一半输入电压，在要求输出电压固定的场合可将输入电压范围提高一倍，相当于拓宽了LLC谐振变换器的增益范围。
本发明的一种LLC谐振变换器谐振腔切换装置以及控制方法，为保证切换前后电路能正常工作，该切换装置在其导通状态下应能保证电流能正反两个方向通过，关断状态下保证至少能承受输入电压峰值的一半大小。
附图说明
图1本发明的一种实施方式框图；
图2输入开关网络实施例。
图3谐振腔实施例示意图；
图4切换装置的示意图及实施例；
图5输出整流装置一种实施例；
图6本发明的一个实施例。
具体实施方式
下面结合附图对本发明做进一步描述。以下实施例仅用于更加清楚地说明本发明的技术方案，而不能以此来限制本发明的保护范围。
采用本发明的LLC谐振变换器可达到的某些既定参数要求：
(1)工作电源电压范围：AC80～265V；
(2)所使用的切换装置处于通态时可使电流双向流动，且断态时至少可承受输入电压的一半以上。
如图1所示为本发明的一种LLC谐振变换器谐振腔切换装置以及控制策略一个实施方式，它包括输入电源，输入开关网络，谐振腔A，谐振腔B，切 换装置，输出整流装置A和输出整流装置B。与输入电源耦接的输入开关网络，其作用是将输入电源逆变为所需频率的高频方波交流电。连接于输入开关网络之后的谐振腔A，包括谐振电容、谐振电感、隔离变压器，其作用是将高频方波交流通过谐振腔的作用，将输入能量耦合到变压器的输出侧，并且通过谐振网络的谐振，实现输入开关网络中开关的软开关(或者称为零电压开通)，减小开关损耗。所述谐振腔有一个输入端口和一个输出端口，所述输入端口接收输入开关网络的输出信号，所述输出端口与相应的输出整流装置。谐振腔A的一个输入端与切换装置相串联，并通过切换装置的另一端耦接至输入开关网络的一个输出端，谐振腔A的另一输入端耦接至输入开关网络的另一个输出端。谐振腔B与谐振腔A类似，也包括谐振电容、谐振电感、隔离变压器，作用也类似。谐振腔B的输入端连接至切换装置的两端，即与切换装置并联。切换装置在控制信号的作用下，提供导通和关断两种模式。输出整流装置A和输出整流装置B分别于谐振腔A与谐振腔B的输出端耦接，其作用是将谐振腔传递的输出信号进行整流，得到相应的直流输出。所述切换装置，在导通模式下，谐振腔B被切换装置旁路；在关断模式下，谐振腔B的输入端与谐振腔A的输入端串联后耦接至输入开关网络。
在上述实施例中，输入电压也可以通过交流输入整流得到，如市电整流得到一个幅值变化的直流电压。在一个实施例中，将频率为50/60Hz，电压有效值为80-265V的交流电，整流成为一个直流。最为传统的实施方式为二极管整流，加上电适当的滤波器，如电容或者LC滤波器等。
图2所示为输入开关网络的示意图，图2中示出了全桥结构和两种半桥结构，即半桥结构-1和半桥结构-2。本领域技术人员应该明白，还可以有其他形式的开关网络，将直流转换成高频交流信号。图中所示开关网络的开关，可以是金属氧化物半导体场效应管(MOSFET)、双极型晶体管(BJT)或者绝缘栅晶体管(IGBT)等。在全桥结构中，一种实施方式中，对角开关交替导通，将直流输入电压你变成高频交流方波信号。本领域技术人员应该明白，也可以有其他多种实施方式，这里不再赘述。
图3所示为谐振腔A或谐振腔B的实施方式示意图。谐振腔通常包括谐振电容Cr，谐振电感Lr，变压器T，以及变压器T的励磁电感Lm组成。其中谐振电感Lr可以是一个独立电感。在一些场合下，谐振电感可以是变压器的漏感，与变压器本身集成在一起，物理上不可见。变压器的励磁电感本身与变压是完全集成的，不是一个独立电感。谐振电容可以串联在谐振腔的任意输入端(如方式1和方式2所示)。在一些实施例中，谐振电容可以输入滤波电容集成，如与图2中所示的半桥结构-2结合，半桥结构-2中的两个电容可以作为谐振电容。谐振腔的输入端通常耦接至输入开关网络的输出端，接收开关网络的输出信号，并将功率传送到变压器的另一边(副边侧)，实现能量的隔离传输。同时，通过谐振网络的谐振，实现输入开关网络中开关的软开关(或者称为零电压开通)，以及输出整流装置中开关的软关断，减小开关损耗。
切换装置为一个受控的开关，包括导通和关断两种状态，通常包括一个输入端、一个输出端和一个控制端，如图4(A)所示。控制端基于控制信号来控制切换装置处于导通或者关断状态。切换装置在一个实施方式中可以是一个继电器。在另一个实施方式中，也可以基于半导体开关实现，如采用两个背靠背的MOSFET实现，如图4(B)所示。在用MOSFET的实施方式中，控制端电压高于MOSFET的开启阈值，则切换装置导通，如低于开启阈值，则关断。本领域技术人员应该明白，还可以有其他形式的半导体开关实施方式，但不影响本发明的实质。
图5所示是输出整流装置的一种实施方式，即全桥整流方式，采用4个二极管将变压器输出侧的高频交流信号整流成为直流输出。整流装置中也可以包括滤波装置，如电容滤波。本领域技术人员基于公知常识可知，整流装置可以有多种实施方式，如全波整流、倍压整流等结构，这里不再赘述。整流装置中，可以采用二极管整流，也可以采用MOSFET实施同步整流，或者二极管与MOSFET混合组成的混合整流方式。但不论采用何种结构、何种器件，均是将变压器的高频输出交流整流成直流信号，不影响本发明的本质。
下面以一具体实例说明切换装置的工作过程。假定一个LLC变换器，其输入电压的工作范围为100V～400V，输出电压为300V不变。在传统设计中， 由于输入电压的变化范围为4倍，导致参数设计困难，变换器效率较低。为了改善其输入电压的适应范围，在一种实施方式中，可将输入电压分为两档，一档为100V～200V的低压档，一档为200V～400V高压档。在低压档，将切换装置导通，此时仅有谐振腔A参与谐振，谐振腔B被短路。当输入为高压档时，此时输入电压相比低压档增加了一倍，将切换装置关断，两谐振腔串联，同时参与谐振，假设谐振腔A与B的参数相同，两谐振腔两端的电压相等，各为输入电源电压的一半，因此两谐振腔的变压器两端电压也相同，又由于与谐振腔A、B后级相连的输出整流装置A、B的输出端并联，所以高压档在切换装置关断后的负载电压等效于低压档切换装置导通时的负载电压，此时由于负载未变，两种范围内的输出功率相等，这就完成了高低压变化的切换过程。同时由于谐振腔B两端的电压为输入电源电压的一半，故与之并联的切换装置所承受的电压也为输入电源电压的一半。
图6是基于上述描述所构成的一个带有切换装置的具体LLC谐振变换器的实施示意图。
综上所述，本发明采用的一种LLC谐振变换器谐振腔切换装置以及控制策略，通过切换装置改变LLC变换器的谐振腔，很好地解决了LLC谐振变换器增益变化范围小的缺点，增大输入、输出电压的变化范围，也保证了器件工作的安全性与可靠性。
以上所述仅是本发明的优选实施方案，应当指出，对于本技术领域的普通技术人员来说，再不脱离本发明技术原理的前提下，还可以做出若干改进和变形，这些改进和变形也应视为本发明的保护范围。

Claims (2)

  1. 一种LLC谐振变换器谐振腔切换控制方法，其特征在于，该方法是将LLC谐振变换器中的谐振腔分为两个，将用于控制导通或关断的切换装置串联在第一谐振腔上，并将第二谐振腔与切换装置并联，当切换装置导通时仅有第一谐振腔工作，第二谐振腔被短路；当切换装置断开时，第一谐振腔和第二谐振腔串联，当谐振参数相同时两谐振腔各分一半输入电压，在要求输出电压固定的场合可将输入电压范围提高一倍。
  2. 一种LLC谐振变换器谐振腔切换装置，其特征在于，包括输入电压、输入开关网络、第一谐振腔、第二谐振腔、切换装置、第一输出整流滤波装置和第二输出整流滤波装置；其中输入电压为一直流电压，与输入开关网络耦接；输入开关网络用于将直流电逆变为高频的方波交流电作为谐振网络的输入；第一谐振腔包括谐振电容、谐振电感、隔离变压器，其作用是将高频方波交流通过谐振腔的作用，将输入能量耦合到变压器的输出侧，并且通过谐振网络的谐振，实现输入开关网络中开关的软开关，减小开关损耗，第一谐振腔的输入端口接收输入开关网络的输出信号，其输出端口与第一输出整流滤波装置相连；切换装置具有导通和关断两种模式，串联在第一谐振腔输入端和所述输入开关网络的输出端之间，在导通模式下，将第一谐振腔的输入耦接至输入开关网络的输出；第二谐振腔耦接在切换装置的两端，在所述切换装置导通模式下被旁路，在所述切换装置关断模式下，所述第二谐振腔与所述第一谐振腔相串联，共同耦接到输入开关网络的输出端，第二谐振腔的输出端与第二输出整流滤波装置相连，所述第一输出整流装置和第二输出整流装置的输出端口并联，与负载相耦合。
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Citations (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102684464A (zh) * 2011-03-15 2012-09-19 雅达电子国际有限公司 谐振变换器装置及用于谐振变换器装置的方法
US20140254208A1 (en) * 2013-03-05 2014-09-11 Futurewei Technologies, Inc. Auxiliary Resonant Apparatus for LLC Converters
CN207234677U (zh) * 2017-09-20 2018-04-13 桂林电子科技大学 交错并联的llc谐振变换器
CN109067190A (zh) * 2018-09-28 2018-12-21 中国石油大学(华东) 一种宽增益的llc谐振变换器
CN109428493A (zh) * 2017-08-28 2019-03-05 欧姆龙株式会社 Llc谐振变换器
CN109478852A (zh) * 2016-07-27 2019-03-15 株式会社村田制作所 并联和串联的多相llc转换器
KR20190072794A (ko) * 2017-12-18 2019-06-26 순천향대학교 산학협력단 ２개의 변압기 구조를 사용해 균형있는 ２차측 전류를 갖는 고효율 ｌｌｃ 공진 컨버터

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106169873A (zh) * 2016-07-21 2016-11-30 连云港杰瑞电子有限公司 适用于高压或大电流输出的混合串并联全桥电路及其控制方法
CN106655788A (zh) * 2016-12-30 2017-05-10 上海联影医疗科技有限公司 一种谐振变换器
CN108122664A (zh) * 2018-02-08 2018-06-05 东南大学 一种同步整流管集成的匝比可调节矩阵变压器
CN109687716A (zh) * 2018-12-30 2019-04-26 杭州中恒电气股份有限公司 一种串并联无缝转换的谐振变换器

Patent Citations (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102684464A (zh) * 2011-03-15 2012-09-19 雅达电子国际有限公司 谐振变换器装置及用于谐振变换器装置的方法
US20140254208A1 (en) * 2013-03-05 2014-09-11 Futurewei Technologies, Inc. Auxiliary Resonant Apparatus for LLC Converters
CN109478852A (zh) * 2016-07-27 2019-03-15 株式会社村田制作所 并联和串联的多相llc转换器
CN109428493A (zh) * 2017-08-28 2019-03-05 欧姆龙株式会社 Llc谐振变换器
CN207234677U (zh) * 2017-09-20 2018-04-13 桂林电子科技大学 交错并联的llc谐振变换器
KR20190072794A (ko) * 2017-12-18 2019-06-26 순천향대학교 산학협력단 ２개의 변압기 구조를 사용해 균형있는 ２차측 전류를 갖는 고효율 ｌｌｃ 공진 컨버터
CN109067190A (zh) * 2018-09-28 2018-12-21 中国石油大学(华东) 一种宽增益的llc谐振变换器

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
HU, H. , FANG, X. , CHEN, F. , SHEN, Z. J. ,BATARSEH, I: "A Modified High-Efficiency LLC Converter With Two Transformers for Wide Input-Voltage Range Applications", IEEE TRANSACTIONS ON POWER ELECTRONICS, vol. 28, no. 4, 1 January 2013 (2013-01-01), pages 1946 - 1960, XP009528376, ISSN: 0885-8993, DOI: 10.1109/TPEL.2012.2201959 *
WENJIN SUN, ET AL.: "Modified High-Efficiency LLC Converters With Two split ResonantBranches for wide Input-Voltage Range Applications", IEEE TRANSACTIONS ON POWER ELECTRONICS, vol. 33, no. 9, 30 September 2018 (2018-09-30), XP011686235, DOI: 10.1109/TPEL.2017.2773484 *

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