WO2020158859A1 - 共振型コンバータ、その制御回路及び制御方法 - Google Patents

共振型コンバータ、その制御回路及び制御方法 Download PDF

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Publication number
WO2020158859A1
WO2020158859A1 PCT/JP2020/003418 JP2020003418W WO2020158859A1 WO 2020158859 A1 WO2020158859 A1 WO 2020158859A1 JP 2020003418 W JP2020003418 W JP 2020003418W WO 2020158859 A1 WO2020158859 A1 WO 2020158859A1
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Prior art keywords
voltage
signal
resonant converter
control circuit
wave signal
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Ceased
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PCT/JP2020/003418
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English (en)
French (fr)
Japanese (ja)
Inventor
上松　武
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Omron Corp
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Omron Corp
Omron Tateisi Electronics Co
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Application filed by Omron Corp, Omron Tateisi Electronics Co filed Critical Omron Corp
Priority to US17/274,643 priority Critical patent/US11515799B2/en
Priority to CN202080004899.8A priority patent/CN112640287B/zh
Priority to EP20749384.2A priority patent/EP3836378A4/en
Publication of WO2020158859A1 publication Critical patent/WO2020158859A1/ja
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33571—Half-bridge at primary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0012—Control circuits using digital or numerical techniques
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0043—Converters switched with a phase shift, i.e. interleaved
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/01—Resonant DC/DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/285—Single converters with a plurality of output stages connected in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0025—Arrangements for modifying reference values, feedback values or error values in the control loop of a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0032—Control circuits allowing low power mode operation, e.g. in standby mode
    • H02M1/0035—Control circuits allowing low power mode operation, e.g. in standby mode using burst mode control
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
    • Y02P80/00—Climate change mitigation technologies for sector-wide applications
    • Y02P80/10—Efficient use of energy, e.g. using compressed air or pressurized fluid as energy carrier

Definitions

  • the present invention relates to a resonance converter control circuit, a control method thereof, and a resonance converter.
  • hysteresis control is generally known as a method of controlling the output voltage of a resonance type DCDC converter (for example, see Non-Patent Documents 1 and 2).
  • the output voltage Vo is detected, and the switching circuit is controlled so that the detected output voltage Vo falls within a predetermined allowable range including the target voltage Vd.
  • the resonant converter can be controlled while suppressing the error between the output voltage Vo and the target voltage Vd to a predetermined value or less.
  • Non-Patent Documents 1 and 2 there is a limit in the control accuracy because the output voltage has a predetermined allowable width. Furthermore, due to factors such as the magnitude of the input voltage or the magnitude of the load, the duty and cycle of the drive signal that controls the resonant converter can change, so the behavior of the resonant converter and the behavior such as the transition of the output voltage can be predicted. Difficult, which also makes control difficult.
  • An object of the present invention is to solve the above problems and to control the output voltage of a resonant converter more precisely and easily than in the prior art, a resonant converter control circuit, a control method therefor, and a resonant converter. To provide.
  • a resonant converter control circuit is a resonance converter that converts an input DC voltage into an AC voltage, causes the converted AC voltage to resonate through a resonance circuit, and then converts the AC voltage into a DC voltage for output.
  • a quiescent period for pausing the resonant converter and the resonant converter control circuit generates first oscillation means for generating a clock signal having a predetermined fundamental frequency, and a sawtooth wave signal synchronized with the clock signal.
  • Second oscillating means a third oscillating means for generating a rectangular wave signal having a predetermined duty and a predetermined frequency higher than the frequency of the sawtooth signal, an output voltage of the resonant converter, and a target of the output voltage.
  • a sawtooth signal is generated based on a voltage difference between the target voltage and the target voltage, and the comparison signal indicating the drive period is obtained by comparing the sawtooth signal with a threshold signal indicating the ratio of the drive period and the rest period.
  • a comparison means for outputting, a logic operation means for calculating a logical product between the comparison signal and the rectangular wave signal, generating a drive control signal indicating the calculation result, and controlling the drive of the resonant converter.
  • the above difference voltage is the voltage that has passed through the compensator for compensating and stabilizing the target voltage waveform.
  • the above rectangular wave signal has a duty of 50%.
  • the third oscillating means multiplies the clock signal to generate the rectangular wave signal.
  • a control method for a resonant converter control circuit converts an input DC voltage into an AC voltage, causes the converted AC voltage to resonate through a resonance circuit, and then converts the DC voltage into a DC voltage.
  • a control method of a resonance converter control circuit for controlling an output resonance type converter so that an output DC voltage reaches a predetermined target voltage, wherein each cycle in drive control of the resonance type converter is a resonance type The control method has a driving period for driving the converter and a rest period for stopping the resonant converter, and the control method generates a clock signal having a predetermined fundamental frequency, and generates a sawtooth wave signal in synchronization with the clock signal.
  • the output voltage of the resonant converter and a target voltage that is a target value of the output voltage are a target value of the output voltage. Comparing the sawtooth wave signal generated based on the difference voltage with a threshold value signal indicating the ratio of the drive period and the idle period, outputting a comparison signal indicating the drive period, and a comparison signal, Calculating a logical product with the rectangular wave signal and generating a drive control signal as a result of the calculation to drive and control the resonant converter.
  • the control method of the resonant converter control circuit described above further includes a step of generating a differential voltage which is a voltage that has passed through a compensator for compensating and stabilizing the target voltage waveform.
  • the rectangular wave signal has a duty of 50%.
  • the step of generating the rectangular wave signal includes multiplying the clock signal to generate the rectangular wave signal.
  • a resonant converter includes any one of the resonant converter control circuits described above, converts an input DC voltage into an AC voltage, and converts the converted AC voltage via the resonant circuit. After resonating, a main circuit for converting to a DC voltage and outputting the DC voltage is provided.
  • the resonance type converter includes a plurality of N main circuits connected in parallel and N resonance type converter control circuits for controlling the N main circuits, respectively.
  • the resonant converter control circuits generate sawtooth signals having a phase difference of 360/N degrees with each other.
  • the N resonance type converter control circuits include one first oscillating means and one second oscillating means, and N resonance type converter control circuits are provided. At least a portion of the circuit shares the first and second oscillating means.
  • the output voltage of the resonant converter can be controlled more accurately and easily than in the conventional technique.
  • FIG. 3 is a block diagram showing a configuration example of a resonant converter 10 according to the first embodiment.
  • 2 is a circuit diagram showing a configuration example of a main circuit 100 of FIG. 1.
  • FIG. 2 is a block diagram showing a configuration example of a resonant converter control circuit 140 in FIG. 1.
  • FIG. 3 is a timing chart showing an example of operation waveforms of signals and the like in each unit of the resonant converter control circuit 140 of FIG. 1.
  • 7 is a block diagram showing a configuration example of a resonance converter 10L according to a second embodiment.
  • FIG. 6 is a timing chart showing an example of operation waveforms of signals and the like in each unit of the resonance converter 10L of FIG.
  • FIG. 1 is a block diagram showing a configuration example of a resonance converter 10 according to the first embodiment.
  • a resonant converter DCDC converter that converts an input DC voltage into an AC voltage, causes the AC voltage to resonate through a resonance circuit 120, and then converts the DC voltage into a DC voltage for output.
  • the resonant converter 10 includes a main circuit 100 and a resonant converter control circuit 140.
  • the main circuit 100 includes a switching circuit 110, a resonance circuit 120, and a rectifying/smoothing circuit 130. Further, the DC voltage source 5, the load 15 and the controller 20 are connected to the resonance converter 10.
  • an external DC voltage source 5 generates a DC voltage Vi and outputs it to the switching circuit 110 of the resonant converter 10. Further, the controller 20 outputs a signal Svd indicating the target voltage Vd, which is the target value of the output voltage of the resonant converter 10, to the resonant converter 10.
  • the resonance converter 10 converts the input DC voltage Vi into a DC output voltage Vo based on the signal Svd indicating the target voltage and supplies the DC output voltage Vo to the external load 15.
  • the resonance converter control circuit 140 generates a drive signal Sdrv for controlling the main circuit 100 based on the output voltage Vo of the main circuit 100 and the signal Svd indicating the target voltage Vd, and outputs the drive signal Sdrv to the main circuit 100.
  • the main circuit 100 is feedback-controlled. As a result, the main circuit 100 converts the input voltage Vi into the output voltage Vo based on the drive signal Sdrv from the resonant converter control circuit 140 and supplies the output voltage Vo to the load 15.
  • the drive signal Sdrv is an example of the “drive control signal” in the present invention.
  • the switching circuit 110 switches the DC input voltage Vi according to the drive signal Sdrv from the resonant converter control circuit 140, and outputs the AC voltage generated by the switching to the rectifying and smoothing circuit 130 via the resonant circuit 120.
  • the rectifying/smoothing circuit 130 rectifies and smoothes the input AC voltage, generates a DC output voltage Vo, and outputs the DC output voltage Vo to the load 15.
  • FIG. 2 is a circuit block diagram showing a configuration example of the main circuit 100 of FIG.
  • the main circuit 100 is an asymmetric half-bridge type LLC converter.
  • the main circuit 100 has MOSFETs 111 and 112, a transformer Tr, a resonance capacitor C1, diodes D1 and D2, and a smoothing capacitor C2.
  • MOSFETs 111 and 112 are n-channel type MOSFETs.
  • the MOSFETs 111 and 112 are respectively driven by the drive signal Sdrv and switch ON/OFF of conduction.
  • the MOSFET 112 is controlled to be off while the MOSFET 111 is on, and conversely, the MOSFET 112 is controlled to be on while the MOSFET 111 is off.
  • the switching circuit 110 switches the input voltage Vi according to the drive signal Sdrv, and outputs the AC voltage generated by the switching to the rectifying and smoothing circuit 130 via the resonance circuit 120.
  • the diodes D1 and D2 and the smoothing capacitor C2 of the rectifying and smoothing circuit 130 supply the output voltage Vo to the load 15 after full-wave rectifying and smoothing the AC voltage from the resonance circuit 120.
  • FIG. 3 is a block diagram showing a configuration example of the resonant converter control circuit 140 of FIG.
  • the resonant converter control circuit 140 includes a control signal generator 150 and a drive signal generator 160.
  • the control signal generator 150 includes an output voltage detection circuit 151, a comparator 152, a compensator 153, a clock oscillator 154, and a resonant converter oscillator 155.
  • the drive signal generator 160 also includes a burst control oscillator 161, a comparator 162, an AND gate 163, and a drive circuit 164.
  • the output voltage detection circuit 151 generates an output voltage signal Svo corresponding to the output voltage Vo of the main circuit 100 and outputs it to the comparator 152.
  • the comparator 152 compares the output voltage signal Svo with the target voltage signal Svd from the controller 20 and based on the difference between the output voltage Vo and the target voltage Vd, for example, is a low-pass filter and compensates the target voltage waveform.
  • a threshold signal Sth indicating a control amount for achieving the target voltage Vd is generated and output to the comparator 162.
  • the clock oscillator 154 generates a clock signal Sclk which is a pulse signal having a predetermined basic frequency and outputs it to the resonant converter oscillator 155 and the burst control oscillator 161.
  • the burst control oscillator 161 generates a sawtooth signal Ssaw having a predetermined cycle Tsaw, a predetermined maximum value Asaw, and a minimum value of 0 in synchronization with the clock signal Sclk, and outputs the sawtooth signal Ssaw to the comparator 162.
  • the maximum value Asaw of the sawtooth signal Ssaw will be described later.
  • the comparator 162 compares the sawtooth wave signal Ssaw with the threshold value signal Sth and has a high level during a period when the value of the sawtooth wave signal Ssaw is equal to or less than the value of the threshold value signal Sth and the value of the sawtooth wave signal Ssaw is In a period larger than the value of the threshold signal Sth, the comparison signal Scmp having a low level is generated and output to the AND gate 163.
  • a period in which the comparison signal Scmp has a high level is called a drive period Pbst
  • a period in which the comparison signal Scmp has a low level is called an idle period Pslp.
  • the maximum value Asaw of the sawtooth wave signal Ssaw output from the burst control oscillator 161 is when the voltage indicated by the target voltage signal Svd is equal to the output voltage Vo when the resonant converter 10 is controlled to have the maximum output.
  • And is set equal to the value of the threshold signal Sth output from the compensator 153.
  • the duty of the comparison signal Scmp becomes equal to the ratio of the value of the threshold signal Sth to the maximum value Asaw of the sawtooth wave signal Ssaw.
  • the resonance converter oscillator 155 multiplies the clock signal Sclk to generate a rectangular wave signal Srec which is a pulse signal having a duty of 50% and outputs the rectangular wave signal Srec to the AND gate 163.
  • the frequency of the rectangular wave signal Srec is set to be an integral multiple (for example, 5 times, 8 times or 10 times) of the frequency of the sawtooth wave signal Ssaw. That is, the cycle Trec of the rectangular wave signal Srec is set to be an integral multiple of the cycle Tsaw of the sawtooth wave signal Ssaw (for example, 1/5, 1/8, or 1/10). To be done.
  • the frequency of the sawtooth wave signal Ssaw may be set to 10 kilohertz and the frequency of the rectangular wave signal Srec may be set to 80 kilohertz.
  • the resonant converter oscillator 155 is an example of the "first oscillating means" in the present invention.
  • the AND gate 163 takes the logical product of the comparison signal Scmp and the rectangular wave signal Srec to generate the gate signal Sg, and outputs the gate signal Sg to the drive circuit 164.
  • the drive circuit 164 generates a drive signal Sdrv based on the gate signal Sg to drive and control the switching circuit 110.
  • FIG. 4 is a timing chart showing an example of operation waveforms of signals and the like in each unit of the resonant converter control circuit 140 of FIG.
  • the comparator 162 compares the sawtooth wave signal Ssaw from the burst control oscillator 161 with the threshold signal Sth from the compensator 153 to generate a comparison signal Scmp shown in FIG.
  • a period in which the comparison signal Scmp has a high level is a drive period Pbst, and a period in which the comparison signal Scmp has a low level is a rest period Pslp.
  • the resonant converter oscillator 155 generates a rectangular wave signal Srec which is a pulse signal having a predetermined cycle Trec and a duty of 50%, and outputs the rectangular wave signal Srec to the AND gate 163.
  • the resonant converter oscillator 155 is an example of the "third oscillating means" in the present invention.
  • the gate signal Sg of the AND gate 163 is a signal obtained as a result of calculating the logical product of the comparison signal Scmp and the rectangular wave signal Srec. Therefore, the gate signal Sg of the AND gate 163 is a signal having the rectangular wave signal Srec in the driving period Pbst and always having the low level in the rest period Pslp.
  • the drive circuit 164 drives and controls the switching circuit 110 of the main circuit 100 by generating a drive signal Sdrv based on the gate signal Sg and outputting the drive signal Sdrv to the main circuit 100.
  • the resonant converter is controlled by the rectangular wave signal Srec during the driving period Pbst, and is not driven and pauses during the pausing period Pslp.
  • the duty of the comparison signal Scmp indicates the ratio of the driving period Pbst to the cycle Tsaw of the sawtooth wave signal Ssaw. Further, the value of the threshold signal Sth changes due to the difference between the output voltage Vo and the target voltage Vd, and the duty of the comparison signal Scmp also changes accordingly. Thereby, the drive circuit 164 can generate the drive signal Sdrv for controlling so as to correct the difference between the current output voltage Vo and the target voltage Vd.
  • the output voltage Vo is higher than the target voltage Vd
  • the value of the threshold signal Sth becomes smaller than the value immediately before, and the duty of the comparison signal Scmp decreases. Therefore, the drive period Pbst in the gate signal Sg becomes shorter than the immediately preceding period, and the number of pulse waves included in the drive signal Sdrv decreases. Therefore, the output voltage Vo of the main circuit 100 is controlled to decrease and approach the target voltage Vd.
  • each cycle in the drive control of the resonant converter 10 has the drive period Pbst for driving the resonant converter 10 and the pause period Pslp for suspending the resonant converter 10.
  • the resonance converter 10 is controlled by the rectangular wave signal Srec which is a periodic pulse signal having a predetermined duty.
  • the value of the threshold signal Sth indicating the ratio between the drive period Pbst and the rest period Pslp changes based on the difference voltage between the output voltage Vo and the target voltage Vd.
  • the output voltage Vo of the resonant converter 10 is controlled to be the target voltage Vd.
  • the output voltage Vo of the resonant converter 10 is compared with the conventional technique so that it becomes the target voltage Vd. Control with high accuracy. Further, the cycle of drive control of the resonant converter 10 is always constant regardless of factors such as the magnitude of the input voltage Vi or the magnitude of the load 15. Therefore, the ripples in the output voltage Vo of the main circuit 100 are periodic and can be easily predicted. As described above, according to the present embodiment, it is possible to precisely and easily control the output voltage Vo of the resonance converter 10 so as to reach the target voltage Vd, as compared with the related art.
  • FIG. 5 is a block diagram showing a configuration example of the resonant converter 10L according to the second embodiment. 5, the resonant converter 10L differs from the resonant converter 10 of FIG. 1 in the following points.
  • the resonant converter 10L further includes a main circuit 100A.
  • the resonant converter 10L further includes a resonant converter control circuit 140A (not shown) that drives and controls the main circuit 100A.
  • the burst control oscillator 161A of the resonant converter control circuit 140A operates with a phase shifted by 180 degrees from the burst control oscillator 161 of the resonant converter control circuit 140.
  • the main circuit 100A has the same configuration and operation as the main circuit 100.
  • Resonant converter control circuit 140A is configured similarly to resonant converter control circuit 140, and includes control signal generation unit 150 and drive signal generation unit 160A.
  • the control signal generator 150 is shared with the resonant converter control circuit 140.
  • FIG. 6 is a timing chart showing an example of operation waveforms of signals and the like in the resonant converter 10L of FIG.
  • the burst control oscillator 161A operates with a phase shifted by 180 degrees compared with the burst control oscillator 161. Therefore, the sawtooth signals Ssaw and SsawA operate with a shift of Tsaw/2. This causes a shift of Tsaw/2 between the gate signals Sg and SgA. Therefore, the driving period in the main circuit 100A is shifted from the driving period Pbst (not shown) in the main circuit 100 by Tsaw/2. By doing so, a phase difference of 180 degrees occurs between the ripples in the output voltages of the two main circuits 100 and 100A. Since the ripples cancel each other out in the combined output voltage Vo, the error due to the ripples is reduced, and control with higher accuracy than in the first embodiment becomes possible.
  • resonant converter control circuits 140 and 140A share control signal generating unit 150, but the present invention is not limited to this, and these may not be shared.
  • the resonant converter control circuit 140A may newly include a control signal generation unit 150A that operates in the same manner as the control signal generation unit 150.
  • the resonant converter 10L includes two main circuits.
  • the present invention is not limited to this, and the number of main circuits included in the resonant converter 10L may be three or more.
  • the resonant converter 10L may include two or more N main circuits connected in parallel and N resonant converter control circuits that control the N main circuits.
  • the N resonant converter control circuits may each have a phase difference of 360/N degrees from each other.
  • at least some of the N resonant converter control circuits may at least partially share their components with each other.
  • the rectangular wave signal Srec and the sawtooth wave signal Ssaw are synchronized with the clock signal Sclk.
  • the present invention is not limited to this, and the rectangular wave signal Srec and the sawtooth wave signal Ssaw may not be synchronized with the clock signal Sclk as long as the frequency of the rectangular wave signal Srec is an integral multiple of the frequency of the sawtooth wave signal Ssaw. ..
  • the rectangular wave signal Srec may not be synchronized with the sawtooth wave signals Ssaw and SsawA.
  • the rectangular wave signal Srec is generated without being synchronized with the clock signal Sclk.
  • the sawtooth wave signal Ssaw and the sawtooth wave signal SsawA are synchronized with each other in order to keep the phase shift between the burst control oscillators 161 and 161A.
  • the comparison signal Scmp is generated using the comparator 162 that compares the sawtooth wave signal Ssaw with the threshold signal Sth.
  • the comparison signals Scmp and ScmpA are generated by using the comparators 162 and 162A that compare the sawtooth wave signals Ssaw and SsawA with the threshold signal Sth.
  • the comparison signals Scmp and ScmpA are merely examples of the “signal indicating the driving period”. Further, these comparators 162 and 162A are merely an example of "comparing means" for generating a signal indicating the driving period. Therefore, the present invention is not limited to this, and the signal indicating the drive period may be any signal as long as it can distinguish the drive period Pbst from the rest period Pslp.
  • an LLC converter is used as the main circuits 100 and 100A.
  • the present invention is not limited to this, and as the main circuit controlled by the resonant converter control circuit, for example, a main circuit such as an E2 class converter, a ⁇ 2 class converter, a series resonant converter, and a parallel resonant converter can be used. ..
  • Controller 100 100A Main circuit 110, 110A Switching circuit 120, 120A Resonant circuit 130, 130A Rectifying and smoothing circuit 140, 140A Resonant type converter control circuit 150 Control signal generator 151 Output Voltage detection circuit 152 Comparator 153 Compensator 154 Clock oscillator 155 Resonant converter oscillator 160, 160A Drive signal generator 161, 161A Burst control oscillator 162, 162A Comparator 163, 163A AND gate 164, 164A Drive circuit

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
PCT/JP2020/003418 2019-02-01 2020-01-30 共振型コンバータ、その制御回路及び制御方法 Ceased WO2020158859A1 (ja)

Priority Applications (3)

Application Number Priority Date Filing Date Title
US17/274,643 US11515799B2 (en) 2019-02-01 2020-01-30 Resonant converter controller circuit for controlling resonant converter converting input DC voltage into DC voltage
CN202080004899.8A CN112640287B (zh) 2019-02-01 2020-01-30 共振型转换器、其控制电路以及控制方法
EP20749384.2A EP3836378A4 (en) 2019-02-01 2020-01-30 RESONANT CONVERTER AND CONTROL CIRCUIT AND CONTROL METHOD THEREOF

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
JP2019017333A JP6988839B2 (ja) 2019-02-01 2019-02-01 共振型コンバータ制御回路とその制御方法及び共振型コンバータ
JP2019-017333 2019-02-01

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WO2020158859A1 true WO2020158859A1 (ja) 2020-08-06

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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115085553A (zh) * 2021-03-16 2022-09-20 宁德时代新能源科技股份有限公司 双向dc/dc变换器及其控制方法、装置、存储介质

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2023049712A (ja) * 2021-09-29 2023-04-10 国立大学法人 岡山大学 制御方法、制御装置及び制御システム

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2010035299A (ja) * 2008-07-28 2010-02-12 Sanken Electric Co Ltd スイッチング電源装置
JP2013078228A (ja) 2011-09-30 2013-04-25 Shindengen Electric Mfg Co Ltd スイッチング電源装置
JP2014027819A (ja) * 2012-07-27 2014-02-06 Rohm Co Ltd Ｄｃ／ｄｃコンバータおよびその制御回路、それを用いた電源装置、電源アダプタおよび電子機器
JP2016152642A (ja) * 2015-02-16 2016-08-22 Tdk株式会社 制御回路およびスイッチング電源装置
JP2018148648A (ja) * 2017-03-02 2018-09-20 京セラドキュメントソリューションズ株式会社 画像形成装置
WO2018198594A1 (ja) * 2017-04-28 2018-11-01 ローム株式会社 Ｌｅｄドライバ、並びに、これを用いるｌｅｄ駆動回路装置および電子機器

Family Cites Families (23)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPH07110132B2 (ja) * 1991-08-22 1995-11-22 日本モトローラ株式会社 電圧変換装置
US5313503A (en) * 1992-06-25 1994-05-17 International Business Machines Corporation Programmable high speed digital phase locked loop
CN1058588C (zh) * 1993-11-30 2000-11-15 王冠国际公司 桥式线性放大器的开关电源
US5384554A (en) * 1993-12-08 1995-01-24 Calcomp Inc. Voltage controlled oscillator circuit employing integrated circuit component ratios
JP2007151381A (ja) * 2005-10-27 2007-06-14 Matsushita Electric Ind Co Ltd Ｄｃ−ｄｃコンバータ及びその制御回路
CN1992493B (zh) * 2005-12-30 2011-05-18 艾默生网络能源系统北美公司 一种谐振直流/直流变换器及其控制方法
US7848117B2 (en) * 2007-01-22 2010-12-07 Power Integrations, Inc. Control arrangement for a resonant mode power converter
CN101291110B (zh) * 2007-04-20 2010-06-02 台达电子工业股份有限公司 具有相对较佳效率的谐振转换器系统及其控制方法
EP2223572A1 (en) * 2007-12-14 2010-09-01 Koninklijke Philips Electronics N.V. Dimmable light generating device
TWI422135B (zh) * 2010-01-18 2014-01-01 Lite On Electronics Guangzhou 電源供應裝置
CN102136801B (zh) * 2010-01-21 2014-02-19 台达电子工业股份有限公司 谐振转换器以及其间歇模式控制方法
CN101951159B (zh) 2010-09-20 2013-04-24 浙江大学 电容隔离型多路恒流输出谐振式直流/直流变流器
KR101198309B1 (ko) * 2010-11-10 2012-11-07 한국전기연구원 스위칭모드 파워서플라이의 스위칭소자 구동장치
TWI422130B (zh) * 2011-01-26 2014-01-01 Macroblock Inc 自適型洩流電路
US9281749B2 (en) * 2012-08-13 2016-03-08 Northrop Grumman Systems Corporation Multiple power supply systems and methods
US9276480B2 (en) * 2013-04-23 2016-03-01 Virginia Polytechnic Institute And State University Optimal trajectory control for LLC resonant converter for LED PWM dimming
US9960673B2 (en) 2015-02-16 2018-05-01 Tdk Corporation Control circuit and switching power supply
CN106953526A (zh) * 2016-01-07 2017-07-14 中兴通讯股份有限公司 一种直流多输入单输出谐振变换器及其控制方法
CN106026754B (zh) * 2016-05-24 2018-12-11 国网福建省电力有限公司 多用途双向功率电力试验电源系统及其控制方法
CN106358354B (zh) * 2016-11-15 2018-04-03 上海联影医疗科技有限公司 X射线高压发生器、谐振变换器的控制电路和控制方法
CN206650891U (zh) * 2017-04-19 2017-11-17 慈溪锐恩电子科技有限公司 一种wifi控制的rgb‑led灯
CN107612335B (zh) * 2017-09-20 2019-10-25 武汉南华工业设备工程股份有限公司 一种三电平llc谐振变换器的交错并联控制方法
US11081966B2 (en) * 2018-12-13 2021-08-03 Power Integrations, Inc. Multi zone secondary burst modulation for resonant converters

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2010035299A (ja) * 2008-07-28 2010-02-12 Sanken Electric Co Ltd スイッチング電源装置
JP2013078228A (ja) 2011-09-30 2013-04-25 Shindengen Electric Mfg Co Ltd スイッチング電源装置
JP2014027819A (ja) * 2012-07-27 2014-02-06 Rohm Co Ltd Ｄｃ／ｄｃコンバータおよびその制御回路、それを用いた電源装置、電源アダプタおよび電子機器
JP2016152642A (ja) * 2015-02-16 2016-08-22 Tdk株式会社 制御回路およびスイッチング電源装置
JP2018148648A (ja) * 2017-03-02 2018-09-20 京セラドキュメントソリューションズ株式会社 画像形成装置
WO2018198594A1 (ja) * 2017-04-28 2018-11-01 ローム株式会社 Ｌｅｄドライバ、並びに、これを用いるｌｅｄ駆動回路装置および電子機器

Non-Patent Citations (3)

* Cited by examiner, † Cited by third party
Title
HELEN DING: "Application Note AN-1160", INFINEON TECHNOLOGIES, 9 October 2010 (2010-10-09), Retrieved from the Internet <URL:https://www.infineon.com/dgdl/an-1160.pdf?fileld=5546d462533600a40153559a85df1115>
KATSUYA HIRACHI: "Circuit Configuration and Operating Principles of LLC DC/DC Converter", MAIZURU COLLEGE OF TECHNOLOGY, 29 May 2014 (2014-05-29), Retrieved from the Internet <URL:http://hirachi.cocolog-nifty.com/kh/files/20140529-3.pdf>
See also references of EP3836378A4

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115085553A (zh) * 2021-03-16 2022-09-20 宁德时代新能源科技股份有限公司 双向dc/dc变换器及其控制方法、装置、存储介质
CN115085553B (zh) * 2021-03-16 2023-12-22 宁德时代新能源科技股份有限公司 双向dc/dc变换器及其控制方法、装置、存储介质
US12126247B2 (en) 2021-03-16 2024-10-22 Contemporary Amperex Technology (Hong Kong) Limited Bi-directional DC/DC converter, control method and apparatus thereof, and storage medium

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