WO2018235455A1 - Alimentation électrique à découpage isolée en courant alternatif triphasé - Google Patents

Alimentation électrique à découpage isolée en courant alternatif triphasé Download PDF

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Publication number
WO2018235455A1
WO2018235455A1 PCT/JP2018/018504 JP2018018504W WO2018235455A1 WO 2018235455 A1 WO2018235455 A1 WO 2018235455A1 JP 2018018504 W JP2018018504 W JP 2018018504W WO 2018235455 A1 WO2018235455 A1 WO 2018235455A1
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current
output end
transformer
input
electrode output
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PCT/JP2018/018504
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English (en)
Japanese (ja)
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羽田　正二
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Ntn株式会社
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Publication of WO2018235455A1 publication Critical patent/WO2018235455A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode

Definitions

  • the present invention relates to an isolated switching power supply that converts three-phase alternating current to direct current.
  • an isolated converter is known as a switching power supply for converting alternating current into direct current.
  • DC / DC converters are disposed after AC / DC conversion by rectifying the alternating current voltage with a rectifying circuit and smoothing with a smoothing capacitor, not limited to single phase and three phase.
  • Patent documents 1 to 7 Also known is a two-stage configuration in which a power factor correction device (PFC) and a DC / DC converter are combined to perform power factor correction.
  • Patent Documents 6 and 7 describe an apparatus for boosting and improving the power factor of a three-phase AC output of a wind power alternator.
  • the present invention has an object of efficiently performing power factor improvement and power conversion with a simple configuration in an insulating switching power supply to which a three-phase alternating current is input.
  • the present invention provides the following configuration.
  • symbol in parenthesis is a code
  • One aspect of the switching power supply of the present invention is (A) first, second and third input terminals (R, S, T) to which three-phase alternating current is input; (B) positive electrode output end (P) and negative electrode output end (N), (C) Each has a primary coil (Lr1, Ls1, Lt1) and a secondary coil (Lr2, Ls2, Lt2), and one end of each primary coil has the first, second and third input ends (R, S) , T) respectively connected to the first, second and third transformers (Tr, Ts, Tt), (D) Each current path between the other end of the primary coil (Lr1, Ls1, Lt1) of each of the first, second and third transformers (Tr, Ts, Tt) and the input side reference potential end (E) First, second and third switching elements (Qr, Qs, Qt) which are on / off controlled by one control signal (Vg) to conduct or interrupt (E) One end of the secondary coil (Lr2, Ls2, Lt2) of each of the
  • the configuration in an isolated switching power supply that receives a three-phase alternating current and performs power factor improvement and power conversion, the configuration can be simplified and the efficiency of the transformer can be improved.
  • FIG. 1 is a view schematically showing an example of the circuit configuration of the embodiment of the switching power supply according to the present invention.
  • FIGS. 2 (a) and 2 (b) are diagrams for explaining the power factor improvement action by the input three-phase alternating current and the switching operation.
  • FIG. 3 is a diagram schematically showing the flow of current during the on period in the T mode of the circuit configuration shown in FIG.
  • FIG. 4 is a diagram schematically showing the potential relationship of the on period on the secondary side of the circuit configuration shown in FIG.
  • FIG. 5 is a diagram schematically showing the flow of current during the off period in the T mode of the circuit configuration shown in FIG.
  • FIG. 6 is a diagram schematically showing the potential relationship of the off period on the secondary side of the circuit configuration shown in FIG.
  • FIG. 1 is a view schematically showing an example of a circuit configuration of an embodiment of the isolated switching power supply of the present invention.
  • the switching power supply of the present invention is a power conversion device that receives three-phase AC power output from an AC generator as input and outputs DC power to a load.
  • three-phase AC power is output from a Y-connected three-phase stator coil in the AC generator.
  • the switching power supply of the present invention is not only a power conversion device but also has a function as a power factor correction device.
  • the power factor correction device aims to make the power factor equal to 1 by making the waveform of the input current the same as that of the input voltage and making the phase match.
  • the switching power supply of the present invention is an insulating type that electrically isolates the input side from the output side.
  • three transformers Tr, Ts and Tt corresponding to each phase are provided.
  • Each of the three transformers Tr, Ts, Tt comprises one primary coil and one secondary coil. It is preferable to use three transformers Tr, Ts, and Tt having the same electromagnetic characteristics, and it is preferable to use a three-phase reactor.
  • the symbols Lr1, Ls1 and Lt1 indicate primary coils of the respective transformers, and the symbols Lr2, Ls2 and Lt2 indicate secondary coils of the respective transformers.
  • each coil is shown by a black circle.
  • a coil when referred to as “one end” and “the other end”, it means a combination of “winding start end” and “winding end” and a combination of “winding end” and “winding start”. Shall be included.
  • One end (in this example, the winding start end) of the primary coils Lr1, Ls1 and Lt1 of the transformer on the input side has three terminals to which a three-phase AC voltage is input: a first input end R, a second input end S and a first The three input terminals T are respectively connected.
  • each phase of the three-phase alternating current is referred to as an R phase, an S phase, and a T phase.
  • the symbol E indicates the input side reference potential end.
  • a positive electrode output terminal P and a negative electrode output terminal N which are two terminals to which a DC voltage is output, are provided.
  • the negative output end N is a secondary side reference potential end. An output voltage is applied to a load (not shown) connected between the positive electrode output terminal P and the negative electrode output terminal N, and an output current flows.
  • each of the three switching elements Qr, Qs, Qt is connected to the other end (in this example, the winding end) of the primary coil Lr1, Ls1, Lt1 of each transformer.
  • the other ends of the switching elements Qr, Qs, Qt are connected to the input side reference potential end E.
  • Each switching element Qr, Qs, Qt has a control end, and each control end conducts or cuts off the current path between the other end of the primary coils Lr1, Ls1, Lt1 and the input side reference potential end E. Each is on / off controlled.
  • the control ends of the three switching elements Qr, Qs, Qt are controlled by one common control signal Vg.
  • the control signal Vg is, for example, a PWM signal having a pulse waveform of a predetermined frequency and a duty ratio. That is, the three switching elements Qr, Qs, Qt are controlled to always be turned on and off at the same time.
  • the switching elements Qr, Qs, Qt are n-channel MOSFETs (hereinafter referred to as "FETQr”, “FETQs”, “FETQt”), one end is a drain, the other end is a source, and the control end is a gate. is there.
  • the control signal Vg is a voltage signal.
  • rectifying elements such as diodes serving as current return paths need to be connected in reverse parallel.
  • first, second and third capacitors are disposed between one end (in this example, the winding start end) of the secondary coils Lr2, Ls2 and Lt2 of each transformer and the negative output end N which is the secondary side reference potential end.
  • C1, C2, and C3 (hereinafter referred to as "sub capacitors") are connected to one another.
  • a smoothing capacitor C4 is connected between the positive electrode output terminal P and the negative electrode output terminal N.
  • first, second and third diodes D1 and D2 which are an example of rectifying elements , D3 are connected respectively.
  • the anodes of the diodes D1, D2 and D3 are connected to the other ends of the secondary coils Lr2, Ls2 and Lt2, respectively, and the cathodes are connected to the positive electrode output terminal P.
  • Each diode D1, D2, D3 conducts the current flowing from the other end of the secondary coil Lr2, Ls2, Lt2 of each transformer to the positive output terminal P when forward biased, and shuts off the current when reverse biased Do.
  • the diodes D1, D2 and D3 preferably have small forward voltage drop and operate at high speed.
  • fourth, fifth and sixth diodes D4, D5 and D6, which are an example of a rectifying element, are connected between the other end of the secondary coils Lr2, Ls2 and Lt2 of each transformer and the negative output end N, respectively. It is done.
  • the cathodes of the diodes D4, D5, D6 are connected to the other ends of the secondary coils Lr2, Ls2, Lt2, respectively, and the anodes are connected to the negative output terminal N.
  • Each of the diodes D4, D5, D6 conducts the current flowing from the negative electrode output end N to the other end of the secondary coil Lr2, Ls2, Lt2 of each transformer when forward biased, and blocks the current when reverse biased.
  • a control unit that generates a control signal Vg is included.
  • the magnitudes of the input voltage and the DC output voltage are detected, the duty ratio of the control signal Vg is determined based on the detected input voltage and output voltage, and the control signal Vg is generated based thereon. It is preferable to use PWMIC as a main part of the control unit.
  • the PWMIC controls, for example, a pulse-like control having a constant duty ratio by inputting a DC signal of a constant voltage corresponding to one determined duty ratio and a carrier triangular wave signal having a constant frequency to the comparator.
  • the signal Vg is output.
  • such a control signal Vg is referred to as a "constant duty ratio" control signal.
  • FIG. 2A shows voltage waveforms of R phase, S phase, and T phase of the input three-phase alternating current.
  • the phase having the highest potential and the phase having the lowest potential are sequentially switched at every phase of 120 °.
  • the frequency of the three-phase alternating current is, for example, about several Hz to 100 Hz in the case of an alternator for wind power generation.
  • the switching frequency that is, the frequency of the control signal Vg in FIG. 1 is several kHz to several hundreds kHz, which is sufficiently higher than the frequency of the three-phase alternating current.
  • T mode a period in which the T phase is at the lowest potential
  • R mode the period in which the R phase is at the lowest potential
  • S mode the period in which the S phase is at the lowest potential
  • the R phase has the highest potential in the first half of the period
  • the S phase has the highest potential in the second half.
  • an input current flows due to the voltage between the positive potential phase and the negative potential phase, and no current flows in the off period.
  • an inter-phase voltage between the R phase and the T phase is referred to as an “RT inter-phase voltage” or the like and denoted as “vrt”.
  • the input current flowing by the RT inter-phase voltage vrt is represented as "irt”.
  • FIG. 2B shows, as an example, the waveform of the PWM control signal at point A on the time axis t in FIG. 2A, the voltage between rt phases vrt, and between the first input end R and the third input end T.
  • the on current irt flowing through the is schematically shown. Since the switching frequency is sufficiently high compared to the frequency of the three-phase alternating current, the RT interphase voltage vrt in one on period can be regarded as a pulse-like constant voltage.
  • the value of the start point of the current irt in the on period is determined by the instantaneous value of the RT inter-phase voltage vrt at the start point of the on period. Since the instantaneous value of the RT inter-phase voltage vrt is scattered on the locus of the sine wave, the current irt flowing through the primary coil during the on period also draws the locus of the sine wave. This means that the input current is a sine wave in phase with the input voltage. Thereby, the power factor improvement on the primary side is realized.
  • a current path including an inductance to which a three-phase AC interphase voltage is applied is turned on / off by using a PWM control signal having a constant frequency and a duty ratio, whereby a sine whose phase matches the input voltage The input current of the wave can be obtained.
  • FIG. 3 schematically shows a current flow (dotted line with an arrow) in the on period in T mode in the circuit configuration shown in FIG. ing.
  • An input current irt flows in the following path in the primary coil of the transformer Tr due to the RT phase voltage vrt.
  • ⁇ Input current irt first input end R ⁇ transformer Tr primary coil ⁇ FET Qr ⁇ FET Qt ⁇ transformer Tt primary coil ⁇ third input end T
  • the input current ist flows through the primary coil of the transformer Ts in the following path due to the ST phase voltage vst.
  • the current returning to the input side such as the current flowing from the primary coil of the transformer Tt to the third input terminal T, is hereinafter referred to as “reflux”.
  • the other ends (in this example, the winding ends) of the secondary coils of the transformer Tr, Ts and Tt are respectively a point, b and c points, and the secondary coil of the transformer Tr, Ts and Tt Let one end (in this example, the winding start end) be point d, point e, and point f.
  • the positive electrode output end P is a point h
  • the negative electrode output end N is a point g.
  • the point h is also one end of the smoothing capacitor C4.
  • the point g is also a common end of the sub capacitors C1, C2, C3 and the smoothing capacitor C4, and is a secondary side reference potential end.
  • FIG. 4 is a diagram schematically showing the potential relationship between the point a to h on the transformer secondary side in the on period. The operation of the transformer secondary side in the on period will be described with reference also to FIG.
  • the sub-capacitors C1, C2, C3 and the smoothing capacitor C4 are charged with the voltages Vc1, Vc2, Vc3, VC4 at both ends respectively.
  • a potential relationship diagram of the on period shown in FIG. 4 is referred to.
  • the secondary coil a point of the transformer Tr is at the same potential as the secondary side reference potential end point g because the diode D4 conducts.
  • the electromotive force Vr of the transformer Tr exceeds the voltage VC1 across the sub capacitor C1
  • the current iron of the on period flows in the following path in the direction of charging the sub capacitor C1.
  • the secondary coil b of the transformer Ts has the same potential as the point g on the secondary side reference potential end because the diode D5 conducts.
  • Vs of the transformer Ts exceeds the voltage VC2 across the sub capacitor C2
  • the current ison of the on period flows in the following path in the direction of charging the sub capacitor C2.
  • an electromotive force Vt is generated in the secondary coil when reflux flows in the primary coil.
  • the electromotive force Vt has a low potential at the point f side and a high potential at the point c side, and is in the opposite direction to the transformer Tr and Ts. Since the diode D6 is reverse biased with respect to the electromotive force Vt, no current flows.
  • the current iton is supplied to the load. Therefore, the current iton corresponds to the forward current in the forward system.
  • the supply current to the load is also merged with the discharge current from the smoothing capacitor C4. Since the sub capacitor C3 is discharged by the current iton, the potential at the point f decreases by that amount, and the voltage VC3 across the sub capacitor C3 decreases.
  • the electromotive force Vt of the transformer Tt is determined by the magnitude of the reflux of the primary coil.
  • the potential at the point c does not exceed the potential at the point h (see the potential at the point c '). In this case, the current iton does not flow.
  • FIG. 5 schematically shows the current flow (dotted line with arrow) in the off period in T mode in the circuit configuration of FIG. is there.
  • FIG. 6 is a diagram schematically showing the potential relationship between the point a to h on the transformer secondary side in the off period. The operation on the secondary side of the off period will be described with reference also to FIG.
  • the back electromotive force Vr generated in the secondary coil of the transformer Tr is directed to a low potential on the point d side and a high potential on the a point side. Since the diode D4 is reverse biased with respect to the back electromotive force Vr, no current flows.
  • a potential relationship diagram of the off period shown in FIG. 6 is referred to.
  • the back electromotive force Vr causes the potential at the secondary coil a of the transformer Tr to rise with respect to the potential at the point d.
  • the diode D1 becomes forward biased and the current iroff flows in the following path.
  • ⁇ Current iroff transformer Tr secondary coil point a ⁇ diode D 1 ⁇ point h ⁇ load (or smoothing capacitor C 4) ⁇ point g ⁇ sub capacitor C 1 ⁇ transformer Tr secondary coil point d
  • the back electromotive force Vs generated in the secondary coil of the transformer Ts is directed to a low potential on the point e side and a high potential on the point b side. Since the diode D5 is reverse biased with respect to the back electromotive force Vs, no current flows.
  • a potential relationship diagram of the off period shown in FIG. 6 is referred to.
  • the diode D2 is forward biased
  • the current isoff flows in the following path.
  • ⁇ Current isoff transformer Ts secondary coil point b ⁇ diode D2 ⁇ point h ⁇ load (or smoothing capacitor C4) ⁇ point g ⁇ sub capacitor C2 ⁇ transformer Ts secondary coil point
  • the currents iroff and isoff in the off period flow in the direction of discharging the sub capacitors C1 and C2, respectively.
  • the currents iroff and isoff in the off period correspond to the flyback current in the flyback system.
  • the magnetic energy stored in the transformer is released, but in the case of this circuit, the energy stored in the sub capacitors C1 and C2 is released.
  • the potential at the point a when iroff flows is the sum of the voltage VC1 across the sub capacitor C1 and the back electromotive force Vr to the potential at the point g.
  • the potential at point b when isoff flows is the sum of the potential at point g, the voltage VC2 across the sub capacitor C2 and the back electromotive force Vs.
  • the sub capacitors C1 and C2 are discharged by the currents iroff and isoff respectively, so the potential at the point d and the potential at the point e decrease by that amount, and the voltages VC1 and VC2 decrease.
  • the back electromotive force generated in the secondary coil of the transformer Tr and Ts in the off period is suppressed by the voltages VC1 and VC2 charged in the sub capacitors C1 and C2 in the on period, so there is no sub capacitor C1 or C2 Smaller than the back electromotive force of As a result, the back electromotive force generated on the primary side of the transformer Tr, Ts also decreases, and the withstand voltage required for the FET Qr, FET Qs on the primary side is reduced.
  • the back electromotive force Vt generated in the secondary coil of the transformer Tt is in the direction of high potential at the point f side and low potential at the point c side, and is opposite to the transformer Tr and Ts. Since the diode D3 is reverse biased with respect to the back electromotive force Vt, no current flows.
  • the potential at point f rises relative to the potential at point c due to the back electromotive force Vt and the potential at point f exceeds the voltage VC3 across the sub capacitor C3, the current itoff flows in the following path to charge the sub capacitor C3.
  • Current itoff transformer Tt secondary coil f point ⁇ sub capacitor C3 ⁇ diode D6 ⁇ transformer Tt secondary coil c point
  • the operation of the off period of this circuit is summarized as follows.
  • the back electromotive force generated in the secondary coil in the off period is added to the voltage of the sub capacitor.
  • the added voltage exceeds the voltage of the smoothing capacitor, current flows in the load.
  • the back electromotive force generated in the secondary coil in the off period exceeds the voltage of the sub capacitor, a current flows in the direction of charging the sub capacitor.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)

Abstract

L'invention concerne une alimentation électrique à découpage isolée à laquelle un courant alternatif triphasé est appliqué, ladite alimentation électrique à découpage isolée améliorant efficacement un facteur d'électricité au moyen d'une configuration simple et effectuant une conversion de courant. L'alimentation électrique à découpage isolée comprend : des extrémités d'entrée R, S, T ; des extrémités de sortie d'électrodes positive et négative P, N ; trois transformateurs Tr, Ts, Tt dont des bobines primaires respectives sont connectées aux extrémités d'entrée respectives ; trois éléments de commutation Qr, Qs, Qt destinés à amener les trajets de courant respectifs entre une autre extrémité des bobines primaires respectives des trois transformateurs et une extrémité de niveau de tension de référence côté entrée dans un état conducteur ou dans un état de coupure ; des premier à troisième sous-condensateurs C1, C2, C3 connectés entre une extrémité des bobines secondaires respectives des trois transformateurs et l'extrémité de sortie d'électrode négative ; des premier à troisième éléments de redressement D1, D2, D3 connectés respectivement entre les autres extrémités des bobines secondaires respectives des trois transformateurs et l'extrémité de sortie d'électrode positive ; des quatrième à sixième éléments de redressement D4, D5, D6 connectés respectivement entre les autres extrémités des bobines secondaires respectives des trois transformateurs et l'extrémité de sortie d'électrode négative ; et un condensateur de filtrage connecté entre l'extrémité de sortie d'électrode positive et l'extrémité de sortie d'électrode négative.
PCT/JP2018/018504 2017-06-23 2018-05-14 Alimentation électrique à découpage isolée en courant alternatif triphasé WO2018235455A1 (fr)

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JP2017123156A JP6800098B2 (ja) 2017-06-23 2017-06-23 三相交流用絶縁型スイッチング電源

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JP6817894B2 (ja) * 2017-05-19 2021-01-20 Ntn株式会社 三相交流用絶縁型スイッチング電源

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JPH07250471A (ja) * 1994-03-09 1995-09-26 Isao Takahashi 三相正弦波入力スイッチング電源回路
JP2002058248A (ja) * 2000-08-11 2002-02-22 Interunits Corp 三相整流装置
JP2002199731A (ja) * 2000-12-25 2002-07-12 Sanken Electric Co Ltd ３相交流−直流変換装置
JP2005033911A (ja) * 2003-07-11 2005-02-03 Sanken Electric Co Ltd ３相交流−直流電力変換装置
JP2009261163A (ja) * 2008-04-18 2009-11-05 Cosel Co Ltd 三相力率改善回路

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JP3261010B2 (ja) 1995-05-31 2002-02-25 オークマ株式会社 電力変換装置
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JP4466089B2 (ja) 2004-01-29 2010-05-26 サンケン電気株式会社 力率改善回路
KR20050105945A (ko) 2005-09-30 2005-11-08 이경욱 탄소 면상발열체를 이용한 농수산물 건조기
KR101803049B1 (ko) 2010-09-01 2017-11-29 구글 엘엘씨 사용자 목록 생성 및 식별
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Publication number Priority date Publication date Assignee Title
JPH07250471A (ja) * 1994-03-09 1995-09-26 Isao Takahashi 三相正弦波入力スイッチング電源回路
JP2002058248A (ja) * 2000-08-11 2002-02-22 Interunits Corp 三相整流装置
JP2002199731A (ja) * 2000-12-25 2002-07-12 Sanken Electric Co Ltd ３相交流−直流変換装置
JP2005033911A (ja) * 2003-07-11 2005-02-03 Sanken Electric Co Ltd ３相交流−直流電力変換装置
JP2009261163A (ja) * 2008-04-18 2009-11-05 Cosel Co Ltd 三相力率改善回路

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JP6800098B2 (ja) 2020-12-16

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