WO2018146877A1 - Dispositif d'alimentation électrique et procédé de commande de dispositif d'alimentation électrique - Google Patents

Dispositif d'alimentation électrique et procédé de commande de dispositif d'alimentation électrique Download PDF

Info

Publication number
WO2018146877A1
WO2018146877A1 PCT/JP2017/040246 JP2017040246W WO2018146877A1 WO 2018146877 A1 WO2018146877 A1 WO 2018146877A1 JP 2017040246 W JP2017040246 W JP 2017040246W WO 2018146877 A1 WO2018146877 A1 WO 2018146877A1
Authority
WO
WIPO (PCT)
Prior art keywords
switching element
transformer
power supply
mode
current
Prior art date
Application number
PCT/JP2017/040246
Other languages
English (en)
Japanese (ja)
Inventor
圭司 田代
Original Assignee
住友電気工業株式会社
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 住友電気工業株式会社 filed Critical 住友電気工業株式会社
Priority to JP2018566756A priority Critical patent/JP6930549B2/ja
Publication of WO2018146877A1 publication Critical patent/WO2018146877A1/fr

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac

Definitions

  • the present invention relates to a power supply device and a control method for the power supply device.
  • This application claims priority based on Japanese Patent Application No. 2017-024055 filed on Feb. 13, 2017, and incorporates all the description content described in the above Japanese application.
  • the DC / DC converter includes an insulation type DC / DC converter (active clamp type DC / DC converter) including an active clamp circuit.
  • a series circuit of a primary winding of a transformer and a main switching element is connected to a DC power source, and an active clamp circuit including a capacitor and an auxiliary switching element is provided at both ends of the primary winding. It is connected.
  • a rectifying element in the forward direction and a rectifying element in the reverse direction are connected to the secondary winding.
  • the power supply apparatus includes a transformer, a first switching element connected in series to a primary winding of the transformer, a first capacitor connected in parallel to the first switching element, and the primary winding.
  • a power supply device comprising: a second rectifier element connected in parallel to the rectifier element; and a control unit that controls on / off of the first switching element and the second switching element.
  • the first switching element is turned on, the second switching element is turned off and the transformer is operated in a first mode, and after the first mode, the first switching element is turned on.
  • the transformer and the first capacitor are operated in a third mode to resonate, and the current flowing through the second rectifier element due to the resonance in the third mode is less than or equal to a predetermined threshold, and the control unit When the current flowing through the second rectifying element becomes equal to or less than the threshold value, the first switching element is turned on to shift to the first mode.
  • a control method for a power supply apparatus includes a transformer, a first switching element connected in series to a primary winding of the transformer, a first capacitor connected in parallel to the first switching element, A series circuit of a second switching element and a second capacitor connected in parallel to the primary winding, a first rectifier element connected in series to the secondary winding of the transformer, and the secondary winding And a second rectifying element connected in parallel to the first rectifying element, and a control unit for controlling on / off of the first switching element and the second switching element.
  • the control unit operates in a first mode in which the first switching element is turned on, the second switching element is turned off to excite the transformer, and after the first mode, the first switching element is operated.
  • the switching element is turned off, the second switching element is turned on and the transformer is operated in a second mode to reset the excitation.
  • the first switching element and the second switching element are simultaneously operated.
  • the transformer and the first capacitor are turned off to operate in a third mode, and the current flowing through the second rectifier element due to the resonance in the third mode is set to be equal to or lower than a predetermined threshold value.
  • the control unit turns on the first switching element and shifts to the first mode when the current flowing through the second rectifying element becomes equal to or less than the threshold value.
  • an object of the present disclosure is to provide a power supply apparatus and a control method for the power supply apparatus that can suppress the generation of steep counter electromotive force.
  • the power supply apparatus includes a transformer, a first switching element connected in series to a primary winding of the transformer, a first capacitor connected in parallel to the first switching element, and the primary winding.
  • a power supply device comprising: a second rectifier element connected in parallel to the rectifier element; and a control unit that controls on / off of the first switching element and the second switching element.
  • the first switching element is turned on, the second switching element is turned off and the transformer is operated in a first mode, and after the first mode, the first switching element is turned off. And operating in a second mode in which the second switching element is turned on to reset the excitation of the transformer, and after the second mode, the first switching element and the second switching element are simultaneously turned off and the second switching element is turned off.
  • the transformer and the first capacitor are operated in a third mode to resonate, and the current flowing through the second rectifier element due to the resonance in the third mode is less than or equal to a predetermined threshold, and the control unit When the current flowing through the second rectifying element becomes equal to or less than the threshold value, the first switching element is turned on to shift to the first mode.
  • a control method for a power supply apparatus includes a transformer, a first switching element connected in series to a primary winding of the transformer, a first capacitor connected in parallel to the first switching element, A series circuit of a second switching element and a second capacitor connected in parallel to the primary winding, a first rectifier element connected in series to the secondary winding of the transformer, and the secondary winding And a second rectifying element connected in parallel to the first rectifying element, and a control unit for controlling on / off of the first switching element and the second switching element.
  • the control unit operates in a first mode in which the first switching element is turned on, the second switching element is turned off to excite the transformer, and after the first mode, the first switching element is operated.
  • the switching element is turned off, the second switching element is turned on and the transformer is operated in a second mode to reset the excitation.
  • the first switching element and the second switching element are simultaneously operated.
  • the transformer and the first capacitor are turned off to operate in a third mode, and the current flowing through the second rectifier element due to the resonance in the third mode is set to be equal to or lower than a predetermined threshold value.
  • the control unit turns on the first switching element and shifts to the first mode when the current flowing through the second rectifying element becomes equal to or less than the threshold value.
  • the controller operates in the first mode in which the first switching element is turned on and the second switching element is turned off to excite the transformer.
  • a power supply voltage on the input side is applied to the primary winding of the transformer, and the first rectifying element is turned on to output a predetermined voltage to the output side.
  • the transformer excitation current increases.
  • the control unit operates in the second mode in which the first switching element is turned off and the second switching element is turned on to reset the excitation of the transformer.
  • the transformer voltage becomes negative
  • the first rectifying element is reverse-biased
  • the load current flows through the second rectifying element.
  • the series circuit of the second switching element and the second capacitor constitutes a so-called active clamp circuit.
  • the control unit operates in the third mode in which the first switching element and the second switching element are simultaneously turned off after the second mode to resonate the transformer and the first capacitor. Due to the resonance, the current flowing through the second rectifying element also resonates and begins to decrease once. On the other hand, when the voltage of the transformer becomes positive due to resonance, the first rectifier element becomes forward biased, current flows through the first rectifier element, and the current of the first rectifier element starts to increase once due to resonance.
  • the current flowing through the second rectifying element due to resonance in the third mode is set to be equal to or less than a predetermined threshold value.
  • the predetermined threshold may be, for example, 0A or a small value near 0A. That is, when the current flowing through the second rectifying element once starts to decrease due to resonance, the current decreases to 0 A or near 0 A. Specifically, the excitation inductance of the transformer may be reduced so that the resonance current is about 0A.
  • the control unit turns on the first switching element and shifts to the first mode when the current flowing through the second rectifying element becomes equal to or less than the threshold value.
  • the first switching element is turned on, the potential of the first rectifying element is lowered by a voltage corresponding to the voltage of the first capacitor, and a reverse voltage is applied to the second rectifying element (becomes a reverse bias).
  • a reverse voltage is applied to the second rectifier element, the current flowing through the second rectifier element is equal to or lower than the threshold value, so that the generation of reverse recovery current can be suppressed and the generation of steep back electromotive force can be prevented. Can be suppressed.
  • the power supply device of the present disclosure satisfies the formula 2 ⁇ Im ⁇ n ⁇ Imax.
  • the winding ratio between the primary winding and the secondary winding of the transformer is n: 1
  • the maximum load current is Imax
  • the exciting current of the transformer when transitioning to the third mode is Im.
  • the second rectifying element includes a load current (Il) flowing through the load, a transformer exciting current (Im), a transformer (transformer leakage inductance), and a resonance current (Ir) due to resonance of the first capacitor.
  • the load current Il becomes a constant value by, for example, relatively increasing the inductance of the output side choke coil or the like.
  • the excitation current Im does not change during the dead time (a period in which both the first switching element and the second switching element are off) because the voltage applied to the excitation inductance is almost zero.
  • the resonance current Ir becomes the same value as the excitation current Im at the resonance start timing (however, the direction of the current is opposite) and is canceled out with the excitation current Im.
  • the second rectifier element has the same magnitude as the load current. Current flows.
  • n the turns ratio of the primary winding and the secondary winding of the transformer
  • Ir the turns ratio of the primary winding and the secondary winding of the transformer
  • the current flowing through the second rectifying element based on the excitation inductance of the transformer is set to be equal to or less than the threshold value.
  • the current flowing through the second rectifying element is set to be equal to or less than the threshold value.
  • the characteristic that the amplitude of the resonance current increases when the excitation inductance of the transformer is reduced is utilized. That is, when the excitation inductance of the transformer is reduced, the amplitude can be increased so that when the current flowing through the second rectifying element starts to decrease due to resonance, the current decreases to a threshold value or less. Thereby, it is possible to suppress the generation of steep back electromotive force by adjusting the excitation inductance of the transformer without adding special parts.
  • the second rectifying element includes a synchronous rectifying element.
  • the second rectifying element includes a synchronous rectifying element.
  • a synchronous rectifying element For example, an FET can be used as the synchronous rectifier.
  • the synchronous rectification is a rectification method in which the FET is turned on / off at a necessary timing to perform a rectification operation. Since synchronous rectifying elements such as FETs have a smaller forward voltage than diodes, loss can be reduced. However, the reverse recovery current tends to increase due to the body diode of the FET.
  • FIG. 1 is an explanatory diagram illustrating a first example of a circuit configuration of the power supply device 100 according to the present embodiment.
  • the power supply apparatus 100 includes terminals A and B on the input side and terminals C and D on the output side.
  • a DC power supply (not shown) is connected to the terminals A and B on the input side, and the output side A load is connected to the terminals C and D.
  • the power supply device 100 is, for example, a step-down converter.
  • the power supply apparatus 100 includes a transformer 30, a MOSFET (Metal / Oxide / Semiconductor / Field / Effect / Transistor, hereinafter referred to as "FET") 11 as a first switching element, a capacitor 21 as a first capacitor, and a second switching element.
  • FET 12 capacitor 22 as the second capacitor
  • diode 41 as the first rectifier
  • diode 42 as the second rectifier
  • capacitor 24 inductor 61 (choke coil on the output side)
  • FET 11 and FET 12 are turned on The control part 50 etc. which control / off are provided.
  • the FET 11 and FET 12 each have a body diode.
  • the terminal A is connected to one end of the primary winding 31 of the transformer 30.
  • the other end of the primary winding 31 is connected to the drain of the FET 11.
  • the source of the FET 11 is connected to the terminal B.
  • a capacitor 21 (resonance capacitor) is connected between the drain and source of the FET 11.
  • a series circuit of the FET 12 and the capacitor 22 is connected to both ends of the primary winding 31.
  • a series circuit of the FET 12 and the capacitor 22 constitutes an active clamp circuit.
  • one end of the capacitor 22 is connected to one end of the primary winding 31, and the drain of the FET 12 is connected to the other end of the capacitor 22.
  • the source of the FET 12 is connected to the other end of the primary winding 31.
  • the cathode of the diode 41 is connected to one end of the secondary winding 32 of the transformer 30, and the anode of the diode 41 is connected to the terminal D (ground level).
  • the other end of the secondary winding 32 is connected to the cathode of the diode 42 and one end of the inductor 61.
  • the anode of the diode 42 is connected to the anode of the diode 41.
  • the anodes of the diode 41 and the diode 42 are connected to each other.
  • the present invention is not limited to this, and the cathodes of the diode 41 and the diode 42 are connected to each other. It may be configured.
  • the other end of the inductor 61 is connected to the terminal C.
  • a capacitor 24 is connected between the terminals C and D.
  • the control unit 50 outputs a gate voltage to the gates of the FETs 11 and 12.
  • FIG. 2 is an explanatory diagram illustrating an example of the operation state D1 of the power supply device 100 according to the present embodiment.
  • the control unit 50 turns on the FET 11 and turns off the FET 12.
  • the operation state D1 corresponds to the first mode.
  • the exciting current of the transformer 30 increases and the transformer 30 is excited.
  • the power supply voltage on the input side is applied to the primary winding of the transformer 30, and the voltage of the primary winding becomes positive.
  • the voltage of the secondary winding also becomes positive, the diode 41 becomes conductive, and a predetermined voltage and current are output to the output side.
  • the exciting current of the transformer 30 increases.
  • symbol Lm represents the exciting inductance of the transformer 30, and Ls represents the leakage inductance.
  • a positive voltage is defined when the upper end potential is higher than the lower ends of the primary and secondary windings.
  • FIG. 3 is an explanatory diagram showing an example of the operation state D2 of the power supply apparatus 100 of the present embodiment.
  • the control unit 50 turns off the FET 11, and the FET 12 remains off.
  • the capacitor Cs (21) is charged.
  • the capacitor 21 is also referred to as a capacitor Cs.
  • the voltage of the transformer 30 primary winding and secondary winding
  • FIG. 4 is an explanatory diagram showing an example of the operation state D3 of the power supply device 100 according to the present embodiment.
  • the FET 11 and FET 12 remain off.
  • the diode 41 becomes reverse biased and becomes non-conductive.
  • the load current flowing in the diode 41 flows through the diode 42.
  • FIG. 5 is an explanatory diagram showing an example of the operation state D4 of the power supply device 100 according to the present embodiment.
  • the operating state D4 when the capacitor Cs is charged to a predetermined voltage, the body diode of the FET 12 becomes forward biased, and the excitation current that has flowed through the capacitor Cs flows through the body diode of the FET 12.
  • the control unit 50 turns on the FET 12.
  • the FET 12 When the FET 12 is turned on, the voltage of the capacitor 22 is applied to the transformer 30 in the reverse direction (negative voltage direction), the exciting current of the transformer 30 decreases, and the state of the transformer 30 is reset.
  • the FET 12 is turned on in the operation state D4, the second mode is supported.
  • FIG. 6 is an explanatory diagram showing an example of the operating state D5 of the power supply apparatus 100 according to the present embodiment.
  • the FET 12 is on and the FET 11 is off.
  • the operation state D5 corresponds to the second mode.
  • the exciting current of the transformer 30 is reversed (becomes negative, the current direction is reversed), the energy stored in the capacitor 22 is released, and the energy is stored in the leakage inductance Ls of the transformer 30.
  • FIG. 7 is an explanatory diagram showing an example of the operation state D6 of the power supply apparatus 100 according to the present embodiment.
  • the control unit 50 turns off the FET 12, and the FET 11 remains off.
  • An operation state D6 and an operation state D7 described later correspond to the third mode, and correspond to a dead time (pause period) in which the FET 11 and the FET 12 are simultaneously turned off before the operation state D1 (the FET 11 is turned on).
  • resonance occurs due to the transformer 30 (more specifically, the sum of the leakage inductance Ls and the excitation inductance Lm) and the resonance capacitor Cs.
  • the diode 41 becomes forward biased, a current flows through the diode 41, and the operation state D7 is entered.
  • FIG. 8 is an explanatory diagram showing an example of the operating state D7 of the power supply apparatus 100 of the present embodiment.
  • the FETs 11 and 12 remain off.
  • resonance occurs due to the transformer 30 (more specifically, the leakage inductance Ls) and the capacitor Cs.
  • the diode 42 includes a load current Il (shown by a solid line in the figure) flowing through the load, an excitation current Im (shown by a broken line in the figure) of the transformer 30, and a transformer 30 (leakage inductance Ls of the transformer 30). And a resonance current Ir (indicated by a one-dot chain line in the figure) due to resonance of the capacitor Cs flows.
  • the winding ratio of the transformer 30 is assumed to be 1: 1 for convenience, but the winding ratio of the transformer 30 is not limited to 1: 1.
  • the load current Il flows through the diode 42, the inductor 61 (also referred to as the output side choke coil), and the closed loop of the load.
  • the load current Il becomes a constant value by relatively increasing the inductance of the inductor 61.
  • the exciting current Im flows through the closed loop of the transformer 30 and the diodes 42 and 41. Since the voltage applied to the exciting inductance Lm is almost zero during the dead time (period in which the FET 11 and the FET 12 are simultaneously turned off), the exciting current Im does not change in the operating state D7, and the operating state D6 is The current value Im at the time of termination is maintained.
  • the resonance current Ir is a current due to resonance of the leakage inductance Ls of the transformer 30 and the capacitor Cs, and can be expressed by Expression (1).
  • t is time
  • the resonance current Ir excitation current Im.
  • the directions of the resonance current Ir and the excitation current Im are opposite. That is, at the start timing of the operation state D7, the resonance current Ir has the same value as the excitation current Im (however, the direction of the current is reversed) and is canceled out with the excitation current Im. The same current flows.
  • the resonance current Ir temporarily decreases. That is, the resonance current Ir decreases in a direction that cancels the load current Il, and the current flowing through the diode 42 decreases toward the threshold value as the resonance proceeds.
  • the current of the diode 41 increases as the resonance proceeds.
  • the resonance frequency f can be obtained by the equation 1 / ⁇ 2 ⁇ ⁇ ⁇ ⁇ (Ls ⁇ Cs) ⁇ .
  • the current flowing through the diode 42 due to resonance is equal to or less than a predetermined threshold value.
  • the predetermined threshold may be, for example, 0A or a small value near 0A. That is, when the current flowing through the diode 42 starts to decrease once due to resonance, the current decreases to 0 A or near 0 A. Specifically, the excitation inductance Lm of the transformer 30 may be reduced so that the resonance current is about 0A.
  • the control unit 50 turns on the FET 11. Thereby, the state shifts to an operation state D8 described later.
  • the winding ratio of the transformer 30 is described as 1: 1 for convenience.
  • the winding ratio of the transformer 30 is n: 1
  • the primary side and the secondary side of the transformer 30 are secondary.
  • the voltage may be 1 / n times and the current may be n times.
  • the expression (2) is satisfied with the excitation current Im as small as possible.
  • the condition for satisfying the expression (2) with the smallest exciting current Im can be expressed by the expression (4).
  • the inductor 61 output-side choke coil
  • the ripple current is zero. That's fine.
  • FIG. 9 is an explanatory diagram showing an example of the operating state D8 of the power supply apparatus 100 according to the present embodiment.
  • the operating state D8 when the FET 11 is turned on, the voltage of the transformer 30 decreases by a voltage corresponding to the voltage of the capacitor Cs. For this reason, when the cathode potential of the diode 41 that is forward-biased decreases, the anode potential of the diode 42 decreases, and a reverse voltage is applied to the diode 42 (becomes reverse bias).
  • the current flowing through the diode 42 is equal to or less than the threshold value, so that the generation of reverse recovery current can be suppressed and the generation of steep counter electromotive force can be suppressed.
  • the current flowing through the diode 42 is set to be equal to or less than the threshold value.
  • the characteristic that the amplitude of the resonance current is increased is used. That is, when the exciting inductance Lm of the transformer 30 is reduced, the amplitude can be increased so that when the current flowing through the diode 42 starts to decrease due to resonance, the current decreases below the threshold value.
  • the exciting inductance Lm of the transformer 30 without adding special parts, it is possible to suppress the generation of steep back electromotive force.
  • the value of the excitation inductance Lm may be calculated by calculation, or may be obtained by actual measurement or simulation.
  • the timing at which the current flowing through the diode 42 becomes equal to or lower than the threshold can be obtained based on the current value of the diode 42, the resonance frequency f, and the like.
  • FIG. 10 is an explanatory diagram showing an example of the waveform of each part in the operating state of the power supply apparatus 100 of the present embodiment.
  • the horizontal axis indicates time.
  • the waveforms in FIG. 10 indicate the gate voltage of the FET 12, the current of the diode 42, the current of the diode 42, the gate voltage of the FET 11, and the voltage of the diode 42 in order from the top.
  • the FET 12 is on and the FET 11 is off.
  • the diode 42 is forward biased, and the voltage of the diode 42 is a forward voltage.
  • a load current flows through the diode 42.
  • the diode 41 is reverse-biased and no current flows.
  • the operation state D6 In the operation state D5, when the FET 12 is turned from on to off, the operation state D6 is entered. In the operation state D6, resonance occurs due to the transformer 30 (more specifically, the sum of the leakage inductance Ls and the excitation inductance Lm) and the resonance capacitor Cs.
  • the operation state D7 is set.
  • the current flowing through the diode 42 also resonates and begins to decrease once.
  • the diode 41 becomes forward biased, a current flows through the diode 41, and the current of the diode 41 starts to increase once due to resonance.
  • the FET 11 In the operation state D7, when the current flowing through the diode 42 is equal to or less than the threshold value, the FET 11 is turned on, and the operation state D8 is entered. Since the FET 11 is turned on when the current flowing through the diode 42 becomes less than the threshold value, the forward current flowing when the diode 42 is reverse-biased by turning on the FET 11 is extremely small, so that reverse recovery is achieved. It is possible to suppress the generation of current (current in the negative direction when shifting from the operating state D7 to D8 in FIG. 10). As a result, the electromotive force generated in the diode 42 (the cathode potential with respect to the anode of the diode 42) can be suppressed. As shown in FIG. 10, it can be seen that the fluctuation of the voltage of the diode 42 is relatively small when shifting from the operating state D7 to D8.
  • FIG. 11 is an explanatory diagram showing an example of the waveform of each part in the operating state of the power supply device as a comparative example.
  • the comparative example shows a case where the current flowing through the diode 42 due to resonance is not set to be equal to or less than a predetermined threshold value.
  • the operation state D5 is the same as that in FIG.
  • the operation state D6 In the operation state D5, when the FET 12 is turned from on to off, the operation state D6 is entered. In the operation state D6, resonance occurs due to the transformer 30 (more specifically, the sum of the leakage inductance Ls and the excitation inductance Lm) and the resonance capacitor Cs.
  • the operation state D7 is set.
  • the current flowing through the diode 42 gradually decreases while resonating.
  • the current flowing through the diode 41 gradually increases while resonating.
  • the amplitude of the current flowing through the diode 42 due to resonance is increased so that the current becomes a predetermined threshold value or less, and this current becomes the threshold value or less. Since the FET 11 is turned on at the timing, even if the diode 42 is reverse biased by turning on the FET 11, the reverse recovery current can be reduced, and as a result, the generation of the surge voltage can be suppressed.
  • FIG. 12 is a flowchart showing an example of the processing procedure of the control method of the power supply apparatus 100 of the present embodiment.
  • the control unit 50 turns on the FET 11, turns off the FET 12 (S 11), excites the transformer 30 (S 12), and sets the power supply apparatus 100 to the operation state D 1.
  • the control unit 50 turns off the FET 11 (S13), shifts the power supply device 100 from the operating state D1 to the operating state D2, and charges the capacitor Cs (21). Thereafter, the power supply device 100 is set to the operation states D3 and D4.
  • the control unit 50 turns on the FET 12 at the timing when the body diode of the FET 12 becomes forward biased (S14), and shifts the power supply apparatus 100 to the operation state D5.
  • the control unit 50 releases the energy stored in the capacitor 22 of the active clamp circuit and stores the energy in the leakage inductance Ls (S15).
  • the control unit 50 turns off the FET 12 (S16) and shifts the power supply device 100 to the operation state D6.
  • the control unit 50 generates resonance by the leakage inductance Ls and the resonance capacitor Cs (S17). Thereafter, the power supply device 100 is shifted to the operation state D7.
  • the current flowing through the diode 42 decreases toward 0 A due to resonance.
  • the control unit 50 determines whether or not the current flowing through the diode 42 is equal to or less than a threshold value (S18). Note that the timing at which the current flowing through the diode 42 becomes equal to or less than the threshold value is obtained in advance, and it can also be determined based on whether or not the timing is reached.
  • control unit 50 continues the process of step S18. If the current flowing through the diode 42 is less than or equal to the threshold (YES in S18), the FET 11 is turned on ( S19), the power supply device 100 is shifted to the operation state D8.
  • the control unit 50 determines whether or not to end the process (S20). When it is determined that the process is not ended (NO in S20), the process after step S12 is continued and it is determined that the process is ended (S20). YES), the process is terminated.
  • control unit 50 is configured by, for example, a CPU (processor), a RAM (memory), and the like, and a computer program that defines the procedure of each process as shown in FIG. Is loaded into a RAM (memory), and a computer program is executed by a CPU (processor), whereby a control method of the power supply device 50 can be realized on the computer.
  • a CPU processor
  • RAM memory
  • CPU processor
  • FIG. 13 is an explanatory diagram showing a second example of the circuit configuration of the power supply device 100 of the present embodiment.
  • the difference from the first example shown in FIG. 1 is that FETs 13 and 14 as synchronous rectifier elements are provided instead of the diodes 41 and 42. That is, in the second example, the drain of the FET 13 is connected to one end of the secondary winding 32 of the transformer 30, and the source of the FET 13 is connected to the terminal D (ground level). The other end of the secondary winding 32 is connected to the drain of the FET 14. The source of the FET 14 is connected to the source of the FET 13.
  • the control unit 50 outputs a gate voltage to the gates of the FET 13 and FET 14 and controls on / off of the FET 13 and FET 14.
  • the controller 50 turns on and off the FET 13 and the FET 14 at a necessary timing to perform a synchronous rectification operation.
  • the current flowing through the FET 14 is equal to or lower than the threshold value. It can be reduced and generation of steep back electromotive force can be suppressed.
  • FIG. 14 is an explanatory diagram showing a third example of the circuit configuration of the power supply device 100 of the present embodiment.
  • a current detection unit 70 that detects the load current of the power supply device 100
  • the control unit 50 includes a dead time adjustment unit 51, a calculation unit 52, and the like.
  • the control unit 50 (dead time adjustment unit 51) adjusts the dead time indicating the time from the time when the FET 12 is turned off to the time when the FET 11 is turned on according to the load current detected by the current detection 70.
  • the third example can also be applied to the second example shown in FIG. Details will be described below.
  • FIG. 15 is a time chart showing an example of the switching state of the FETs 11 and 12 of the power supply apparatus 100 of the present embodiment.
  • the time chart illustrated in FIG. 15 is apparent from the description of the first example and the second example described above, but will be described again for convenience.
  • the FET 12 on time is T12
  • the FET 11 on time is T11
  • the dead time from the FET 12 off time to the FET 11 on time is Td1
  • the dead time from the FET 11 off time to the FET 12 on time is dead.
  • Td2 T.
  • T is the switching period of the FET 12. Note that the period T is constant.
  • the on-time T11 of the FET 11 can also be made constant when the rated input voltage of the power supply device 100 does not change.
  • the noticeable dead time is the period of the operating states D6 and D7, which is Td1.
  • FIG. 16 is an explanatory diagram showing an example of the optimum value of dead time due to the load current of the power supply device 100 of the present embodiment.
  • Td1 operation states D6 and D7
  • the current flowing through the diode 42 decreases and increases and decreases repeatedly.
  • the load current is relatively large
  • the time until the current flowing through the diode 42 reaches about 0 A is relatively long.
  • the load current is relatively small
  • the time until the current flowing through the diode 42 reaches about 0 A is relatively short. That is, it can be seen that the optimum value of the dead time Td1 (that is, the time from when the FET 12 is turned off until the current flowing through the diode 42 first reaches around 0 A) changes.
  • FIG. 17 is an explanatory diagram showing a correspondence relationship between the dead time Td1 and the load current of the power supply device 100 according to the present embodiment.
  • the horizontal axis represents the load current (corresponding to the load current detected by the current detection unit 70), and the vertical axis represents the dead time Td1.
  • the dead time Td1 can be set smaller as the load current decreases, and conversely, the dead time Td1 can be set larger as the load current increases.
  • the dead time Td1 is made smaller than the lower limit value, the FET 12 and the FET 11 are simultaneously turned on due to the operation delay of the gate drive circuit, etc., and there is a possibility that an overcurrent flows. .
  • the FET 12 may be turned off at a timing at which the resonance current flowing through the diode 42 does not become around 0 A, and the dead time Td1 is preferably set to the upper limit value or less.
  • the information indicating the correspondence between the dead time Td1 and the load current as shown in FIG. 17 may be stored in a non-volatile memory (not shown) provided inside or outside the control unit 50, or A chart as shown in FIG. 17 may be realized by an arithmetic circuit, and the dead time Td1 may be calculated from the load current.
  • the current detector 70 detects the load current while the FET 11 is on.
  • the current detection unit 70 can detect a current having a value obtained by dividing the load current by the turn ratio of the transformer 30. As a result, the load current is detected from the ON time point to the OFF time point in a certain switching cycle of the FET 12, so that the OFF time point can be determined within the switching cycle and the dead time Td1 can be adjusted.
  • the current detection unit 70 detects the load current a plurality of times while the FET 11 is turned on over a plurality of switching cycles of the FET 11, and the control unit 50 detects the load current detected a plurality of times by the current detection unit 70.
  • the dead time Td1 can be adjusted according to the statistical value.
  • the statistical value can be an average value, for example.
  • FIG. 18 is an explanatory diagram showing an example of a method for adjusting the dead time Td1 of the power supply apparatus 100 according to the present embodiment.
  • the dead time adjusting unit 51 (or the control unit 50) changes the OFF time of the FET 12 to adjust the dead time Td1.
  • the dead time Td1 can be adjusted while keeping T and T11 constant.
  • the dead time adjustment unit 51 increases the dead time Td1 when the load current is large, and shortens the dead time Td1 when the load current is small.
  • the calculation unit 52 calculates the ON time T12 of the FET 12 based on the load current detected by the current detection unit 70 and information indicating the correspondence relationship between the dead time Td1 and the load current illustrated in FIG.
  • the switching element is not limited to a MOSFET, but may be a device such as an IGBT (Insulated Gate Bipolar Transistor).
  • IGBT Insulated Gate Bipolar Transistor
  • the switching element is a MOSFET as in the present embodiment, there is an equivalently incorporated body diode between the drain and source.
  • a bipolar transistor is used as the switching element, a diode may be connected in antiparallel between the collector and emitter of the transistor.
  • the current detection unit 70 is provided between one end of the primary winding 31 of the transformer 30 and the input terminal A, and the current is detected when the FET 11 is on.
  • the present invention is not limited to this.
  • a current detector 70 may be provided between one end of the inductor 61 and the output terminal C so that the current is detected when the FET 12 is on.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

La présente invention concerne une unité de commande qui : active un premier mode, dans lequel un premier élément de commutation est mis en circuit et un deuxième élément de commutation est mis hors circuit, ce qui excite un transformateur ; active, après le premier mode, un deuxième mode dans lequel le premier élément de commutation est mis hors circuit et le deuxième élément de commutation est mis en circuit, ce qui réinitialise le transformateur ; et active, après le deuxième mode, un troisième mode dans lequel le premier élément de commutation et le deuxième élément de commutation sont tous deux mis hors circuit en même temps, ce qui met en résonance le transformateur et un premier condensateur. Le courant qui circule vers un deuxième élément de redressement au moyen de la résonance dans le troisième mode est réglé pour être inférieur ou égal à un seuil prédéterminé, et l'unité de commande met en circuit le premier élément de commutation lorsque le courant qui circule vers le deuxième élément de redressement est inférieur ou égal au seuil.
PCT/JP2017/040246 2017-02-13 2017-11-08 Dispositif d'alimentation électrique et procédé de commande de dispositif d'alimentation électrique WO2018146877A1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
JP2018566756A JP6930549B2 (ja) 2017-02-13 2017-11-08 電源装置及び電源装置の制御方法

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
JP2017024055 2017-02-13
JP2017-024055 2017-02-13

Publications (1)

Publication Number Publication Date
WO2018146877A1 true WO2018146877A1 (fr) 2018-08-16

Family

ID=63108105

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/JP2017/040246 WO2018146877A1 (fr) 2017-02-13 2017-11-08 Dispositif d'alimentation électrique et procédé de commande de dispositif d'alimentation électrique

Country Status (2)

Country Link
JP (1) JP6930549B2 (fr)
WO (1) WO2018146877A1 (fr)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2023042393A1 (fr) * 2021-09-17 2023-03-23 Tdk株式会社 Dispositif de commande de commutation, dispositif d'alimentation électrique à commutation et système d'alimentation électrique

Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2006238649A (ja) * 2005-02-25 2006-09-07 Sanken Electric Co Ltd 直流変換装置
JP5032525B2 (ja) * 2009-03-12 2012-09-26 コーセル株式会社 スイッチング電源装置

Patent Citations (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2006238649A (ja) * 2005-02-25 2006-09-07 Sanken Electric Co Ltd 直流変換装置
JP5032525B2 (ja) * 2009-03-12 2012-09-26 コーセル株式会社 スイッチング電源装置

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2023042393A1 (fr) * 2021-09-17 2023-03-23 Tdk株式会社 Dispositif de commande de commutation, dispositif d'alimentation électrique à commutation et système d'alimentation électrique

Also Published As

Publication number Publication date
JP6930549B2 (ja) 2021-09-01
JPWO2018146877A1 (ja) 2019-11-21

Similar Documents

Publication Publication Date Title
US9667153B2 (en) Switching power supply apparatus for generating control signal for lowering switching frequency of switching devices
EP3522350B1 (fr) Dispositif de conversion de puissance
JP6260665B2 (ja) Ｄｃ／ｄｃ変換装置
JPWO2014155604A1 (ja) Ｄｃ／ｄｃコンバータ
WO2018146877A1 (fr) Dispositif d'alimentation électrique et procédé de commande de dispositif d'alimentation électrique
WO2023226896A1 (fr) Circuit de commande de module d'alimentation, module d'alimentation et dispositif électronique
US11342841B2 (en) Method for controlling resonance-type power converter, resonance-type power converter, and DC-DC converter
US20220393597A1 (en) System and methods for switching an active clamp flyback converter
JP5355655B2 (ja) Ｄｃｄｃコンバータおよびｄｃｄｃコンバータの制御方法
US8564974B2 (en) Switching power source apparatus
JP5954256B2 (ja) 制御方法
US11476748B2 (en) Method for controlling resonant power conversion device, and resonant power conversion device
WO2018186344A1 (fr) Bloc d'alimentation et procédé de commande de bloc d'alimentation
JP6662151B2 (ja) Ｄｃ／ｄｃ変換装置、コンピュータプログラム及びｄｃ／ｄｃ変換装置の制御方法
JP2002078323A (ja) 電源装置
CN112673561B (zh) 电力变换装置以及电力变换装置的控制方法
US20230268760A1 (en) Charging system
WO2018185999A1 (fr) Alimentation électrique et procédé de commande d'alimentation électrique
US11870355B2 (en) Power converting device, and control method for power converting device
WO2018163631A1 (fr) Dispositif source électrique et procédé de commande de dispositif source électrique
JP2019146384A (ja) 電源装置及び電源装置の制御方法
WO2019131469A1 (fr) Dispositif d'alimentation électrique et son procédé de commande
CN114598153A (zh) 电压转换装置
CN113824333A (zh) 改良型llc谐振转换装置
JP2018107869A (ja) 昇降圧変換装置及び昇降圧変換装置の制御方法

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 17895620

Country of ref document: EP

Kind code of ref document: A1

ENP Entry into the national phase

Ref document number: 2018566756

Country of ref document: JP

Kind code of ref document: A

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 17895620

Country of ref document: EP

Kind code of ref document: A1