WO2017073150A1 - Dispositif d'alimentation électrique et procédé de commande associé - Google Patents

Dispositif d'alimentation électrique et procédé de commande associé Download PDF

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Publication number
WO2017073150A1
WO2017073150A1 PCT/JP2016/074780 JP2016074780W WO2017073150A1 WO 2017073150 A1 WO2017073150 A1 WO 2017073150A1 JP 2016074780 W JP2016074780 W JP 2016074780W WO 2017073150 A1 WO2017073150 A1 WO 2017073150A1
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Prior art keywords
converter
cell
inverter
power supply
temperature
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PCT/JP2016/074780
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English (en)
Japanese (ja)
Inventor
祐樹 河口
充弘 門田
尊衛 嶋田
泰明 乗松
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株式会社日立製作所
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Priority to JP2017547652A priority Critical patent/JP6482676B2/ja
Priority to CN201680061181.6A priority patent/CN108174625B/zh
Publication of WO2017073150A1 publication Critical patent/WO2017073150A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/49—Combination of the output voltage waveforms of a plurality of converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/501—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode sinusoidal output voltages being obtained by the combination of several pulse-voltages having different amplitude and width

Definitions

  • the present invention relates to a power supply device in which a large number of power conversion devices that use an AC or DC voltage as a power source and supply a desired AC voltage to a load with a transformer are connected in series, and a control method thereof.
  • SST is a high-frequency transformer driven at a high frequency of several kHz to several hundred Hz, a converter that drives the high-frequency transformer, an inverter that outputs an AC voltage of several tens Hz that is the same as the system frequency, using the output voltage of the converter as a power source, etc. It is a substitute for the conventional insulation transformer by comprising from this power converter.
  • a power converter such as a converter or an inverter is added to the conventional isolation transformer alone, but miniaturization by driving the isolation transformer at a high frequency of several tens to several hundreds of kHz Even in the configuration of the SST to which the converter is added, a significant reduction in size and weight can be realized as compared with the conventional isolation transformer driven at several tens of Hz.
  • the SST functions as an insulating transformer, and the SST itself also functions as a power converter.
  • Non-Patent Document 1 As a specific configuration example of a power conversion device using SST, for example, a configuration disclosed in Non-Patent Document 1 has been proposed.
  • the power conversion device described in Non-Patent Document 1 can be applied to high-voltage / high-power applications by connecting a small-capacity, low-breakdown-voltage power conversion device using a high-frequency transformer in a multi-series / multi-parallel connection.
  • the SST which is a small-capacity, low-voltage power conversion device using a high-frequency transformer, will be described on the assumption that it is connected in a multi-series / multi-parallel manner.
  • the connected SST is called a cell converter.
  • Patent Document 1 is disclosed as means for solving this problem.
  • the temperature detection means for detecting the internal temperature of each converter is provided, the output current of the converter having a high temperature is reduced, By increasing the output current of the converter having a low temperature, the internal temperatures of the plurality of converters are made uniform.
  • Patent Document 1 is limited to a configuration in which inputs and outputs of a plurality of converters are connected in parallel, and does not describe anything regarding a configuration in which the inputs or outputs of the converters are connected in series.
  • the AC outputs of a plurality of cell converters are connected in parallel to constitute a power supply device applied to a high voltage / high power application, and each cell converter is determined individually.
  • a constant voltage determined for each period is output, and a sine wave of an AC system is generated by combining a number of outputs connected in series.
  • a power supply device configured by connecting a plurality of cell converters configured in SST in series
  • temperature variation between the cell converters is appropriately controlled and further appropriately protected. It is an object of the present invention to provide a power supply apparatus capable of performing the above and a control method thereof.
  • a cell converter that converts a direct current to a high frequency in a converter and then converts the direct current through a high-frequency transformer and generates a rectangular voltage from the direct-current voltage provided by the converter in an inverter.
  • a plurality of cell converters, and a rectangular voltage that is an output of an inverter of a plurality of cell converters is connected in series to obtain a low-frequency alternating current, and is provided for each cell converter according to an output command value.
  • the present invention is also provided with "a plurality of cell converters that convert a direct current into a high frequency in a converter and then convert the direct current through a high frequency transformer, and generate a rectangular voltage from a direct current voltage provided by the converter in an inverter.
  • a power supply device that obtains low-frequency alternating current by connecting rectangular voltages that are output from inverters of a converter in series, and the inverter in a plurality of cell converters includes a smoothing capacitor between the converters and a full bridge A switching element with an anti-parallel diode configured, and the inverter turns on or off the switching element with the anti-parallel diode configured in a full bridge so that the current flowing to the AC side does not flow to the smoothing capacitor.
  • the present invention includes a plurality of cell converters that convert a direct current to a high frequency in a converter and then convert the direct current through a high frequency transformer and generate a rectangular voltage from a direct current link voltage provided by the converter in an inverter.
  • a power supply device that obtains low-frequency alternating current by connecting a rectangular voltage that is an output of an inverter of a cell converter in series, and a control device provided for each of the plurality of cell converters The inverter output currents are equal and the converter input currents are different from each other. ”
  • the present invention also provides a cell having a converter that converts a direct current to a high frequency and then converts the direct current through a high frequency transformer to generate a rectangular voltage from the direct current voltage provided by the converter in the inverter and includes a capacitor between the converter and the inverter.
  • a method of controlling a power supply device comprising a plurality of converters, wherein a rectangular voltage that is an output of an inverter of a plurality of cell converters is connected in series to obtain low-frequency alternating current, and is a rectangular shape that is an output of a cell converter
  • the voltage period is set in advance to a different time length for each cell converter, and when the temperature of the switching elements constituting the converter or inverter varies, the rectangular voltage of the cell converter having a high temperature The period is shortened, the period of the rectangular voltage of the other cell converter is lengthened, and the operation is continued.
  • the converter converts the direct current into a high frequency and then converts the direct current through a high-frequency transformer, generates a rectangular voltage from the direct-current voltage provided by the converter in the inverter, and has a capacitor between the converter and the inverter.
  • a plurality of cell converters are connected, and the rectangular voltage that is the output of the inverters of the plurality of cell converters is connected in series to obtain low-frequency alternating current, and the converter and inverter are switched with anti-parallel diodes configured in a full bridge
  • a method of controlling a power supply device constituted by an element wherein when the temperature of a switching element constituting a converter or an inverter is high, the converter of the cell converter is stopped and the current flowing to the AC side is Fully-bridged anti-parallel diode that flows in one direction With respect to one or more healthy cell converters among the plurality of cell converters, the current flowing on the AC side is in a second direction opposite to the first direction of the smoothing capacitor.
  • the switching element with the anti-parallel diode configured in a full bridge is turned on or off so as to flow ".
  • the temperature of the cell converter can be made uniform even in a power converter configured by connecting inputs or outputs of a plurality of cell converters in series. Therefore, it becomes possible to suppress the bias
  • FIG. 3 is a diagram illustrating a configuration example of a power supply device according to the first embodiment.
  • the figure which shows the circuit structural example of the inverter in the cell converter of FIG. The figure which shows the circuit structural example of the converter in the cell converter of FIG.
  • the flowchart which shows the determination logic of the control apparatus of the power supply device of FIG.
  • FIG. 6 is a diagram showing an inverter circuit configuration and a current flow in mode 1 of FIG. 5.
  • FIG. 6 is a diagram showing an inverter circuit configuration and a current flow in mode 2 of FIG. 5.
  • FIG. 6 is a diagram showing an inverter circuit configuration and a current flow in mode 3 of FIG. 5.
  • FIG. 6 is a diagram showing an inverter circuit configuration and a current flow in mode 4 of FIG. 5.
  • FIG. 6 is a diagram showing an inverter circuit configuration and a current flow in mode 5 of FIG. 5.
  • FIG. 6 is a diagram showing an inverter circuit configuration and a current flow in mode 6 of FIG. 5.
  • FIG. 6 is a diagram showing an inverter circuit configuration and a current flow in mode 7 of FIG. 5.
  • FIG. 6 is a diagram showing an inverter circuit configuration and a current flow in mode 8 of FIG. 5. The figure which shows the inverter circuit structure and the flow of an electric current in the mode 5 of FIG. 5 at the time of temperature dispersion
  • FIG. 6 is a diagram showing an inverter circuit configuration and a current flow in mode 6 of FIG.
  • FIG. 10 is a flowchart illustrating determination logic of a control device of the power conversion device according to the second embodiment.
  • FIG. 9 is a flowchart illustrating determination logic of a control device of a power conversion device according to a third embodiment. The figure explaining the concept of the electric power interchange using the inverter in Example 3.
  • FIG. FIG. 10 is a flowchart illustrating determination logic of a control device of the power conversion device according to the second embodiment. The wave form diagram explaining operation
  • FIG. 9 is a flowchart illustrating determination logic of a control device of a power conversion device according to a third embodiment. The figure explaining the concept of the electric power interchange using the inverter in Example 3.
  • FIG. 13 is a diagram showing an inverter circuit configuration and a current flow in mode 31a of FIG.
  • FIG. 13 is a diagram showing an inverter circuit configuration and a current flow in a mode 31b of FIG. 12;
  • FIG. 13 is a diagram showing an inverter circuit configuration and a current flow in a mode 31c of FIG.
  • FIG. 13 is a diagram showing an inverter circuit configuration and a current flow in a mode 32a in FIG.
  • FIG. 13 is a diagram showing an inverter circuit configuration and a current flow in mode 32b of FIG. 12;
  • FIG. 13 is a diagram showing an inverter circuit configuration and a current flow in a mode 32c in FIG.
  • FIG. 13 is a diagram showing an inverter circuit configuration and a current flow in mode 34 of FIG. 12.
  • FIG. 13 is a diagram showing an inverter circuit configuration and current flow in mode 35 of FIG. 12.
  • FIG. 1 is a diagram illustrating a configuration example of a power supply device according to a first embodiment of the present invention.
  • a power supply apparatus 100 whose overall schematic configuration is shown in FIG. 1 includes, for example, four cell converters 1a, 1b, 1c, and 1d, and the input terminals of the cell converters 1a, 1b, 1c, and 1d are connected in parallel.
  • AC power is supplied to the system 3, which is a load, by connecting the output terminals in series, using the power supply 2 as an input, and outputting an arbitrary AC voltage Vinv. Since the AC voltage Vinv given by the configuration of FIG. 1 is for one phase, when the three-phase AC is used, the configuration of FIG.
  • cell converters 1a, 1b, 1c, and 1d are converters 6a, 6b, 6c, and 6d that generate arbitrary DC voltages Vdc1, Vdc2, Vdc3, and Vdc4 from a power source 2, respectively, and DC voltages Vdc1, Vdc2, and Vdc3. , Vdc4 as inputs, and inverters 7a, 7b, 7c, 7d that generate AC voltages, converters 6a, 6b, 6c, 6d, temperatures Tc1, Tc2, Tc3, Tc4, and inverters 7a, 7b, 7c, 7d. It comprises control means 5a, 5b, 5c and 5d for detecting temperatures Ti1, Ti2, Ti3 and Ti4. Note that the SST corresponds to the circuit portion composed of the converters 6a, 6b, 6c, and 6d and the inverters 7a, 7b, 7c, and 7d.
  • Temperature information detected by the control means 5a, 5b, 5c, 5d is transmitted to the control device 4.
  • the control device 4 determines the output command value of each cell converter 1a, 1b, 1c, 1d based on the detected temperature information, and the control means 5a, 5b, 5c of each cell converter 1a, 1b, 1c, 1d. 5d, output command values Pref1, Pref2, Pref3, Pref4 are transmitted.
  • the control means 5a, 5b, 5c, 5d of each cell converter 1a, 1b, 1c, 1d are connected to the inverters 7a, 7b, 7c, 7d and the converter 6a, according to the given output command values Pref1, Pref2, Pref3, Pref4. 6b, 6c and 6d are controlled.
  • the inverters 7a, 7b, 7c, and 7d include a smoothing capacitor C7, four switching elements Q1, Q2, Q3, and Q4 connected in a full bridge, and switching elements Q1, Q2, and Q3. , Q4 and diodes D1, D2, D3, and D4 connected in antiparallel to each other, and an AC / DC converter circuit is configured to generate an arbitrary AC voltage from the DC voltage Vdc determined by the converter 6, respectively.
  • the converters 6a, 6b, 6c, and 6d include an input capacitor C1, switching elements H1, H2, H3, and H4 connected in a full bridge, and switching elements H1, H2, H3, and H4. Is composed of diodes DH1, DH2, DH3, DH4 connected in reverse parallel to each other, a resonant capacitor Cr, a transformer T, four rectifier diodes Dr1, Dr2, Dr3, Dr4 connected in a bridge, and a filter capacitor Cm. DC voltage Vdc is generated.
  • the transformer T is composed of a step-up inductor Lr, a primary winding N1, and a secondary winding N2, and may be a so-called LLC transformer including the resonance capacitor Cr.
  • an orthogonal transformation circuit is configured by bridge connection of the switching elements H1, H2, H3, and H4 and the diodes DH1, DH2, DH3, and DH4, and the DC input of the power source 2 is several kHz to several Convert to a high frequency of 100 Hz.
  • the transformer T can be significantly reduced in size and weight as compared with a single insulating transformer that has been driven at several tens of Hz by securing a high-frequency transformer while ensuring insulation.
  • the high-frequency output on the secondary side of the transformer T is rectified in a rectifier circuit including rectifier diodes Dr1, Dr2, Dr3, and Dr4 to obtain a DC voltage Vdc.
  • the SST is configured by the inverter 7 of FIG. 2 and the converter 6 of FIG.
  • FIG. 4 is a flowchart showing the determination logic of the control device 4 of the power supply device 100 of FIG.
  • the temperature information Tc1, Tc2, Tc3, Tc4, Ti1, Ti2, Ti3, Ti4 detected by each cell converter 1a, 1b, 1c, 1d is input to the control device 4.
  • the In process step S102 the presence / absence of temperature variation between the cell converters is determined based on the temperature information input in process step S101.
  • Processing step S103 is performed when it is determined that there is temperature variation in processing step S102, and generates an output command value for the cell converter so as to reduce the input current of the cell converter having a high temperature.
  • the processing step S104 is performed when it is determined in the processing step S102 that there is a temperature variation, and generates an output command value for the cell converter so as to increase the input current of the cell converter having a low temperature. Thereby, the sum total of the output command value which the control apparatus 4 of the power supply device 100 gives is hold
  • the output command value of each cell converter 1a, 1b, 1c, 1d by the control device 4. Pref1, Pref2, Pref3, Pref4 are determined.
  • FIGS. 5, 6a, 6b, 6c, and 6d are diagrams for explaining operation modes of the power supply device 100 according to the first embodiment.
  • FIG. 5 shows operation waveforms of the power supply device 100 according to the first embodiment
  • FIGS. 6a, 6b, 6c, and 6d show circuit diagrams illustrating circuit operations of the power supply device according to the first embodiment.
  • operation waveforms of the power supply device 100 of FIG. 5 will be described.
  • a voltage waveform and an input current to the converter in one cycle of the AC system voltage are shown as operation waveforms.
  • T1 is a positive half-wave period and T2 is a negative half-wave period.
  • the converters 6a, 6b, 6c, and 6d in the four cell converters 1a, 1b, 1c, and 1d having the configuration of FIG. 1 have the DC voltages Vdc1 and Vdc2 having respective predetermined magnitudes.
  • Vdc3 and Vdc4 are continuously generated, while the inverters 7a, 7b, 7c and 7d generate a rectangular AC voltage only during a predetermined conduction period.
  • a sinusoidal AC voltage Vinv is finally determined.
  • the converter 6 adjusts the size and the inverter 7 is in the conduction period. As described below, the adjustment will be described.
  • the DC voltages Vdc1, Vdc2, Vdc3, and Vdc4 determined by the converters 6a, 6b, 6c, and 6d are assumed to be constant.
  • the inverter 7a applies a positive DC voltage Vdc1 during the period from time t0 to time t7
  • the inverter 7b applies the positive DC voltage Vdc2 during the period from time t1 to time t6.
  • the inverter 7c applies a positive DC voltage Vdc3 during the period from time t2 to time t5
  • the inverter 7d generates a positive AC voltage Vdc4 during the period from time t3 to time t4, thereby generating a positive AC waveform.
  • inverter 7a applies negative DC voltage Vdc1 during the period from time t9 to time t16
  • inverter 7b applies negative DC voltage Vdc2 during the period from time t10 to time t15
  • inverter 7c operates from time t11 to time t11.
  • a negative DC voltage Vdc3 is applied during the period t14
  • the inverter 7d applies a negative DC voltage Vdc4 during the period from time t12 to time t13, thereby generating a negative AC waveform.
  • the output command values Pref1, Pref2, Pref3, Pref4 given from the control device 4 to the control means 5a, 5b, 5c, 5d of the cell converters 1a, 1b, 1c, 1d finally realize the sine waveform of FIG. Accordingly, information such as the size and timing to be borne by each cell converter 1a, 1b, 1c, and 1d is given as a command.
  • the voltage command This will be described as a value Vref.
  • the sinusoidal voltage command value Vref is given to the control means 5a, 5b, 5c, 5d of each cell converter 1a, 1b, 1c, 1d, and the DC voltage to be borne by each of the control means 5a, 5b, 5c, 5d.
  • the magnitude of Vdc is determined, and the timing for starting and stopping each flow is determined.
  • FIG. 5 shows the magnitude of the direct current input from the power source 2 to each cell converter 1a, 1b, 1c, 1d when the voltage is applied by each cell converter 1a, 1b, 1c, 1d. ing.
  • DC currents I1a, I1b, I1c, and I1d having large values flow in the order of cell converters 1a, 1b, 1c, and 1d having a long conduction period.
  • the DC currents I1d, I1b, I1c, and I1a having large values flow in the order of the cell converters 1d, 1b, 1c, and 1a having the long conduction periods.
  • the alternating current Iinv has a sine wave system in which the inverter output currents are equal in a plurality of cell converters.
  • the power supply device of the first embodiment is controlled such that the output currents Iinv of the inverters are equal and the input currents I1a, I1b, I1c, and I1d of the converters are different in a plurality of cell converters. You can say that. Further, based on the detected temperature information, the input current of the cell converter having a high temperature is decreased and the input current of the cell converter having a low temperature is increased.
  • FIGS. 6a, 6b, 6c, and 6d show circuit configurations and current paths of the inverters 7a, 7b, 7c, and 7d in each period of FIG.
  • the state in the period from time t0 to t1 is shown in FIG. 6a as mode 1
  • the state in the period from time t1 to t2 is shown in FIG. 6b as mode 2
  • the state in the period from time t2 to t3 is shown as mode 3.
  • the state in the period from time t3 to t4 is shown as mode 4 in FIG.
  • C7a, C7b, C7c, and C7d are smoothing capacitors provided on the input side of the inverters 7a, 7b, 7c, and 7d.
  • the mode 2 is entered.
  • In mode 2 time t1 to t2 shown in FIG. 6b, in the state of mode 1, switching element Q1b of inverter 7b is turned on. By doing so, in the inverter 7b, a current flows in the loop of the switching element Q4b, the smoothing capacitor C7b, and the switching element Q1b.
  • Inverters 7a, 7c and 7d operate in the same manner as in mode 1.
  • the output voltage Vinv of the power supply device is the sum of the DC voltage Vdc1 of the cell converter 1a and the DC voltage Vdc2 of the cell converter 1b.
  • the mode 3 is entered.
  • mode 3 time t2 to t3 shown in FIG. 6c, in the state of mode 2, switching element Q1c of inverter 7c is turned on. By doing so, in the inverter 7c, a current flows in the loop of the switching element Q4c, the smoothing capacitor C7c, and the switching element Q1c.
  • Inverters 7a, 7b and 7d operate in the same manner as in mode 2.
  • the output voltage Vinv of the power supply device is the sum of the DC voltage Vdc1 of the cell converter 1a, the DC voltage Vdc2 of the cell converter 1b, and the DC voltage Vdc3 of the cell converter 1c.
  • the output voltage Vinv of the power supply device is the sum of the DC voltage Vdc1 of the cell converter 1a, the DC voltage Vdc2 of the cell converter 1b, the DC voltage Vdc3 of the cell converter 1c, and the DC voltage Vdc4 of the cell converter 1d.
  • the switching element Q4a is turned on in the inverter 7a.
  • 7A, 7b, 7c, and 7d show a circuit configuration and a current flow for realizing a negative sine wave voltage in the range of 180 to 360 degrees of the output voltage Vinv of the power supply device.
  • 7a is a diagram showing an inverter circuit configuration in mode 5 of FIG. 5
  • FIG. 7b is a diagram showing an inverter circuit configuration in mode 6 of FIG. 5
  • FIG. 7c is a diagram showing an inverter circuit configuration in mode 7 of FIG.
  • FIG. 7d is a diagram showing an inverter circuit configuration in mode 8 of FIG.
  • FIGS. 7a, 7b, 7c, and 7d are matters that can be easily estimated from the circuit configuration and current flow of FIGS. 6a, 6b, 6c, and 6d, Although detailed description is omitted, basically, in the case of the inverter 7 sharing the AC voltage Vinv, the switching elements Q2 and Q3 are turned on, the other switching elements Q1 and Q4 are turned off, and the switching element Q2 A current flows through the loop of the smoothing capacitor C7 and the switching element Q3. In the other inverter 7 that does not share the AC voltage, the switching element Q3 is turned on, and a current flows through the loop of the diode D1 and the switching element Q3.
  • the order of each mode may be carried out in the order of mode 5, mode 6, mode 7, and mode 8 following the order in the positive wave.
  • the above operation describes the operation in the control device 4 when it is determined that there is no temperature variation in the processing step S102 of FIG. 4, and the circuit configuration realized thereby. On the other hand, if it is determined in step S102 in FIG. 4 that there is a temperature variation, the following processing is performed.
  • the control device 4 determines that the temperature of the cell converter 1 detected by the control device 4 is the highest in the cell converter 1a and the temperature of the cell converter 1d is the lowest. Shall.
  • the control device 4 generates output command values so that the roles of the cell converter 1a and the cell converter 1d are switched in the negative half cycle T2 of the voltage command value as shown in FIG. Send an output command to the cell converter.
  • the cell converter 1a that has generated a rectangular wave voltage during the period from time t8 to time t16 in a normal state is changed to generate a rectangular wave voltage during the period from time t12 to time t13.
  • the cell converter 1d that has generated a rectangular wave voltage during the period from time t12 to time t13 in a normal state is changed to generate a rectangular wave voltage during the period from time t8 to time t16.
  • the input current of the cell converter 1a having a high temperature is decreased and the input current of the cell converter 1d having a low temperature is increased. It becomes possible.
  • FIG. 8a, FIG. 8b, FIG. 8c, and FIG. 8d show the circuit configuration and current flow for realizing a negative sine wave voltage when temperature variation occurs.
  • 8a is a diagram showing an inverter circuit configuration in mode 5 of FIG. 5 when temperature varies
  • FIG. 8b is a diagram showing an inverter circuit configuration in mode 6 of FIG. 5 when temperature varies
  • FIG. 8c is a diagram when temperature varies.
  • FIG. 8D is a diagram showing an inverter circuit configuration in mode 7 in FIG. 5
  • FIG. 8D is a diagram showing an inverter circuit configuration in mode 8 in FIG. 5 when temperature varies.
  • FIGS. 8a, 8b, 8c, and 8d can be easily estimated from the circuit configuration and current flow of FIGS. 7a, 7b, 7c, and 7d.
  • mode 5 time t9 to t10
  • mode 6 time t10 to t11
  • the inverter 7b is added and the inverters 7b and 7d share the AC voltage.
  • mode 7 time t11 to t12
  • the inverter 7c is further added and the inverters 7b, 7c and 7d share the AC voltage.
  • mode 8 time t12 to t13
  • an inverter 7a having a small temperature margin is added, and the inverters 7a, 7b, 7c, and 7d share the AC voltage.
  • the current flow period of the inverter 7a having a small temperature margin is minimized, and temperature generation is suppressed.
  • the output command value is generated so that the roles of the cell converter 1a and the cell converter 1d are switched in the negative period after this. Needless to say, it is continued even after the next positive half-wave period.
  • the output command value used as the drive pattern of a cell converter can be determined based on the temperature information detected by the temperature detection means with which each cell converter was equipped. Thereby, since the temperature of a cell converter can be averaged, the dispersion
  • the number of cell converters in series is four.
  • the number of gradations of the output voltage of the power converter can be increased by further increasing the number of stages, the grid and power conversion It is possible to reduce the size of the filter inductor and the filter capacitor connected between the devices, that is, the size of the power conversion device.
  • the input of the cell converter is a common power source, but the present invention is not limited to this. It is good also as a structure which connected the independent power supply for every cell converter.
  • the driving pattern of the cell converter is switched every half cycle of the voltage command value. However, the driving pattern may be switched every cycle shorter than the half cycle of the voltage command value or every several cycles.
  • the first embodiment is a solution that focuses on the flow period of the cell converter, in which the flow period in the cell converter is replaced between a cell converter having a thermal margin and a cell converter having no margin. is there.
  • the second embodiment focuses on the DC link voltage Vdc of the converter, which is another control factor in the cell converter, and the DC link voltage Vdc of the cell converter having a thermal margin is set higher.
  • the DC link voltage Vdc of the cell converter having no thermal margin is set low.
  • Example 2 of the present invention will be described with reference to FIGS.
  • the configuration of the power supply device according to the second embodiment is the same as that according to the first embodiment, and a description thereof will be omitted.
  • differences from the first embodiment will be described.
  • FIG. 9 is a flowchart illustrating the determination logic of the control device 4 of the power supply device of FIG. 1 in the second embodiment.
  • a description will be given with reference to FIG.
  • the temperature information Tc1, Tc2, Tc3, Tc4, Ti1, Ti2, Ti3, Ti4 detected by each cell converter 1a, 1b, 1c, 1d is input to the control device 4.
  • Processing step S203 generates a command value for the cell converter so as to decrease the DC link voltage Vdc of the cell converter having a high temperature when it is determined that the temperature variation is present in processing step S202.
  • the processing step S204 generates a command value for the cell converter so as to increase the DC link voltage Vdc of the cell converter having a low temperature when it is determined in the processing step S202 that the temperature variation is present.
  • the sum of the command values (DC link voltage Vdc) given by the control device 4 of the power converter is kept constant.
  • the control device 4 uses the command values Pref1, each of the cell converters 1a, 1b, 1c, and 1d. Pref2, Pref3, and Pref4 are determined.
  • the conduction period in the target cell converter is appropriately changed. This measure is essential to obtain a sinusoidal alternating voltage.
  • the control means 5a, 5b, 5c, and 5d of each cell converter 1a, 1b, 1c, and 1d control the magnitude and length of the DC link voltages Vdc1, Vdc2, Vdc3, and Vdc4 by generating converter control signals. To do.
  • FIG. 10 shows an example in which the temperature of the cell converter 1d is the highest and the temperature of the cell converter 1a is the lowest.
  • the input current I1d of the cell converter 1d can be reduced and the input current I1a of the cell converter 1a can be increased.
  • the voltage drop in the DC link voltage Vdc4 is added to the DC link voltage Vdc1 as it is, so that the voltage burdened as a whole can be kept constant.
  • fine power control can be performed by controlling the DC link voltage Vdc of the converter. Therefore, the temperature variation of the cell converter can be reduced as compared with the first embodiment. .
  • the cell conversion is performed by controlling the DC link voltage of all the cell converters. It becomes possible to further reduce the temperature variation of the vessel.
  • the input current of the converter in FIG. 10 is of a magnitude determined according to the DC link voltage Vdc of the converter and the conduction period.
  • Example 1 and Example 2 correspond to each other within the range of normal control when temperature variation of the cell converter is detected.
  • the temperature variation becomes larger, it is necessary to perform protective processing including stopping measures.
  • the third embodiment is characterized in that a protective measure is taken in addition to the first and second embodiments. As a protection measure, it is effective to stop the converter of the cell converter that has detected a high temperature. Here, however, power is exchanged from other cell converters.
  • FIG. 11 is a flowchart illustrating determination logic of the control device 4 of the power conversion device of FIG. 1 in the third embodiment.
  • the temperature information Tc1, Tc2, Tc3, Tc4, Ti1, Ti2, Ti3, Ti4 detected by the cell converters 1a, 1b, 1c, 1d is input to the control device 4.
  • Processing step S303 determines whether or not the converters 6a, 6b, 6c, and 6d of the cell converters 1a, 1b, 1c, and 1d are stopped when it is determined that there is temperature variation in the processing step S302.
  • Control in a state where there is a temperature variation but not so much as to activate the protection function is defined in processing step S305 and processing step S306.
  • the output command reduced from the control device 4 is transmitted to the converter of the cell converter determined as Tref> Tmax in the processing step S303.
  • processing step S306 when Tref> Tmax is satisfied in processing step S303, a command for increasing the output command is transmitted from the control device 4 to the converter of the cell converter having a low temperature.
  • the processing defined in processing step S305 and processing step S306 is the same as the processing content in FIG.
  • a converter stop command is generated from the control device 4 for the cell converter determined as Tref ⁇ Tmax in the processing of step S303, and the corresponding control means 5a, 5b, 5c, 5d.
  • a converter stop command is sent to. That is, when there is a temperature variation and the detected temperature Tmax is high enough to be equal to or higher than the temperature threshold value Tref, the converter is immediately stopped as a measure against overheating of the protection function.
  • the processing step S304 is obtained by adding a protection function to the function of FIG.
  • the controller 4 can determine whether or not the converter is stopped based on the temperature information of each cell converter detected by the temperature detection unit. As a result, the cell converter can be protected, and the power supply device can be highly reliable.
  • the device breakdown voltage of the semiconductor element of each cell converter must be designed to be large, leading to an increase in cost. Since the voltage sharing of the cell converter 1 can be reduced by the AC side series connection and the withstand voltage capacity of the semiconductor elements used for the inverter 7 and the converter 6 can be reduced, the power supply device can be miniaturized in combination with the adoption of SST. This means that it is necessary to allow a margin for the withstand voltage capacity per cell converter as part of the stop operation is performed, and it is necessary to take measures against the increase in size and cost.
  • the following additional measures after the converter is stopped are executed.
  • the operation of the power conversion apparatus when only the converter is stopped will be described with reference to the drawings.
  • the temperature T1a of the cell converter 1a exceeds the temperature threshold Tref during the positive half cycle of the system voltage (Tref ⁇ T1a), and additional correspondence is performed in the negative half cycle of the system voltage. .
  • additional measures will be continued in the future.
  • the control device 4 determines the operation pattern of the cell converters 1a, 1b, 1c, and 1d so that the operation period of the cell converter 1a is the shortest.
  • the operation patterns of the cell converters 1a, 1b, 1c, and 1d are set as cell converters 1d ⁇ 1b ⁇ 1c ⁇ 1a. That is, as described with reference to FIG. 5, replacement is performed such that the flow period of the cell converter 1a that needs to be protected is the shortest and the flow period of the cell converter 1d that has a margin is the longest.
  • the flow period of the cell converter 1a that needs to be protected is set between the shortest t34-t35, and the flow period of the cell converter 1d with a margin is changed to be the longest period t31-t38. It is carried out.
  • the other cell converters 1b, 1c, and 1d receive the current passing period t34. It is necessary to take measures to charge the capacitor C7a prior to -t35. This charging is called power interchange.
  • mode 31 the mode of power interchange for charging the capacitor C7a prior to the conduction period t34-t35 is denoted as mode 31.
  • Mode 31 is executed in the period from time t31 to t32 in FIG. Further, the mode 31 includes modes 31a, 31b, and 31c described below.
  • mode 31 the operation of the power supply device will be described by taking as an example the case of charging the smoothing capacitor C7a of the cell converter 1a.
  • Va, Vb, Vc, and Vd are AC side voltages provided by the cell converters 1a, 1b, 1c, and 1d, respectively, and the sum of the output voltage Vinv is controlled to be equal to the voltage command value Vref. It controls the power supplied to the load system.
  • Vinv Va + Vb + Vc + Vd
  • a circuit configuration in the cell converters 1a, 1b, 1c, and 1d in the three small modes 31a, 31b, and 31c constituting the mode 31 (period from time t31 to t32), and current paths at that time are shown in FIG. This is shown in FIGS. 13b and 13c.
  • mode 31a which is the first small mode, as shown in FIG. 13a
  • the switching elements Q1a and Q4a are turned on, and the current flows from the power supply side to the ground side in the path of Q1a ⁇ C7a ⁇ Q4a.
  • power is interchanged from the inverters 7b and 7d to the inverter 7a.
  • mode 31a and mode 31b are alternately repeated until DC voltage Vdc1 of cell converter 1a reaches target value Vdcref or until time t32.
  • the ratio of the mode 31a and the mode 31b is determined by the duty ratio D so as to satisfy the expression (2).
  • processing is performed as shown in FIG. 13c.
  • the mode 32 (time t32-t33) implemented after the mode 31 (time t31-t32) will be described.
  • the circuit configuration in the cell converters 1a, 1b, 1c, and 1d in the three small modes 32a, 32b, and 32c constituting the mode 32 (period from time t32 to t33) and the current path at that time are shown in FIG. It is shown in FIGS. 14b and 14c.
  • inverter 7a has switching elements Q1a and Q4a turned on, and current flows from the power supply side to the ground side.
  • Va + Vdc1 is given as the output voltage Va of the cell converter 1a.
  • power is interchanged from the inverters 7b, 7c, and 7d to the inverter 7a.
  • power is interchanged from the inverters 7b and 7d to the inverter 7a.
  • mode 32a and mode 32b are alternately repeated until DC voltage Vdc1 of cell converter 1a reaches target value Vdcref.
  • the ratio of the mode 32a and the mode 32b is determined by the duty ratio D so as to satisfy the above equation (2).
  • mode 33 time t33-t34
  • mode 34 time t34-t35
  • Vinv ⁇ Vdc2 ⁇ Vdc3 ⁇ Vdc4.
  • Mode 33 continues until time t34.
  • the switching elements Q2a and Q3a of the inverter 7a are in the on state, and the current flows from the power source side to the ground side through the path Q2a ⁇ C7a ⁇ Q2a.
  • the period from time t35 to t36 is the same as that in mode 33, the period from time t36 to t37 is the same as that in mode 32, and the period from time 37 to 38 is the same as that in mode 31, so detailed description is omitted. To do.
  • the stop-side inverter is stopped from the sound-side inverter in a period before the start-up time of the stop-side inverter.
  • Charging can be performed by accommodating power toward the smoothing capacitor of the side inverter, so that even when the converter is stopped, the inverters of all the cell converters can be operated.
  • the case where the cell converter 1a is charged during the period of the mode 31 and the mode 32 in FIG. 12 is described as an example.
  • the mode 31a is used during the period of the mode 31.
  • mode 31b is repeated.
  • charging of the cell converter 1a is completed only during the period of the mode 31, it may be operated so as to be fixed to the mode 32c of FIG.
  • the input currents I1a, I1b, I1c, and I1d of the converter become zero when the converter 6a is stopped in the negative half wave. Further, the input currents I1b and I1d of the converters 6b and 6d of the cell converters 1d and 1b participating in the power interchange increase, but the input current I1c of the converter 6c of the cell converter 1c not participating in the power interchange is changing. Absent.
  • the circuit configuration of these inverters 7 is the reverse of a full bridge configuration so that the current flowing to the AC side does not flow to the smoothing capacitor.
  • the first state eg, 7b, 7c, 7d in FIG. 6a
  • the second state for example, 7a in FIG.
  • the inverter 7a connected to the stopped converter has the first current flowing in the AC side opposite to the first direction of the smoothing capacitor C7a.
  • the third state (for example, 7a in FIG. 13a) in which the switching element with the anti-parallel diode configured in a full bridge is turned on or off so as to flow in the direction 2 (the direction from the top to the bottom of the smoothing capacitor 7). Then, charging is performed by setting the inverter in the other cell converter to the second state.
  • the power conversion device of the present invention can be applied to a power conversion device linked to a high-voltage commercial system such as solar power generation, wind power generation, and electric railway.
  • 1a, 1b, 1c, 1d cell converter
  • 2 power supply
  • 3 system
  • 4 control device
  • 5a, 5b, 5c, 5d control means
  • 6, 6a, 6b, 6c, 6d converter
  • T Transformer 7, 7a, 7b, 7c, 7d: Inverter, H1, H2, H3, H4, Q1, Q2, Q3, Q4, Q1a, Q2b, Q3c, Q4d: Switching element, DH1, DH2, DH3, DH4, D1 , D2, D3, D4: anti-parallel diode, Dr1, Dr2, Dr3, Dr4: rectifier diode
  • Lr boost inductor
  • Cr resonant capacitor
  • N1 primary winding
  • N2 secondary winding
  • C1 input capacitor
  • Cm DC capacitor
  • C7, C7a, C7b, C7c, C7d Smoothing capacitor

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L'invention concerne un dispositif d'alimentation électrique et un procédé de commande associé, dans lequel une variation de température entre des transformateurs cellulaires peut être régulée de façon appropriée et une protection adaptée peut être établie dans un dispositif d'alimentation électrique configuré par la connexion en série de transformateurs cellulaires multiples configurés avec des transformateurs à semi-conducteurs (SST). Le dispositif d'alimentation selon l'invention est pourvu de transformateurs cellulaires multiples dans lesquels du courant continu est converti en une haute fréquence, puis converti en courant continu par l'intermédiaire d'un transformateur haute fréquence dans un convertisseur, la tension de courant continu fournie par le convertisseur sert à générer une tension rectangulaire dans un onduleur, et la tension rectangulaire qui est la sortie des onduleurs des transformateurs cellulaires multiples est connectée en série pour fournir un courant alternatif basse fréquence. Ce dispositif d'alimentation électrique comprend : des moyens de commande dont est doté chaque transformateur cellulaire et qui régulent la tension rectangulaire, c'est-à-dire la sortie du transformateur cellulaire pertinent, conformément à une valeur d'instruction de sortie, les périodes de la tension rectangulaire ayant été prédéfinies à une durée différente pour chaque transformateur cellulaire ; des moyen de détection de température qui détectent la température d'éléments de commutation constituant les convertisseurs et onduleurs ; ainsi qu'un dispositif de commande qui fournit à chaque moyen de commande la valeur d'instruction de sortie, qui reflète des variations de température détectées par le moyen de détection de température. Lorsque se produisent des variations de température, les périodes des tensions rectangulaires, qui ont été prédéfinies pour être différentes pour chaque transformateur cellulaire, sont modifiées et le fonctionnement continue.
PCT/JP2016/074780 2015-10-29 2016-08-25 Dispositif d'alimentation électrique et procédé de commande associé WO2017073150A1 (fr)

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CN111193414A (zh) * 2018-11-15 2020-05-22 航天科工惯性技术有限公司 一种环境自适应油水分离电源设备及系统

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JPWO2019130533A1 (ja) * 2017-12-28 2020-11-19 新電元工業株式会社 電力変換装置
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JP6622442B1 (ja) * 2018-10-18 2019-12-18 株式会社東芝 電力変換装置、電力変換システム、電力変換方法、及びプログラム
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