WO2016163066A1 - Dispositif de conversion de puissance - Google Patents

Dispositif de conversion de puissance Download PDF

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Publication number
WO2016163066A1
WO2016163066A1 PCT/JP2016/001204 JP2016001204W WO2016163066A1 WO 2016163066 A1 WO2016163066 A1 WO 2016163066A1 JP 2016001204 W JP2016001204 W JP 2016001204W WO 2016163066 A1 WO2016163066 A1 WO 2016163066A1
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WIPO (PCT)
Prior art keywords
voltage
circuit
power converter
power supply
switching element
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PCT/JP2016/001204
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English (en)
Japanese (ja)
Inventor
藤井　幹介
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富士電機株式会社
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Publication of WO2016163066A1 publication Critical patent/WO2016163066A1/fr

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode

Definitions

  • the present invention relates to a power conversion device that performs AC-DC-AC conversion using a plurality of power converters composed of semiconductor switching elements, and relates to a technique applicable to, for example, an uninterruptible power supply.
  • FIG. 4 is a configuration diagram of the uninterruptible power supply described in Patent Document 1.
  • the uninterruptible power supply 100 includes an AC-DC conversion converter 102 connected to a three-phase AC power supply 200 via an input filter 101.
  • the uninterruptible power supply 100 includes a DC-AC conversion inverter 105 connected to a converter 102 via a DC intermediate circuit 104 having a series circuit of capacitors 103a and 103b.
  • the uninterruptible power supply 100 includes an output filter 106 connected between the AC output side of the inverter 105 and the load 300.
  • the uninterruptible power supply 100 also includes a voltage detector 107 that detects an AC input voltage, a current detector 108 that detects an AC input current, and a current detector 109 that detects the current of a DC voltage source 120 such as a storage battery. And a voltage detector 110 that detects the voltage of the DC voltage source 120.
  • the uninterruptible power supply 100 includes a chopper 111 for DC-DC conversion, a voltage detector 112 that detects the voltages of the capacitors 103a and 103b, a power failure detection circuit 113 that detects a power failure of the three-phase AC power source 200, And a control circuit 114 that controls the semiconductor switching elements in the converter 102, the inverter 105, and the chopper 111 based on the outputs of the detectors 107 to 110, 112 and the power failure detection circuit 113.
  • FIG. 5 is a specific configuration diagram of the converter 102 and the inverter 105 of FIG. 4, both of which are configured by a three-level circuit.
  • the three-level circuit is a power converter that can mutually convert a DC voltage and an AC voltage that changes to three voltage levels by the operation of the semiconductor switching element.
  • 102R, 102S, and 102T are the respective phase arm portions of the converter 102
  • 105U, 105V, and 105W are the respective phase arm portions of the inverter 105
  • P is the positive potential point of the DC bus
  • N is the negative potential point
  • M is Indicates a neutral point (intermediate potential point).
  • the converter 102 and the inverter 105 are constituted by a three-level circuit, and these three-level circuits are connected via the positive and negative potential points P and N and the neutral point M of the DC intermediate circuit, a capacitor
  • the voltages of the capacitors 103a and 103b may become unbalanced due to differences in the capacitances of the capacitors 103a and 103b and the characteristics of the switching elements.
  • this voltage imbalance occurs, not only the voltage and current according to the command value cannot be output from the inverter 105 to the load 300, but also an overvoltage is applied to the switching element, and in the worst case, the device may be destroyed. .
  • the control circuit 114 shown in FIG. 4 performs balance control by adjusting the zero-phase voltage according to the voltage deviation of the capacitors 103 a and 103 b during the operation of the converter 102.
  • the chopper 111 includes an arm part 111a including four semiconductor switching elements Q 1 to Q 4 and a reactor 111b, and the voltage of the capacitors 103a and 103b is set at the time of a power failure of the AC power supply 200. Accordingly, the balance elements are controlled by controlling the switching elements Q 1 to Q 4 .
  • Patent Document 2 A technique for performing balance control by adjusting the zero-phase voltage as described above is also described in Patent Document 2.
  • the three-level circuit can be configured as shown in FIG. This circuit is described in Patent Document 3, for example. That is, in the three-level circuit for one phase, the semiconductor switching elements S 1 and S 2 are connected in series between the positive potential point P and the negative potential point N of the DC power supply, and the series connection point is used as the AC terminal U. , between the intermediate potential point M of the DC power source and the AC terminal U, which are connected to the bidirectional switch S 3 consisting of antiparallel circuit of two reverse blocking type IGBT (RB-IGBT).
  • RB-IGBT reverse blocking type IGBT
  • positive potential P of the DC power supply by turning on the switching element S 1 is a negative potential N of the DC power supply by turning on the switching element S 2 is an intermediate potential M of the DC power supply by turning on the bidirectional switch S 3 is, Each will appear at the AC terminal U.
  • Japanese Patent No. 5463289 (FIG. 1, FIG. 2, FIG. 4, paragraphs [0029] to [0039], etc.)
  • Japanese Patent No. 2888104 (FIGS. 1 to 3, paragraphs [0036] to [0039], etc.) JP 2013-240252 A (FIG. 1 etc.)
  • a plurality of devices may be connected in parallel between the AC power supply 200 and the load 300 and used.
  • FIG. 8 shows an example in which two uninterruptible power supply devices 100A and 100B are connected in parallel, the number of parallel units may be two or more.
  • the configuration of uninterruptible power supply 100A, 100B is the same as that of uninterruptible power supply 100 shown in FIG. 4, and only the main part is shown in FIG. As shown in FIG.
  • the common mode circulating current needs to be reduced because it may cause a reduction in device efficiency and power supply quality.
  • the chopper 111 is always operated.
  • a method of performing balance control can be considered.
  • the chopper 111 for supporting the three-level circuit needs to be configured by four semiconductor switching elements Q 1 to Q 4 like the arm portion 111a shown in FIG. 6, and this chopper 111 is always operated.
  • the balance control is performed, there is a problem in that losses in the switching elements Q 1 to Q 4 and the reactor 111b increase to cause a reduction in device efficiency.
  • the problem to be solved by the present invention is to control the balance of capacitors in a series intermediate circuit when a plurality of power conversion units that perform AC-DC-AC conversion are connected in parallel between an AC power source and a load. Is to provide a power converter capable of reducing the common mode circulating current.
  • one aspect of a power conversion device is a first power converter capable of mutually converting a DC voltage and an AC voltage changing to three voltage levels by the operation of a semiconductor switching element.
  • a second power converter a first capacitor connected between a positive potential point and an intermediate potential point formed between the first power converter and the second power converter, a negative potential point and an intermediate point
  • a DC intermediate circuit composed of a series circuit of a second capacitor connected between the potential points and a DC voltage between the potential points in the DC intermediate circuit and a DC voltage of the DC voltage source by the operation of the semiconductor switching element.
  • a third power converter capable of mutual conversion, the first power converter supplied with AC power, a DC intermediate circuit, a second power converter for supplying AC voltage to the load, and a third 1 unit with power converter
  • a power conversion unit is configured, and a plurality of power conversion units are connected in parallel between the AC power supply and the load.
  • the power conversion unit includes a first power converter, a second power converter, and And a control circuit for controlling each of the third power converters, wherein the control circuit of at least one power conversion unit has a predetermined value of a zero-phase current flowing through either the first power converter or the second power converter.
  • the zero-phase voltage of the first power converter is changed based on the voltage deviation of the first capacitor and the second capacitor to suppress the potential fluctuation at the neutral point.
  • the operation of the third power converter is controlled to suppress the potential fluctuation at the neutral point.
  • the first power converter when the zero-phase current flowing through the first or second power converter is small, the first power converter performs balance control by changing the zero-phase voltage, and when the zero-phase current is large. Balance control is performed by the third power converter. For this reason, a loss can be reduced compared with the case where balance control is always performed using a third power converter made of, for example, a chopper, and a highly efficient power converter can be provided. Further, when balance control is performed by the third power converter, the voltage source through which the zero-phase current flows is equivalently removed from the circuit, so that the common mode circulating current can be reduced.
  • FIG. 1 It is a figure which shows the power conversion unit in embodiment of this invention. It is a block diagram of the circulating current detection circuit in FIG. It is principle explanatory drawing of embodiment of this invention. It is a lineblock diagram of the uninterruptible power supply indicated in patent documents 1. It is a block diagram of the converter and inverter in FIG. It is a block diagram of the chopper in FIG. It is a circuit diagram which shows the other structural example of a 3 level circuit. It is a block diagram of a system in which two uninterruptible power supply devices are connected in parallel.
  • an AC-DC-AC conversion power conversion unit including a converter 102, an inverter 105, and a chopper 111 between a three-phase AC power supply 200 and a load 300.
  • a plurality of units (corresponding to the uninterruptible power supply devices 100A and 100B in FIG. 8) are connected in parallel, and the converter 102 and the inverter 105 are all configured by a three-level circuit.
  • the converter 102 corresponds to a first power converter
  • the inverter 105 corresponds to a second power converter
  • the chopper 111 corresponds to a third power converter.
  • FIG. 1 specifically shows a converter 102, a chopper 111, and their control circuits in a power conversion unit according to an embodiment of the present invention, and parts having the same functions as those in FIG. Therefore, the description will be omitted, and in the following, the description will focus on parts different from FIG.
  • the voltage between the terminals of the capacitor of the input filter 101 is detected as the input voltage detection values V R , V S , and V T of the converter 102 by the input voltage detector DV0.
  • the output current of the input filter 101 is input current detection value I R by the input current detecting unit DI, I S, is detected as I T.
  • the voltage between the terminals of the capacitors 103a and 103b of the DC intermediate circuit 104 is detected as the voltage detection values E dp and E dn between the terminals by the voltage detectors DV1 and DV2.
  • the adder 11 adds the detected voltage values E dp and E dn of the capacitors 103 a and 103 b of the DC intermediate circuit 104 detected by the voltage detectors DV 1 and DV 2.
  • a subtractor 12 calculates a deviation between the added value (E dp + E dn ) output from the adder 11 and the DC voltage target value E * .
  • the multiplier 14 outputs the output of the regulator 13 that operates so that the voltage deviation becomes zero and the input voltage detection values V R , V S , and V T of the converter 102 detected by the voltage detection unit DV0 for each phase. Multiply. As a result, input current command values It R , It S and It T for each phase of converter 102 are generated.
  • the correction command value V 0 * is added to the input voltage command value of each phase output from the adder 17 in the previous stage, so that the voltage command values V R * , V S * , V of each phase are added. T * is generated.
  • These voltage command values V R * , V S * , and V T * control the input / output voltage of the converter 102 to a predetermined value, and make the voltages E dp and E dn of the capacitors 103 and 104 equal by balance control.
  • the adder 11, the subtracter 12, the adjuster 13, the multiplier 14, the subtracter 15, the adjuster 16 and the adder 17 constitute a command value calculation circuit 35.
  • the PWM circuit 21 performs PWM calculation according to the voltage command values V R * , V S * , and V T * , and generates a drive signal (gate signal) for controlling on / off of the semiconductor switching element of the converter 102. Output.
  • an abnormality detection flag that is a high level signal is output from the abnormality detection circuit 22.
  • the balance control by the converter 102 is stopped and the converter 102 is gate-blocked.
  • the control of the chopper 111 is different between when the three-phase AC power supply 200 is abnormal and when it is normal.
  • the abnormality of the three-phase AC power supply 200 is a concept including not only a power failure but also a significant voltage drop (voltage fluctuation), and the abnormality detection circuit 22 described below may be considered as an abnormality detection circuit of the AC power supply 200. good.
  • the normally open switch 28 is turned on by the abnormality detection flag output from the abnormality detection circuit 22, and the normally closed switch 26 is turned off.
  • the first DC power supply voltage control circuit 27 operates so that the DC voltage (E dp + E dn ) matches the target value E * , and the output of the first DC power supply voltage control circuit 27 via the normally open switch 28 and the adder 29 The result is input to each end of the subtractor 33.
  • the correction command value V 0 * output from the second neutral point potential control circuit 30 is Input to the other ends of the adder 32 and the subtractor 33.
  • the outputs of the adder 32 and subtracter 33 are input to the PWM circuit 34 as voltage command values V 103 * and V 104 * of the capacitors 103 and 104 .
  • the second neutral point potential control circuit 30 is configured in the same manner as the first neutral point potential control circuit 18.
  • the normally closed switch 19, the normally open switch 31, and the OR gate 24 constitute a selection unit 40.
  • the PWM circuit 34 performs PWM calculation according to the input voltage command values V 103 * and V 104 * , and generates and outputs a drive signal (gate signal) for controlling on / off of the semiconductor switching element of the chopper 111. . Thereby, balance control is performed while making the DC voltage (E dp + E dn ) coincide with the target value E * .
  • the charging current of the DC voltage source 120 is reduced to a predetermined value or less by the second DC power supply voltage control circuit 25 to which the voltage detection value V bat and the current detection value I bat of the DC voltage source 120 are input. A voltage command value for controlling charging while being suppressed is generated. At this time, as shown in FIG.
  • the PWM circuit 34 switches only the switching elements Q 1 and Q 4 in FIG. 6 to increase the efficiency of the chopper 111, and the remaining switching elements Q 2 , the Q 3 operates to the gate block state.
  • the normally closed switch 19 is turned off and the normally open switch 31 is turned on by the output of the OR gate 24. As a result, converter 102 enters a state where balance control is not performed.
  • voltage command values V 103 * and V 104 * obtained by adding and subtracting the correction command value V 0 * from the second neutral point potential control circuit 30 to the output of the second DC power supply voltage control circuit 25 are changed to the PWM circuit 34. Is input.
  • the PWM circuit 34 operates so as to switch all the switching elements Q 1 to Q 4 in FIG. 6, and the chopper 111 performs balance control.
  • Whether the balance control is performed by the converter 102 or the chopper 111 is determined by the abnormality detection circuit 22 and the circulating current detection circuit 23 provided on the input side of the OR gate 24.
  • the abnormality detection circuit 22 does not detect an abnormality due to a power failure or a significant voltage drop of the AC power supply 200, and the common mode circulating current detected by the circulating current detection circuit 23 is smaller than a predetermined value, it is always on.
  • the balance control is performed by the converter 102 using the correction command value V 0 * output from the first neutral point potential control circuit 18 via the normally closed switch 19, and the chopper 111 performs the balance control under other conditions. Do.
  • FIG. 2 is a configuration diagram of the circulating current detection circuit 23.
  • This circulating current detecting circuit 23 each phase (R, S, T phase) current detection value I R in, I S, common mode circulating current (zero-phase current by adding the I T adders 23a, at 23b ) And the absolute value is calculated by the absolute value calculator 23c. Further, the circulating current detection circuit 23 supplies the output of the absolute value calculator 23c to the comparator 23e through a low-pass filter 23d for preventing unnecessary false detection due to noise. Then, the circulating current detection circuit 23 outputs a circulating current detection flag that becomes a high level signal to the OR gate 24 when the output of the low-pass filter 23d is equal to or higher than the upper limit level in the comparator 23e.
  • FIG. 3 is a diagram for explaining the principle of this embodiment.
  • the converters 102 of the power conversion units (uninterruptible power supply devices) 100A and 100B connected in parallel perform power conversion. Since it operates, a circulation path of the common mode circulation current is formed through the switching elements of both converters 102. For this reason, the normally open switch 140 shown in FIG. 3 is turned on and the voltage source 150 for supplying the zero-phase current is connected to the circuit, so that the converter 102 adjusts the zero-phase voltage.
  • the chopper 111 mainly performs balance control
  • the converter 102 does not perform power conversion and zero-phase voltage adjustment. For this reason, the circulation path of the common mode circulating current is not formed, and the voltage source 150 is removed from the circuit by turning off the normally open switch 140, whereby the common mode circulating current can be reduced.
  • the converter 102 when the AC power supply 200 is normal and the common mode circulating current is less than a certain value, the converter 102 causes the DC voltages E dp and E dn of the capacitors 103a and 103b of the DC intermediate circuit 104 to be used. Adjust the balance.
  • the chopper 111 when the AC power supply 200 is normal and the common mode circulating current is greater than or equal to a certain value and when the AC power supply 200 is abnormal, the chopper 111 causes the DC voltages E dp and E of the capacitors 103a and 103b of the DC intermediate circuit 104 to be Adjust dn balance.
  • the balance control of the capacitor of the series intermediate circuit 104 is realized with high efficiency and the balance control is performed by the chopper 111, the voltage source for flowing the common mode circulating current is equivalently removed from the circuit.
  • the common mode circulating current can be reduced.
  • loss can be reduced and a highly efficient power conversion device can be provided as compared with the case where balance control is always performed using the chopper 111.
  • the circulating current detection circuit 23 need not be provided in both the power conversion units (uninterruptible power supply) 100A and 100B, and may be provided in either one. Further, since the first neutral point potential control circuit 18 and the second neutral point potential control circuit 30 have the same configuration, if the correction command value V 0 * to be output is the same value, the second neutral point potential control circuit 18 and the second neutral point potential control circuit 30 have the same configuration.
  • the point potential control circuit 30 is omitted, a normally open switch 31 is provided in parallel with the normally closed switch 19 on the output side of the first neutral point potential control circuit 18, and the adders 32 and 33 are connected via this state switch 31. May be supplied with a correction command value (zero-phase voltage command value) V 0 * .
  • the present invention is not limited to the case where the present invention is applied to an uninterruptible power supply, and the present invention is applied to another power conversion unit including a first power converter, a second power converter, and a third current converter. Can do.
  • the parallel number of power conversion units can be set arbitrarily.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Rectifiers (AREA)
  • Power Conversion In General (AREA)
  • Ac-Ac Conversion (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L'objectif de la présente invention est de pourvoir à un dispositif de conversion de puissance qui présente un haut rendement par utilisation sélective de convertisseurs de puissance pour une commande d'équilibrage de condensateurs en série, et de réduire le courant circulant en mode commun. De multiples unités de conversion de puissance sont connectées en parallèle entre une alimentation en courant alternatif triphasé (200) et une charge (300), chacune des unités de conversion de puissance comprenant un convertisseur (102) et un onduleur (105) qui sont chacun un circuit à trois niveaux, un circuit intermédiaire en courant continu (104) comprenant des condensateurs (103a, 103b), et un hacheur (111). Quand l'alimentation en courant alternatif est normale et un courant à phase nulle circulant dans le convertisseur (102) ou l'onduleur (105) est inférieur à une valeur prédéterminée, un circuit de commande modifie la tension à phase nulle du convertisseur (102) en fonction d'un écart de tension entre les condensateurs (103a, 103b) afin de réaliser une commande d'équilibrage. Quand l'alimentation en courant alternatif est anormale, ou quand le courant à phase nulle est supérieur ou égal à la valeur prédéterminée, le circuit de commande commande le fonctionnement du hacheur (111) afin de réaliser une commande d'équilibrage.
PCT/JP2016/001204 2015-04-06 2016-03-04 Dispositif de conversion de puissance WO2016163066A1 (fr)

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JP2015077460A JP2018093558A (ja) 2015-04-06 2015-04-06 電力変換装置
JP2015-077460 2015-04-06

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CN108761304A (zh) * 2018-04-03 2018-11-06 国家电网有限公司 动态泄能装置的参数整定方法、装置及仿真设备
JP2019054625A (ja) * 2017-09-14 2019-04-04 パナソニック株式会社 電力変換装置及びランキンサイクルシステム
JP6571903B1 (ja) * 2018-11-20 2019-09-04 東芝三菱電機産業システム株式会社 無停電電源装置

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JP6779339B1 (ja) * 2019-06-03 2020-11-04 三菱電機株式会社 電力変換器

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JP2013176296A (ja) * 2008-08-22 2013-09-05 Toshiba Mitsubishi-Electric Industrial System Corp 電力変換装置
JP2013255317A (ja) * 2012-06-06 2013-12-19 Meidensha Corp ３レベルインバータの制御装置

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Publication number Priority date Publication date Assignee Title
JP2001061283A (ja) * 1999-08-19 2001-03-06 Yaskawa Electric Corp ３相中性点クランプ式ｐｗｍインバータ装置
JP2013176296A (ja) * 2008-08-22 2013-09-05 Toshiba Mitsubishi-Electric Industrial System Corp 電力変換装置
JP2013255317A (ja) * 2012-06-06 2013-12-19 Meidensha Corp ３レベルインバータの制御装置

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Publication number Priority date Publication date Assignee Title
JP2019054625A (ja) * 2017-09-14 2019-04-04 パナソニック株式会社 電力変換装置及びランキンサイクルシステム
CN108761304A (zh) * 2018-04-03 2018-11-06 国家电网有限公司 动态泄能装置的参数整定方法、装置及仿真设备
CN108761304B (zh) * 2018-04-03 2020-08-25 国家电网有限公司 动态泄能装置的参数整定方法、装置及仿真设备
JP6571903B1 (ja) * 2018-11-20 2019-09-04 東芝三菱電機産業システム株式会社 無停電電源装置
WO2020105126A1 (fr) * 2018-11-20 2020-05-28 東芝三菱電機産業システム株式会社 Dispositif d'alimentation électrique sans coupure
KR20210003815A (ko) * 2018-11-20 2021-01-12 도시바 미쓰비시덴키 산교시스템 가부시키가이샤 무정전 전원 장치
US11228258B2 (en) 2018-11-20 2022-01-18 Toshiba Mitsubishi-Electric Industrial Systems Corporation Uninterruptible power supply apparatus
KR102475947B1 (ko) 2018-11-20 2022-12-08 도시바 미쓰비시덴키 산교시스템 가부시키가이샤 무정전 전원 장치

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