WO2015118678A1 - モータ電力変換装置 - Google Patents
モータ電力変換装置 Download PDFInfo
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- WO2015118678A1 WO2015118678A1 PCT/JP2014/052994 JP2014052994W WO2015118678A1 WO 2015118678 A1 WO2015118678 A1 WO 2015118678A1 JP 2014052994 W JP2014052994 W JP 2014052994W WO 2015118678 A1 WO2015118678 A1 WO 2015118678A1
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- motor
- loss
- total loss
- value
- temperature
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P29/00—Arrangements for regulating or controlling electric motors, appropriate for both AC and DC motors
- H02P29/60—Controlling or determining the temperature of the motor or of the drive
Definitions
- the present invention relates to a motor power converter, and more particularly to a motor power converter that detects motor loss and performs overload protection.
- induction type motor induction type motor
- inverter driven by speed control application as power source.
- Permanent magnet type brushless DC motor is used, and semiconductors, liquid crystal manufacturing devices, electronic parts manufacturing and assembly machines, industrial robots, metal processing machines, forging machines, etc.
- Amusement machines, medical devices, electronic machines other than production sites Permanent magnet AC servomotors for acceleration, constant speed operation, deceleration, positioning stop, etc. in speed, torque control, position control applications, etc., utilizing excellent servo control such as automatic toll collection systems, elevators, and vehicle simulators.
- An induction motor dedicated to vector control inverter driving is used.
- a forging machine an automobile body or the like is die-cut from a plate material and drawing is performed by a press machine.
- an AC servomotor excellent in low speed and high torque characteristics is used as a drive motor.
- high-performance permanent magnet rare earth e.g., neodymium (Nd)
- Nd neodymium
- Dy dysprosium
- the maximum efficiency of the AC servomotor for servo press was specially designed to be the low speed and high torque region which is most frequently used.
- This iron loss causes the voltage applied to the motor to be high even in the induction type motor, and in the case of the overexcitation state, the motor current may be burnt even if it is equal to or less than the rated current.
- a method of stopping the motor operation and preventing burnout is taken by detecting the motor current as motor overload detection and detecting the electronic thermal protection that operates with a constant current squared time product, but iron loss It can not be protected by detection of motor current.
- the iron loss may cause burnout even if the motor current is lower than the rated current if the voltage applied to the motor is high even in the induction type motor and the motor is over-excited.
- Table 2 on page 45 of Non-Patent Document 1 shows measures for reducing motor losses.
- mechanical loss, iron loss, primary copper loss, secondary Five types of copper loss and stray load loss are shown.
- the secondary copper loss is excluded when the motor is an induction type and the rotor is an AC servomotor of permanent magnet or DCBL.
- FIG. 3 on page 45 shows the relationship between motor loss and load factor, and it is described that iron loss and mechanical loss are not affected by load factor fluctuation.
- Patent Document 1 it is assumed that overheat protection of the motor is reliably taken into consideration in consideration of iron loss that increases when the motor is operated in the overexcitation state with the induction motor, and electronic thermal protection that performs ordinary overload protection can not be used.
- the ratio of the rated voltage / rated frequency that becomes the reference of the motor and the output voltage command / frequency command corrected by the frequency voltage calculator is calculated as the magnetic flux ratio, and the motor is judged to be over-excitation, A method of performing overheat protection by correcting the detected current value of the motor according to the excitation state is shown.
- Patent Document 2 is an induction motor, and as a motor protection device, a temperature detector is installed in the vicinity of a stator winding to prevent burning of the stator winding, but the installation of the temperature detector increases the cost. is there.
- the overload protection of the motor is carried out only by the copper loss, and the rotation loss including the mechanical loss and the iron loss has not been considered for the overload detection, and the sum of the predicted values of both the copper loss and the rotation loss
- the overload is determined to be detected when it is determined that the value exceeds the predetermined value, the value for each type of loss is not discussed.
- the average value of each of the motor current detection value and the motor rotation speed detection value is determined, divided by the rated current and the rated rotation speed, and discussed with the total value of the sum of the respective ratios. There was no mention of the type of loss and the amount of each.
- the protection against temperature rise of the motor due to the influence of iron loss, mechanical loss and stray load loss is that the monitoring of electronic thermal by motor current can not be overload protection, and it is an accurate overload protection method to replace motor current detection. .
- the core loss is determined by magnetic field analysis simulation because a magnetic circuit is formed by the material of the core of the rotor, the plate thickness, and the cross-sectional hole shape of the core.
- a motor power converter provided with an electronic thermal function for overload protection of a motor, it operates with a constant total loss time product of the motor, outputs an integrated value simulating the winding temperature of the motor, and the integrated value is predetermined
- the motor power conversion device has a total loss time integration counter that outputs a signal to stop the operation of the motor when it reaches the threshold.
- the total loss time integration counter operates with a constant total loss time product of the motor including the loss of the inverter of the motor power converter.
- the motor works to convert electrical energy into work energy.
- all of the input power Pin input to the motor does not serve as work energy, and a part is wastefully consumed inside the motor to generate heat and sound.
- the power useful for work is the output power Pout, which provides torque T and rotational speed Nf to the load connected to the motor. Input and output are expressed in units of W (watts).
- the relational expressions of the input Pin, the output Pout, the loss Ploss and the efficiency ⁇ are represented by the following (Equation 3) (Equation 4).
- the loss of the motor is mostly conducted as heat through metal solids such as fixtures, from the cooling ribs on the motor surface to natural air or forced convection, radiation into the atmosphere, and some is dissipated as sound into the environment.
- the temperature rise of the motor generates heat as copper loss (square of the current flowing through the winding) x (winding resistance), and iron loss changes the magnetic flux generated in the iron core, causing the core and magnet on the stator side
- the embedded rotor core of the embedded structure generates heat.
- the core on the stator side has a motor winding, and when the core generates heat due to iron loss, the temperature of the winding also rises through the core.
- mechanical loss causes loss of bearing friction and fan ventilation resistance to increase the motor winding temperature.
- Stray load loss is a decrease in magnetic flux density in the gap between the rotor and the stator other than those mentioned here.
- the total loss amount obtained by summing various losses is accurately detected, and based on this, the motor can be protected from burnout prevention and the like of the coil.
- FIG. 5 is a view for explaining overload protection of the AC servomotor drive power conversion system with a permanent magnet type sensor according to FIG. 2; It is a figure explaining the overload protection of the vector control motor drive power conversion system with an induction type sensor by FIG. 1A.
- FIG. 5 is a view for explaining overload protection of the AC servomotor drive power conversion system with a permanent magnet type sensor according to FIG. 2; It is a figure explaining the overload protection of the vector control motor drive power conversion system with an induction type sensor by FIG. 1A.
- FIG. 5 is a diagram for explaining overload protection of a vector control motor drive power conversion system with an inductive sensor according to FIG. 2; It is a figure explaining the overload protection of a permanent magnet type sensorless DCBL motor drive power conversion system by FIG. 1A.
- FIG. 5 is a diagram for explaining overload protection of a permanent magnet type sensorless DCBL motor drive power conversion system according to FIG. 2; It is a figure explaining the overload protection of the induction type sensorless vector control motor drive power conversion system by FIG. 1A.
- FIG. 5 illustrates overload protection of the inductive sensorless vector control motor drive power conversion system according to FIG. 2; It is a figure explaining the overload protection of the induction type VF inverter control general purpose motor drive power conversion system by FIG. 1A.
- FIG. 5 illustrates overload protection of the inductive sensorless vector control motor drive power conversion system according to FIG. 2; It is a figure explaining the overload protection of the induction type VF inverter control general purpose motor drive power conversion system by FIG. 1A.
- FIG. 5 is a diagram for explaining overload protection of the induction type VF inverter control general-purpose motor drive power conversion system according to FIG. 2; It is a time chart explaining the speed at the time of the positive / reverse acceleration / deceleration operation in this embodiment, a torque, and an output.
- FIG. 6 is a diagram for explaining the rotational speed-torque characteristics in the present embodiment and the polarity of the sign of the output in a four quadrant area. It is a figure explaining the equivalent circuit for one phase of the permanent-magnet type synchronous motor of this embodiment. It is a figure explaining the vector figure at the time of power running of the permanent magnet type synchronous motor of this embodiment. It is a figure explaining the vector figure at the time of regeneration of the permanent magnet type synchronous motor of this embodiment.
- FIG. 7 is a diagram for explaining input, loss, and output power in the rotational speed-torque characteristic of the motor at the time of power running according to the present embodiment. It is a figure explaining an input, loss, and output electric power in motor rotation speed-torque characteristic at the time of regeneration of this embodiment. It is a figure explaining the electronic thermal operation time at the time of addition and subtraction of this embodiment. It is a figure explaining the weight value at the time of all the loss maximum application of this embodiment. It is a figure explaining the weight value at the time of the total loss time product of the electronic thermal of this embodiment. It is a figure explaining overload protection characteristic curve b) different from Drawing 14 of this embodiment.
- FIG. 19 is a partial view of the electronic thermal circuit of the overload protection characteristic curve b) of FIG. 18 replacing the electronic thermal circuit of FIGS. 3 a to 7 b of the present embodiment. It is a figure explaining operation of motor winding temperature of this embodiment. It is a figure explaining the driving
- FIG. 1A shows a diagram for explaining the loss of the motor 1a in the motor drive power conversion system.
- 1a is an AC motor.
- the power supply supplied from the AC power supply is rectified by the forward converter 2 a, smoothed by the smoothing capacitor 3, and converted into direct current.
- the direct current power source converts it into an alternating current again by the reverse converter 4, and drives the motor 1a while controlling the torque and rotational speed of the motor 1a.
- the reverse converter 4 is composed of the switching element 5 and the flywheel diode 6.
- the output Pout of the motor 1a is the rotational speed Nf and the torque T, which are applied to the load as power for the motor output shaft to drive the machine.
- the unit of motor output Pout is shown as watts (W).
- the input power Pin is given from the motor drive unit by each phase voltage V, current I, and power factor cos ⁇ which is a phase difference between phase voltage V and current I, and the unit is shown by watt (W) as three-phase power.
- the difference between input power and output power is total loss, including copper loss, iron loss, stray load loss, and mechanical loss. The entire loss including these changes to the heat and noise of the motor and is emitted to the periphery.
- the width of the arrow in the figure represents the magnitude of the power, and in the steady state, the motor 1a obtains the input power Pin and outputs the motor output Pout, so the input power Pin is large and the motor output Pout is small.
- the amount of loss is Ploss.
- FIG. 1B shows the case of the elevator motor 1b in which the motor performs four quadrant operation.
- the elevator motor vertically moves up and down, and when it descends, performs a regenerative operation that smoothly moves the speed downward while suppressing the vehicle cage falling in the direction of gravity while outputting the motor torque in the upward direction.
- the motor rotation shaft is turned from the outside when the carriage of the vehicle falls by gravity, so a kind of generator mode is set, and the generated (regenerated) energy is returned from the elevator motor 1b to the reverse converter 4
- the smoothing capacitor 3 is charged with power generation (regeneration) energy.
- the configuration is the same as that of the inverter 4; it regenerates the power generation (regeneration) energy stored in the smoothing capacitor 3 into a power source through 49 alternating current reactors.
- the relationship between the input power Pin and the motor output Pout is that the energy flows from the load (machine) side through the motor 1b, the reverse converter 4, the smoothing capacitor 3, the forward converter with power regeneration function 2b, the AC reactor 49 Through the power source to be regenerated.
- the direction of the arrow in the figure is opposite to that in FIG. 1b, and the width of the arrow is the largest for the motor output Pout and the smaller for the input power Pin.
- the direction of the arrow of loss Ploss is the direction of loss in the same direction as that of FIG. 1a, and the direction of the arrow can not be reverse (energy is generated).
- the configuration of the motor and motor drive power converter is the same as that of FIG. 1a, but the input power Pin is not the input terminal of the motor but the input of the inverter 4 of the motor drive, It is a portion of the smoothing capacitor 3 which is an intermediate potential of the output point of 2a. This is because in the user machine, the motor and motor drive power converter are installed together in the machine, the temperature rise of the motor drive power converter in the same room also rises with the temperature rise of the motor, and the mutual loss raises the room temperature. Is shown as the sum of the motor and the motor drive converter.
- FIG. 3A is a diagram for explaining an overload protection block diagram of an AC servomotor drive power conversion system with a permanent magnet encoder (sensor).
- the point at which the input power Pin is detected is the output of the inverter 4 (input terminal portion of the motor) shown in FIG. 1a.
- 2a is a forward converter to full-wave rectify the AC power supply, convert it into DC, and smooth it to smooth DC with a smoothing capacitor 3;
- This DC power supply is connected to the reverse converter 4 and is composed of six flywheel diodes connected in anti-parallel to the five switching elements.
- the output of the inverter 4 is connected to the motor 1a through 9 and 10 U-phase and W-phase current detectors CTu and CTw provided on the power line.
- the motor 1a shows the whole motor.
- the motor 1a is an AC servomotor, is a permanent magnet synchronous motor 7a, is mechanically connected to the permanent magnet synchronous motor 7a and the motor shaft, and detects the position and rotational speed of the motor 7a.
- an encoder 8 for detecting the magnetic pole position of the rotor.
- the output of the encoder 8 is output to the position / speed magnetic pole position calculator 17 a of the control logic circuit 29.
- the amplified signal Iq becomes a torque current command and is output to the q-axis current error amplifier 27.
- the current of the permanent magnet synchronous motor 7a is detected by the U-phase current detector CTu 9 and the W-phase current detector CTw 10, and becomes the current feedback Iuf and Iwf signals. It is output to the converter 16.
- the Iuf and Iwf signals are input, and the 3-phase signal is converted into a 2-phase signal represented by d and q axis orthogonal.
- the position / velocity magnetic pole position calculator 17a converts the magnetic pole position signal ⁇ r of the rotor of the motor 7a into a two-phase signal of d and q axes.
- One torque feedback current Iqf of the 3-phase / 2-phase converter 16 takes a difference (Iq-Iqf) with the torque current command signal Iq in the q-axis current error amplifier 27, and the q-axis current controller (ACR) 13 Is amplified and the q-axis motor voltage command Vq is output.
- the control is performed by the magnetic flux of the permanent magnet of the rotor.
- a current of a certain value is supplied to the d-axis current command Id, field weakening control or control of power factor or efficiency is performed by changing the current phase.
- the d-axis current command Id outputs the difference (Id-Idf) from the d-axis current feedback Idf in the d-axis current error amplifier 26, and is amplified by the d-axis current controller (ACR) 12, and the d-axis motor voltage command It becomes Vd.
- the Vd and Vq signals are converted by the two-phase / three-phase converter 14 from the two-phase signal of d-axis and q-axis orthogonal to the three-phase signal Vu, Vv, Vw.
- the position / speed magnetic pole position calculator 17a converts the magnetic pole position signal ⁇ r of the rotor as a reference.
- the three-phase signals Vu, Vv, Vw are given as a gate signal of the switching element 5 of the inverter 4 in the form of a PWM (Pulse Width Modulation) signal by the PWM circuit 15, and controlled by the permanent magnet type synchronous motor (SM) 7a. It is supposed to be
- the speed magnetic pole position calculator 17a and the error amplifiers 25 to 27 are realized by cooperation of a CPU or DSP with software.
- each block diagram in the total loss calculation / accumulation circuit 23 is realized by cooperation of the arithmetic unit and software.
- the motor current feedback Iuf and Iwf signals are used by the torque calculator 18 to calculate the motor torque T. When the d-axis current command Id is zero, the motor torque T is proportional to Iqf.
- the torque in the case of giving a current to the d-axis current command Id is calculated by calculation of a motor constant and Idf and Iqf.
- the motor output Pout is shown in FIG.
- FIG. 8 is a time chart explaining the speed, torque, and output of the permanent magnet type motor during acceleration / deceleration operation.
- the figure shows acceleration during normal rotation and reverse rotation, constant speed (both power running operation) and deceleration (regenerative operation), torque during acceleration / deceleration is load torque T1 due to friction, and acceleration torque is positive direction during forward rotation
- the decelerating torque is added in the negative direction.
- the load torque due to friction is negative
- the acceleration torque is added in the negative direction
- the deceleration torque is added positively.
- the output Pout is the product of the rotational speed Nf and the positive / negative polarity of the torque T, and is represented as the output Pout (W) in FIG.
- FIG. 9 is a diagram for explaining the rotational speed-torque characteristics and the polarity of the sign of the output in the four quadrant area.
- the rotational speed is (+)
- the output Pamax multiplied by the torque (+) is power running at (+).
- the rotation speed and torque are both (-) in the third quadrant, and the multiplied output is the product of (-) each other and becomes the power running with (+).
- the first quadrant only the polarity of the torque is reversed (-) in the fourth quadrant, and the output is (-) for regenerative operation.
- the torque of the third quadrant is reversed (+), and the output is (-), which is a regenerative operation.
- a current calculator 20 calculates an effective current I of the motor according to the following equation (5).
- the calculated effective current I is output to the motor input power calculator 21.
- a motor phase voltage (effective value) V is input to the motor input power calculator 21 from the two-phase / three-phase converter 14. Since the two-phase / three-phase converter 14 calculates the three-phase voltages Vu, Vv, Vw and outputs them to the PWM circuit 15, the effective value V thereof is obtained.
- FIG. 10 is a diagram for explaining an equivalent circuit of one phase of a permanent magnet type synchronous motor.
- the permanent magnet synchronous motor rotates, it becomes a generator and generates an induced voltage E0.
- the current flows as Iqf, a voltage drop of Ra ⁇ Iqf occurs in the resistance Ra of the motor winding, and a reactance drop of j ⁇ ⁇ La ⁇ Iqf occurs in the inductance La. 11 and 12 show this in a vector diagram.
- FIG. 11 is a vector diagram during powering of the permanent magnet synchronous motor, and FIG.
- FIGS. 11 and 12 are vector diagram during regeneration of the permanent magnet synchronous motor.
- the phase voltage ⁇ of the motor input and the phase angle ⁇ of the current are shown in FIGS. 11 and 12, and during powering, 0 ⁇ ⁇ 90 °, and cos ⁇ takes a positive value.
- ⁇ is 90 ° ⁇ ⁇ 180 °
- cos ⁇ is a negative value.
- the phase angle ⁇ is calculated by the motor input power calculator 21 as a power factor cos ⁇ .
- the three-phase input power Pin is obtained by triple the single-phase V ⁇ I cos ⁇ , and is calculated by the motor input power calculator 21.
- Pin-Pout is calculated by the subtraction circuit 28 to calculate the total loss Ploss of the motor.
- the total loss Ploss is sent to the electronic thermal circuit 22 and converted to a weight value for the total loss Ploss for each sampling ts which is an electronic thermal operation cycle, and addition, rated loss if the electronic counter exceeds the rated loss for each sampling If it is less than zero, a weight value of zero is added at the rated loss.
- a weight value of zero is added at the rated loss.
- FIG. 3B is a diagram for explaining an overload protection block diagram of the AC servomotor drive power conversion system with a permanent magnet encoder (sensor) according to FIG. 2.
- the point at which the input power Pin is detected is not the input terminal of the motor but the input of the inverter 4 of the motor drive, and the point is the same as the output of the forward converter 2a. That is, it is a point at which the intermediate potential is set. The difference from FIG.
- the DC side current detector 32 for detecting the output current Idc of the forward converter 2a and the voltage across the smoothing capacitor 3 (voltage between P and N) are detected by voltage dividing resistors, and the voltage dividing The voltage is input to Idc and Vpn to the DC input power computing unit 34 through an isolation amplifier, and the product of the signals is obtained to derive an output Pin.
- the DC side current detector 32 detects on the negative side (N side) of the forward converter 2
- the DC side current detector 32 detects even on the positive side (P side) of the forward converter 2.
- the smoothing capacitor 3 and the forward converter 2 you may detect between the smoothing capacitor 3 and the reverse converter 4 side (N side).
- the other parts are the same as those in FIG.
- the voltage Vpn at both ends is divided by the P side voltage dividing resistor 30 and the N side voltage dividing resistor 31 to isolate the voltage dividing point as an insulation amplifier
- the main circuit side and the control logic circuit 29 side are electrically isolated.
- the output of the isolation amplifier 33 is sent to the DC input power calculator 34 as Vpn.
- the DC side current detector 32 detects Idc of the main circuit, outputs a current signal Idc isolated from the secondary side of CT, and is sent to the input power calculator 34.
- the total loss Ploss is the loss of the inverter 4 (loss of the power semiconductor elements of the switching element 5 and the flywheel diode 6) to the total loss of the motor (copper loss, iron loss, stray load loss, mechanical loss, etc.) Is included.
- FIG. 4A is a diagram for explaining an overload protection block diagram of a vector control motor drive power conversion system with an inductive encoder (sensor) according to FIG. 1A.
- the motor 7b is an induction type vector control motor, and the output of the encoder 8 is output to the position / speed calculator 17b. Since no permanent magnet is used in the induction type vector control motor, there is no magnetic pole position detection signal in the position / speed calculator 17b, and the position / speed is calculated.
- the amplified signal Iq becomes a torque current command, and is output to the q-axis current error amplifier 27 and sent to the slip frequency calculator 36.
- the magnetic flux calculator 35 takes in the rotational speed Nf of the induction type vector control motor 7b, and performs constant output control at a constant magnetic flux current up to the base rotational speed and higher than the base rotational speed.
- Output The slip frequency calculator 36 outputs the slip angular frequency ⁇ s of the output in proportion to the torque current when the magnetic flux current Id is lower than the base rotational speed.
- the angular frequency ⁇ 1 ⁇ is sent to the two-phase / three-phase converter 14 and the three-phase / two-phase converter 16 to perform two-phase / three-phase conversion and three-phase / two-phase conversion based on ⁇ 1.
- the other parts are the same as those in FIG.
- the total loss calculation / integration circuit 23 is the same as that of FIG. 3A in FIG.
- FIG. 4b is a diagram for explaining an overload protection block diagram of a vector control motor drive power conversion system with an inductive encoder (sensor) according to FIG.
- the motor 7b is an induction type vector control motor, and the output of the encoder 8 is output to the position / speed calculator 17b.
- 4A differs from FIG. 4A in that the DC side current detector 32 for detecting the output current Idc of the forward converter 2a and the voltage across the smoothing capacitor 3 (voltage between P and N) are detected by voltage dividing resistors, The voltage is input to Idc and Vpn to the DC input power computing unit 34 through an isolation amplifier, and the product of the signals is obtained to derive an output Pin.
- the difference from FIG. 4A is shown below.
- the voltage Vpn at both ends is divided by the P side voltage dividing resistor 30 and the N side voltage dividing resistor 31 to isolate the voltage dividing point as an insulation amplifier
- the main circuit side and the control logic circuit 29 side are electrically isolated.
- the output of the isolation amplifier 33 is sent to the DC input power calculator 34 as Vpn.
- the DC side current detector 32 detects Idc of the main circuit, outputs a current signal Idc isolated from the secondary side of CT, and is sent to the input power calculator 34.
- the total loss Ploss is the loss of the inverter 4 (loss of the power semiconductor elements of the switching element 5 and the flywheel diode 6) to the total loss of the motor (copper loss, iron loss, stray load loss, mechanical loss, etc.) Is included.
- FIG. 5A is a diagram for explaining an overload protection block diagram of a permanent magnet type sensorless brushless DC motor (hereinafter abbreviated as DCBL motor) driving power conversion system according to FIG. 1A.
- the motor 7a is a permanent magnet sensorless DCBL motor, and the structure is a sensorless permanent magnet synchronous motor without using an encoder.
- the difference from the AC servomotor with permanent magnet encoder (sensor) in FIG. 3A is that there is no encoder (sensor), so in FIG.
- the position / velocity magnetic pole position calculator 17a becomes a position / speed estimation calculator 17c and
- the phase voltage commands Vu and Vw are input from the output of the / 3 phase converter 14, and the current feedback is input from the U-phase and W-phase current detectors CTu, CTw 9 and 10, and the motor voltage is calculated from the phase voltage command.
- the speed is estimated by estimating the induced voltage of the motor by vector operation of the voltage drop of the motor winding resistance Ra and the voltage drop of the inductance La and the reactance drop. If the velocity can be estimated by the position / speed estimation computing unit 17c, the operation of FIG. 5A can be handled in the same manner as in FIG. 3A, and the permanent magnet type sensorless DCBL motor 17a can be driven.
- the motor overload protection can be protected by the operation of the total loss calculation and integration circuit 23.
- FIG. 5A is a diagram for explaining an overload protection block diagram of a permanent magnet type sensorless DCBL motor drive power conversion system according to FIG.
- the motor 7a is a permanent magnet sensorless DCBL motor
- the structure is a sensorless permanent magnet synchronous motor without using an encoder.
- the point at which the input power Pin is detected is not the input terminal of the motor but the input of the inverter 4 of the motor drive device, and the point is the same as the output of the forward converter 2a.
- the difference from FIG. 5A is that there is a smoothing capacitor 3 between the forward converter 2a and the reverse converter 4, and the voltage Vpn across the both ends is divided by the P side voltage dividing resistor 30 and the N side voltage dividing resistor 31.
- the voltage dividing point is electrically isolated from the main circuit side and the control logic circuit 29 side by the isolation amplifier 33.
- the output of the isolation amplifier 33 is sent to the DC input power calculator 34 as Vpn.
- the DC side current detector 32 detects Idc of the main circuit, outputs a current signal Idc isolated from the secondary side of CT, and is sent to the input power calculator 34.
- the total loss Ploss is the total loss of the motor (copper loss, iron loss, stray load loss, mechanical loss, etc.), the loss of the inverter 4 (loss of the power semiconductor elements of the switching element 5 and the flywheel diode 6) Is included.
- FIG. 6A is a diagram for explaining an overload protection block diagram of the inductive sensorless vector control motor drive power conversion system according to FIG. 1A.
- the motor 7b is an induction type sensorless vector control motor, and the structure is a sensorless induction type motor without using an encoder.
- the difference from the vector control motor with inductive encoder (sensor) in FIG. 4A is that there is no encoder (sensor), so in FIG. 4A, the position / speed calculator 17b performs position / speed calculation from the output from the encoder 8.
- FIG. 4A the position / speed calculator 17b performs position / speed calculation from the output from the encoder 8.
- phase voltage commands Vu and Vw are input from the output of the two-phase / three-phase converter 14 by the position / speed estimation computing unit 17c, and U-phase / W-phase current detectors CTu, CTw 9, 10
- the current feedback is input from the above, and the speed is estimated by estimating the induced voltage of the motor by vector operation of the motor winding resistance Ra and the voltage drop of the inductance La and the reactance drop which are motor constants from the phase voltage command.
- the velocity can be estimated by the position / velocity estimation computing unit 17c
- the operation of FIG. 6A can be handled in the same manner as FIG. 4A, and the inductive sensorless vector control motor 17b can be driven.
- the motor overload protection can be protected by the operation of the total loss calculation and integration circuit 23.
- FIG. 6B is a diagram for explaining an overload protection block diagram of the inductive sensorless vector control motor drive power conversion system according to FIG. 2;
- the motor 7b is an induction type sensorless vector control motor, and the structure is a sensorless induction type motor without using an encoder.
- the point for detecting the input power Pin is not the input terminal of the motor but the input of the inverter 4 of the motor drive device, and the point is the same as the output of the forward converter 2.
- the parts different from FIG. 6A are the part of the output signal Pin of the DC input power calculator 34 from the DC side current detector 32 that detects the output current Idc of the forward converter 2 and Vpn that detects the voltage across the smoothing capacitor 3 It is.
- the input power Pin detection unit is the same as that of FIG.
- the motor overload protection can be protected by the operation of the total loss calculation and integration circuit 23.
- the total loss Ploss is the total loss of the motor (copper loss, iron loss, stray load loss, mechanical loss, etc.), the loss of the inverter 4 (loss of the power semiconductor elements of the switching element 5 and the flywheel diode 6) Is included.
- FIG. 7A is a diagram for explaining an overload protection block diagram of the induction type VF inverter control general-purpose motor drive power conversion system according to FIG. 1A.
- the motor 7b is an induction type sensorless general-purpose motor, and the structure is a sensorless induction general-purpose motor that does not use an encoder.
- the rotational speed Nf of the induction type general-purpose motor 7b is expressed by the following (Equation 6).
- a recent inverter has a sensorless vector control function as described in FIGS. 6A and 6B, and also has a function of controlling an induction general-purpose motor with constant VF control, and the user can perform sensorless vector control or It is possible to select VF constant control.
- the frequency f given to the motor is changed to control the speed.
- the voltage V is automatically changed in proportion to the frequency f, and the V / F constant control is performed.
- the rotational speed Nf of the motor rotates slower than the given frequency f by the amount of slip s.
- the basic operation of the VF inverter is described in FIG. 7a.
- the frequency command frev is input to the voltage / frequency controller 39, and the voltage / frequency controller 39 outputs f in accordance with the frequency command frev, and at the same time the voltage V is also output in proportion to the frequency f.
- the voltage V and the frequency f are sent to a three-phase distributor of 40, and phase voltages Vu, Vv and Vw which change with the frequency are input to the PWM circuit 15.
- the PWM circuit 15 applies a gate signal to the switching element 5 of the inverter 4 to drive the induction general motor 7b.
- the above is the basic operation of the VF inverter.
- the current of the induction type general-purpose motor 7b detects Iuf and Iwf by 9, 10 U-phase and W-phase current detectors CTu and CTw.
- this ideal value torque T (ideal) has a known motor constant, and a torque T (ideal) at the time of sensorless vector control can be obtained from converted values of current and torque.
- T (ideal) is sent to the 43 V / F to vector maximum torque ratio operation coefficient part.
- the V / F to vector maximum torque ratio operation coefficient unit 43 is generally disclosed in the sales material from the inverter manufacturer and is specified for each model.
- FIG. 13 is a diagram for explaining the maximum torque of the VF control inverter, and one example thereof is the output frequency (Hz) vs. output torque (%) characteristics, the maximum torque T (vec) max of sensorless vector control, and V / F control
- the maximum torque T (V / F) max is specified.
- the V / F to vector maximum torque ratio operation coefficient unit 43 multiplies the input torque T (ideal) by the maximum torque ratio operation coefficient of T (V / F) max / T (vec) max to control the VF inverter
- the motor torque T is output.
- the inverter output frequency F is output by the voltage / frequency controller 39, and the frequency F input by the synchronous rotational speed conversion factor unit 46 is multiplied by a factor (120 / 2p) to obtain the synchronous rotational speed Ns.
- the motor rotation speed Nf ⁇ Ns, and Ns is regarded as the motor rotation speed Nf, and the output Pout computing unit 19 obtains the output Pout from the calculation processing of 2 ⁇ Nf ⁇ T / 60.
- the input power Pin is a multiplier of 44
- the U-phase voltage Vu is input from the three-phase distributor 40
- the U-phase current Iuf is input from the U-phase current detector CTu 9
- the product of both signals is calculated by the multiplier 44
- the output provides single-phase input power. If this single-phase input power is tripled ( ⁇ 3) with a three-phase magnification factor of 47, the input power Pin is obtained, and the subtraction circuit 28 obtains the total loss of the induction type VF inverter drive general-purpose motor 7b from Pin-Pout. .
- the total loss Ploss is sent to the electronic thermal circuit 22 and is converted to a weight value every sampling ts which is an electronic thermal operation cycle, and addition is added if the rated loss is exceeded for the electronic counter at each sampling, if less than the rated loss At the time of subtraction and rated loss, weight value zero is added.
- all losses are constantly added and subtracted repeatedly, and when a certain threshold is reached, the motor is judged to be overloaded and an OL signal is output to the protection processing circuit 24 to stop the motor for overload protection.
- FIG. 7B is a diagram for explaining an overload protection block diagram of the induction type VF inverter control general-purpose motor drive power conversion system according to FIG.
- the motor 7b is an induction type sensorless general-purpose motor, and the structure is a sensorless induction general-purpose motor that does not use an encoder.
- the point at which the input power Pin is detected is not the input terminal of the motor, but the input of the inverter 4 of the motor drive device, and the point is the same as the output of the forward converter 2.
- FIG. 7B the point at which the input power Pin is detected is not the input terminal of the motor, but the input of the inverter 4 of the motor drive device, and the point is the same as the output of the forward converter 2.
- the total loss Ploss is the total loss of the motor (copper loss, iron loss, stray load loss, mechanical loss, etc.), the loss of the inverter 4 (loss of the power semiconductor elements of the switching element 5 and the flywheel diode 6) Is included.
- FIGS. 3A-7B show that overload protection can be achieved by total loss detection rather than protection.
- FIG. 9 is a diagram for explaining the relationship between input, output, and total loss at the time of regeneration.
- the direction is opposite to that in FIG.
- the magnitudes of the input Pin and the output Pout at the time of deceleration in iii) of FIG. 8, that is, the absolute value, the output Pout is large. This represents that the power (W) is returned from the machine side through the motor 1 to the motor drive converter 48.
- FIG. 14 is a diagram for explaining the input, loss, and output power in the speed-torque characteristics of the motor during powering.
- the horizontal axis is the rotational speed Nf
- the vertical axis is the torque T
- the maximum torque of the motor is shown by the point A-point B-point C-point D.
- rated points for the rated torque To of the motor and the rated rotational speed Nfo are indicated by black points.
- FIG. 15 is a diagram for explaining input, loss and output power in the motor rotational speed-torque characteristic at the time of regeneration.
- the horizontal axis is the rotational speed Nf
- the axis is a positive scale
- the vertical axis is a torque T
- the axis is a negative scale.
- FIG. 15 does not separately show individual losses, the portion between input power Pin and output Pout is the total loss Ploss.
- the total loss is dominated by copper loss in the high torque range in the low speed range, and iron loss in the range where the maximum torque in the high speed range is reduced. Even in the regenerative state, the total loss can always be calculated as a positive amount if the total loss can be signed according to equation (4).
- FIG. 16 is a diagram for explaining an overload protection characteristic curve of the present embodiment.
- Ploss (0) is called the rated loss
- Ploss 100 (%) ).
- the electronic thermal operation time t (s) is shown in the following (Equation 9).
- the asymptotic line Ploss 100 (%) described above is the total loss axis of the x-axis.
- the curves between the two orthogonal asymptotes are the first quadrant curve and the third quadrant curve.
- the first quadrant curve shows how many seconds a short overload operation can be operated.
- the third quadrant then shows electronic thermal operation with a total loss of less than 100%. Since the motor can be operated continuously at the rated point in the case of continuous rating, the winding temperature of the motor is manufactured to be less than the maximum allowable temperature determined by the heat resistant class.
- the amount of heat generation is reduced relative to the amount of heat release determined by the motor heat release area, and the amount of heat release is superior, so the winding temperature of the motor decreases.
- the electronic thermal integration counter continues to be added every sampling time, and approaches the upper limit value for protecting the motor. In this state, when the total loss is less than 100%, the counter integrated on the third quadrant curve is shifted to subtraction every sampling time. That is, the first quadrant curve is an addition characteristic of the electronic thermal integration counter, and the third quadrant curve is a curve showing a subtraction characteristic.
- FIG. 17 is a diagram for explaining the slope at the time of maximum application of total loss.
- the electronic thermal integration counter value at this time is 2).
- the maximum value Kf of the electronic thermal integration counter value is 6,000,000 (digit) in consideration of the quantized resolution, and the motor is stopped for protection when the counter value reaches this value. In the above example, the counter is tripped in t (trip) seconds.
- the upper limit of the working temperature in the working environment of the motor is generally 40.degree.
- the maximum allowable temperature of the motor is determined by the heat resistance class according to the standard, and is as follows.
- Motor temperature rise limit ⁇ Tmax is (maximum allowable temperature of heat resistant class)-(upper limit value of motor operating temperature 40 ° C)-Ts
- Ts is insulation to insulate winding when measuring winding temperature by resistance method
- FIG. 19 is a diagram for explaining an overload protection characteristic curve of the present embodiment which is different from FIG. A different point from FIG. 16 is that there is one curve, and the asymptote is the total loss axis of the x axis and the electron thermal operation time axis of the y axis. This is because the motor winding temperature rises if any total loss occurs, so that the motor winding temperature is faithfully simulated, and the total electronic loss time when the total loss at rated output exceeds 100% The integration counter does not start adding.
- FIG. 20 is a diagram for explaining an operation in which the winding temperature rises from the upper limit value of the motor operating temperature range to the heat resistant limit value when the motor heat resistant class and the overload are applied.
- the upper limit of the operating temperature in the operating environment of the motor is generally 40.degree.
- the maximum allowable temperature of the motor is determined by the heat resistance class according to the standard, and is as follows.
- the temperature rise limit ⁇ Tmax of the motor is expressed as (maximum allowable temperature of heat resistant class) ⁇ (upper limit 40 ° C. of motor operating temperature) ⁇ Ts (temperature difference between average temperature and maximum temperature by resistance method) as follows.
- FIG. 21 is a diagram in which the electronic total loss time integration counter using the overload protection characteristic curve of FIG. 19 is described in a hardware image.
- Reference numeral 56 denotes a full loss / pulse frequency converter, which converts the pulse frequency into a pulse frequency proportional to the total loss Ploss input and outputs it.
- the total loss amount input is increased by 20%, the number of pulse frequencies is increased by 20%.
- One of the outputs of the total loss / pulse frequency converter 56 is input to the 59 UP (add) input inhibit circuit. If the UP (addition) input inhibition circuit 59 is not in the inhibition state, the pulse frequency from the total loss / pulse frequency converter 56 is input to the total loss time integration up / down counter of 60 to simulate the motor winding temperature. Even if the counter value is a constant total loss amount input, the winding temperature increases as the accumulated amount increases, so the counter value continues to be added.
- the other output of the total loss / pulse frequency converter 56 is a dead time element circuit of 57, and is input to the DN (subtraction) input inhibit circuit of 58 through the dead time element circuit which operates for a fixed time delay. If the DN (subtraction) input inhibition circuit 58 is not in the inhibition state, the pulse frequency from the dead time element circuit 57 is input to the total loss time integration up / down counter 60 for subtraction. In this subtraction, the heat accumulated in the motor winding is dissipated by conduction through the solid through the insulating material through a solid such as iron, and is dissipated by conduction from the cooling ribs on the motor outer periphery into the atmosphere by convection or forced air cooling. Do. In order to conduct and convect, there is a delay time for heat to be transmitted to the installation contact surface and the motor surface, so the dead time element circuit 57 is configured.
- the motor can be operated continuously at rated torque and rated rotational speed and continuously rated, and heat is stored in the motor winding and temperature rises, but after the dead time due to the delay time, heat storage and heat dissipation gradually reach an equilibrium state .
- the total loss and rated loss at this time do not result in overload.
- the loss exceeds the rated loss the heat storage amount prevails over heat dissipation and the winding temperature continues to rise.
- the maximum slope rate is the maximum slope rate when adding the maximum slope rate at 100% only on the subtraction side, and the maximum subtraction slope rate is limited only at the time of subtraction. ing. Therefore, when a loss equal to or higher than the rated loss is applied, the temperature continues to rise, and the temperature is determined to be an overload, and the operation of the motor is stopped and protected.
- the total loss time integration up / down counter 60 is started after 63 motor winding temperature preset data are set in the total loss time integration up / down counter 60 when the control power is turned on or at the start of operation. It has become.
- 61 is a 40 ° C. motor winding temperature (preset at power on) circuit. The temperature of 40 ° C., which is the upper limit temperature of the motor operating temperature range when the control power is on, is transferred to the motor winding temperature at the start of 62 The motor winding temperature preset data is written.
- the total loss time integration up / down counter 60 can start from the measured winding temperature.
- FIG. 22 is a diagram for explaining the operation of the motor winding temperature.
- FIG. 22 is a diagram showing the operation of FIG. 21 in a time chart.
- the horizontal axis represents time t, and the vertical axis represents the operation of the electronic total loss time integration counter as the winding temperature T of the motor.
- the straight line rising from the origin to the upper right as indicated by the rated total loss is the heat accumulation operation of the motor winding of the addition counter on the up side of the electronic total loss time integration counter in FIG. 21 during rated operation.
- the heat dissipation operation dissipates heat by conduction and convection, and after delay time "L" until heat is transferred to the installation contact surface or motor surface, the function input to the total loss time integration counter is reversed in polarity and subtracted
- the inclination rate is the maximum subtraction inclination rate, and after the time "L” has elapsed, it is falling downward to the right.
- the straight line indicated by the rated total loss upward to the right and the straight line obtained by adding the heat radiation characteristics are indicated by the bold character broken line adding both straight lines, rising upward to the right and the time “L” It has been changing horizontally.
- the motor winding overload set temperature determined to be an overload is shown, and if this line is exceeded, it is determined to be an overload and protection operation is performed.
- the straight line which is rising sharply from the origin at maximum total loss, reaches the motor winding overload set temperature without waiting until the dead time “L”, and the overload protection stop operation is performed at the point of ⁇ .
- FIG. 23 is a diagram for explaining the post-preset operation of the motor winding temperature in the motor drive power conversion device.
- 1a is a motor
- 48 is a motor drive power converter
- the separation switch 55 at the time of motor winding resistance measurement opens this switch 55, separates the motor 1a and the motor drive power conversion device 48, and Measure with a winding resistance measuring instrument.
- 54-1, 54-2 and 54-3 are terminal blocks for selecting terminals to be measured of the motor 1a.
- 54-1 is a measurement block between motor winding U and V terminals and 54-2 is motor winding VW Measuring block between terminals
- 54-3 is a measuring block between motor coil W and U terminal.
- Switching block of measuring phase of motor coil of 54-0 selects block depending on which terminal of motor 1a to measure And measure by the resistance method.
- the resistance method is a method of calculating the temperature rise from the winding resistance value before the start of operation and after the start of operation using the fact that the temperature coefficient of the winding is known. As for the winding resistance value before the start of operation, the winding resistance value according to the ambient temperature may be recorded in advance.
- the temperature rise value measured by the winding resistance measuring device 53 of the motor and calculated and calculated the winding temperature is input to the host control device 52.
- the host control device 52 When operating the motor, remove all the switching connection pieces of the measurement phase of the motor winding of 54-0, close the separation switch 55 at the time of measuring the motor winding resistance, and then supply the control circuit power to the motor drive power converter 48. 51 is turned on, and the motor drive power conversion device 48 presets the 40 ° C. motor winding temperature. Thereafter, the main circuit power supply 50 is turned on.
- the host device 52 transfers motor temperature preset data to the motor drive power conversion device 48 by communication, rewrites the 40 ° C. motor winding temperature data, and starts the operation of the total loss time integration counter.
- FIG. 24 is a view for explaining the electronic thermal circuit 22 of FIGS. 3A to 7B of this embodiment different from FIG.
- the electronic thermal circuit 22 obtains the primary winding temperature rise value of the motor by a thermal model of the motor different from that of FIG.
- the subtraction circuit 28 subtracts "+" of the input power Pin on the left side of the figure and "-" of the output power Pout to output the total loss PLOSS as a command.
- the total loss P LOSS is subtracted from the feedback at summing point 68 and the deviation ⁇ is sent to the transfer function 70 of the motor frame heating element including the integral element.
- the total heat quantity Q (J) of the motor is expressed by equation (12) by integrating the total loss Ploss with time.
- Equation 13 the total heat quantity Q of the motor is expressed by Equation 13 when it is divided into the primary side (stator) winding of the motor and the copper bar on the secondary side (rotor).
- the rotor of the motor is a permanent magnet, secondary side copper loss does not occur.
- the temperature rise Tc1 (K) of the primary winding of the motor is the heat quantity of the primary side of the motor Q1 (J), the mass m1 (kg) of the primary motor winding, the specific heat c1 (J / kg ⁇ If K), it becomes like (Equation 14).
- the heat dissipated from the motor is conducted through metal solids such as a motor installation jig, and is naturally or forced convection or radiated from the cooling rib on the motor surface to the atmosphere.
- Heat transfer by convection between the cooling rib (solid) on the motor surface and the atmosphere (fluid) includes free convection and forced convection, and in both cases, the heat transfer is as shown in Formula 16.
- the total loss Ploss is integrated by the integral element 1 / s from (Equation 12) to make the total heat quantity Q (J) of the motor.
- Motor mass temperature increase value Tc0 is output by dividing by motor mass m0 ⁇ (motor specific heat C).
- the motor frame temperature rise value Tc0 is calculated as the difference (Tc0-Ta) from the ambient temperature Ta at the addition point 69, and the difference is calculated by the transfer function 71 of the motor frame heat dissipation part using equation (16).
- Output the heat radiation amount Qf 'of time is the heat radiation amount for each heat radiation route, for example, the heat radiation from the mounting leg of the motor and the heat radiation from the cooling rib around the motor frame are unknown, and measurement is also difficult.
- the thermal model of the motor is a negative feedback loop
- the thermal equilibrium state means that the total loss Ploss has a constant value in the steady state and the heat radiation amount Qf 'of the unit time which is the feedback amount.
- the deviation ⁇ which is the output of the summing point 68, branches from the negative feedback loop and is multiplied by the ratio k1 of the loss on the primary side to the total loss Ploss of the motor in the transfer function 72, and then the integral element in the transfer function 73 Integrate at 1 / s to obtain the heat quantity Q1 (J) of the primary winding of the motor, and calculate according to (Equation 14), that is, (mass m1 of primary winding of motor) ⁇ (specific heat c1 of primary winding (copper wire)
- the temperature rise value Tc1 of the primary winding of the motor is output by dividing by.
- the motor frame has a large mass, it is difficult to warm and cool. For this reason, even if the total loss Ploss fluctuates somewhat, the temperature rise value of the entire motor frame becomes a stable value that does not receive a large fluctuation in a short time.
- a negative feedback feedback loop is configured by a motor frame that is stable using this characteristic, and the value of total loss Ploss-the amount of heat release Qf 'per unit time is a loss that does not diverge in a thermal equilibrium state.
- the thermal time constant is sufficiently smaller than that of the motor frame, and the primary winding temperature rise value of the motor that is greatly influenced by the fluctuation of the total loss Ploss is obtained. Then, the temperature rise value of the primary winding to be overload-protected catches the fluctuation of the loss k1 ⁇ Ploss of the primary winding, monitors the peak value of the instantaneous temperature rise value, and is sent to the overload protection judging circuit 76.
- the ambient temperature Ta of the motor is input, and the initial value is set to the upper limit 40 ° C. of the working temperature of the motor.
- the control is performed as 40 ° C. regardless of the actual ambient temperature of the motor, so that even an instantaneous overload can be protected as compared with a threshold determined to be an overload.
- the transfer functions 70 and 73 in FIG. 24 have an integral element 1 / s. These 70 and 71 integral elements 1 / s are added, and one from the joining point 68 can be moved to the total loss on the command side, and the other can be moved to the feedback side for equivalent conversion.
- the command side integrates the total loss to become the total heat quantity Q (J)
- the feedback side integrates the heat release amount Qf 'of the unit time to become the total heat release amount Qf (J). Even in this case, the motor frame temperature rise value Tc0 and the temperature rise value Tc1 of the primary winding of the motor are the same as in FIG.
- FIG. 25 is an explanatory diagram for detecting the ambient temperature of the motor with a temperature sensor and performing overload protection of the motor.
- 1a is a motor
- 48 is a motor drive power converter.
- the ambient temperature of the motor is detected by the temperature sensor of the ambient temperature measurement thermistor 74, and is taken in from the analog input terminal of the motor drive power conversion device 48 through the sensor cable 75.
- the control circuit power supply 51 is turned on to the motor drive power converter 48, and the motor drive power converter 48 presets the motor ambient temperature of 40 ° C. Thereafter, the main circuit power supply 50 is turned on, and the operation is started by the operation command from the host controller 52.
- the motor drive power conversion device 48 sets the initial value of the motor ambient temperature Ta to the upper limit 40 ° C. of the operating temperature range of the motor.
- the temperature rise value is (temperature rise allowable value) + (upper limit value of the motor operating temperature range).
- the ambient temperature of the motor detected by the overload protection determination circuit 76 is always known, so the new allowable temperature rise tolerance value is (temperature rise allowable value) + ⁇ (motor operating temperature Upper limit of range)-(Ambient temperature of detected motor) ⁇ , and when ambient temperature of detected motor is lower than upper limit of working temperature range of motor, upper limit of primary winding temperature of motor is It can be increased by the difference.
- the motor when the ambient temperature of the motor is higher than the upper limit value of the working temperature range of the motor, the motor may be burnt in the past, but since the threshold value is lowered, the motor is not burned. As a result, more accurate overload protection can be realized, and the user can use the overload protection as the specification according to the performance.
- the iron loss, the mechanical loss, etc. that are not caused by the motor current, the iron plate thickness t, the frequency f, the maximum magnetic flux density Bm, and the resistance of the magnetic body
- inverter gate 68 ... addition point (command-feedback), 69 ... addition point (motor frame temperature rise value-ambient temperature), 70 ... integration element Transfer function of motor frame heating part, 71 ... Transfer function of motor frame heat sink, 72 ... Ratio of primary side loss to total loss Ploss of motor, 73 ... Transfer function of motor primary winding including integral element, 74 ... Ambient temperature measurement thermistor, 75 ... sensor cable, 76 ... overload protection judgment circuit
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Abstract
Description
鉄損のヒステリシス損と渦電流損については、従来からスタインメッツの実験式として知られており、ヒステリシス損Phは、下記(数1)の関係となり、過電流損Peは、下記(数2)の関係となる。
本発明の他の課題や効果は以下の記載から明らかになる。
図1Aにモータ駆動電力変換システムでのモータ1aの損失を説明する図を示す。1aは、交流モータである。交流電源から供給された電源を順変換器2aで整流し、平滑コンデンサ3により平滑して直流に変換する。次に、直流電源から逆変換器4により再び交流に変換し、モータ1aのトルク、回転速度を制御しながらモータ1aを駆動する。なお、逆変換器4はスイッチング素子5およびフライホイルダイオード6で構成される。モータ1aの出力Poutは回転速度Nf、トルクTとし、これらはモータ出力軸に動力として負荷に与えられその機械を駆動する。モータ出力Poutの単位はワット(W)として示される。一方入力電力Pinはモータ駆動装置から各相電圧V、電流Iと、相電圧Vと電流Iの位相差である力率cosφで与えられ、3相電力として単位はワット(W)で示される。入力電力と出力電力の差は全損失になり、銅損、鉄損、漂遊負荷損、機械損などを含む。これらを含む全損失がモータの発熱や音に変わり周辺に放出される。なお、図中の矢印の幅は、電力の大きさの程度を表し、定常状態ではモータ1aが入力電力Pinを得て、モータ出力Poutを出力するので、入力電力Pinが大きくモータ出力Poutは小さくなり、小さくなった分は損失Plossとなる。
なお、このとき損失Plossの矢印の方向は、図1aと同一方向で損失する方向であり、矢印の方向が逆(エネルギーが生み出される)方向になることはあり得ない。
図10は、永久磁石形同期モータ1相分の等価回路を説明する図である。永久磁石形同期モータは回転すると発電機になるため誘起電圧E0を発生する。モータに流れる電流をIqfとして電流が流れると、モータ巻線の抵抗RaにはRa・Iqfの電圧降下が生じ、また、インダクタンスLaにはjω・La・Iqfのリアクタンス降下が発生する。これをベクトル図に表したものが図11と図12である。図11は永久磁石形同期モータの力行時のベクトル図で、図12は永久磁石形同期モータの回生時のベクトル図である。モータ入力の相電圧、電流の位相角φは図11、図12で表わされ、力行時は0<φ<90°となり、cosφは正の値となる。回生時のφは90°<φ<180°となり、cosφは負の値となる。
全損失演算・積算回路23については、図4Aにおいても図3Aと同様のため説明は省略する。
図6Aの動作は図4Aと同様に扱うことができ、誘導形センサレスベクトル制御モータ17bが駆動できる。モータの過負荷保護は、全損失演算・積算回路23の動作により保護することができる。
なお、図1は力行状態の入力Pin、出力Pout、全損失PLOSSを太矢印で示し、入力Pinが最も太く、出力Poutが細く、矢印が細くなった分、全損失PLOSSの太さになっていることを表している。
モータの使用環境における使用温度の上限は一般的には40℃である。またモータは耐熱クラスにより最高許容温度が規格で決められており、次のとおりである。
耐熱クラス 最高許容温度(℃)
120(E) 120
130(B) 130
155(F) 155
180(H) 180
モータの温度上昇限度ΔTmaxは(耐熱クラスの最高許容温度)-(モータ使用温度の上限値40℃)-Tsとしており、Tsは巻線温度を抵抗法で測定する場合、巻線を絶縁する絶縁物が許容最高温度の最高点を対称にしているが、温度上昇を抵抗法により測定する場合は、平均温度上昇値を測定するものであリ、その差5~15℃を考慮している。
全損失Ploss=400(%)で電子サーマル動作時間がt(trip)秒でトリップさせるには、図17の2)に傾斜aの直線y=axが描かれている。Δtは電子サーマルを演算するサンプリング時間、Δyは1回のサンプリング時間(s)で加減算する重み値である。電子サーマル積算カウンタ値のmax値をKfとする。ここで(数8)と直線y=ax=Kfより1回のサンプリング時間(s)に加減算する重み値Δyを求める。傾きa=(Δy/Δt)とし、tに上述の(数9)を代入すると、下記(数10)となり、このうちΔyは(数11)で示される。
耐熱クラス 規格による最高許容温度(℃) 温度上昇許容値ΔTmax(K)
120(E) 120 75
130(B) 130 80
155(F) 155 105
180(H) 180 125
図20の時間t=0はモータの使用環境における使用温度の上限値として40℃からスタートし、モータの各耐熱クラスにより温度上昇許容値ΔTmaxに達すると、過負荷と判定しモータを停止させて保護する。電子的な全損失時間積算カウンタ動作に当てはめると、制御電源投入時に積算カウンタを40℃にプリセットしてスターとする。温度上昇許容値ΔTmaxは過負荷と判定する閾値に相当し、積算カウンタは6,000,000(digit)に達したときである。
なお、両者を比較するコンパレータ66の出力が一致し“L”レベルを出力すると、67のインバータゲートを通り、OL信号として保護処理回路24に入力され、モータが過負荷と判定され、モータの運転を停止してモータを保護する。
モータの全熱量Q(J)は全損失Plossを時間積分し(数12)で表される。
モータ表面の冷却リブ(個体)から大気(流体)との間の対流による熱伝達には、自由対流と強制対流があり、いずれの場合も熱伝達は(数16)の様になる。
過負荷保護判定回路76では、モータの周囲温度Taが入力され、初期値はモータの使用温度の上限値40℃が設定される。モータの周囲温度を検出しない場合、実際のモータの周囲温度にかかわらず制御上は40℃として制御され、過負荷と判定される閾値と比較し、瞬時過負荷でも保護できる構成とした。なお、伝達関数72のk1はモータの回転子が永久磁石のPMモータでは二次側銅損がないとしてk1=1とすることができる。
Claims (11)
- モータの過負荷保護用電子サーマル機能を備えたモータ電力変換装置において、
モータの全損失時間積一定で動作し、モータの巻線温度を模擬した積算値を出力して、
前記積算値が所定の閾値に達した時、モータの運転を停止する信号を出力する全損失時間積算カウンタを有するモータ電力変換装置。 - 請求項1に記載のモータ電力変換装置において、
前記全損失時間積算カウンタが、前記モータ電力変換装置の逆変換器の損失を含むモータの全損失時間積一定で動作するものであるモータ電力変換装置。 - 請求項1に記載のモータ電力変換装置において、
前記全損失時間積算カウンタが、モータの全損失を、モータの入力電力からモータの出力電力を差し引いて求めるものであるモータ電力変換システム。 - 請求項2に記載のモータ電力変換装置において、
全損失時間積算カウンタが、前記逆変換器の損失を含むモータの全損失を、モータ電力変換装置の順変換器と逆変換器の中間電位の入力電力からモータの出力電力を差し引いて求めるものであるモータ電力変換装置。 - 請求項3又は4に記載のモータ電力変換装置において、
前記全損失時間積算カウンタが、更に、x軸が全損失軸、y軸が全損失=100%軸で直交する2本の漸近線に挟まれる全損失と、時間積一定の反比例曲線とで、漸近線の交点を点対称とする2つの曲線の内、一方の曲線とを積算カウンタの加算、他方の曲線を積算カウンタの減算とするモータ電力変換装置。 - 請求項3又は4に記載のモータ電力変換装置において、
前記全損失時間積算カウンタは、全損失0%以上で常時動作するものであり、
更に前記モータ電力変換装置は、常時動作する減算カウンタを有し、
該減算カウンタが、加算時に全損失時間積算カウンタに入力された関数を極性反転し、一定時間ディレー動作するむだ時間要素を持ち、減算する最大傾斜率を全損失=100%で加算した時の傾斜率を最大の減算傾斜率として減算時にのみ制限を加え、
前記全損失時間積算カウンタが、温度上昇許容値に達した時にモータの運転を停止する信号を出力するモータ電力変換装置。 - 請求項1又は2において、
前記全損失時間積算カウンタが、モータ使用温度範囲の上限温度を前記モータの巻線温度の初期値として制御電源投入時に設定されるものであり、
該モータ使用温度範囲の上限温度を、モータの巻線温度の初期値からモータの耐熱クラスの最高許容温度近傍未満までの温度上昇限度値に達した時に過負荷と判定し、モータの運転を停止する信号を出力するモータ電力変換装置。 - 請求項7において、
前記全損失時間積算カウンタは、前記モータの運転開始前に、モータ巻線温度の入力を外部から受けるものであり、
該モータ巻線温度の入力に応じて、(温度上昇許容値)+{(モータ使用温度範囲の上限値)-(運転開始前のモータの巻線温度)}を新たな温度上昇許容値とし、
該新たな温度上昇許容値に達した時にモータの運転を停止する信号を出力するものであるモータ電力変換装置。 - 請求項7に記載のモータ電力変換装置において、前記全損失時間積算カウンタが、モータの周囲温度の入力を常時外部から受けるものであり、
該周囲温度の入力に応じて、(温度上昇許容値)+{(モータ使用温度範囲の上限値)-(検出したモータの周囲温度)}を新たな温度上昇許容値とし、該新たな温度上昇許容値に達した時にモータの運転を停止する信号を出力するものであるモータ電力変換装置。 - モータの過負荷保護用電子サーマル機能を備えたモータ電力変換装置において、
交流モータの全損失をモータの熱量の基となる物理量として検出し、モータの全損失を指令とし、モータの単位時間当たりの放熱量を帰還量とし、指令と帰還量の差を偏差として積算し、その積算値をモータの内部発熱量とする前向きループとモータの単位時間当たりの放熱量を負帰還ループとした負帰還フィードバックの熱モデルを構成し、前記負帰還フィードバックの偏差を分岐し、モータの一次側損失/全損失の比率を分岐した偏差に乗じ、比率を乗じた偏差に(モータの一次巻線の質量)×(モータの一次巻線の比熱)で除算し、その値を時間毎加算による累積積算することで、モータの一次巻線の温度上昇値として算出し、前記モータの一次巻線温度上昇値が過負荷と判定する閾値に達した時、モータの運転を停止するものであるモータ電力変換装置。 - 請求項9に記載のモータ電力変換装置において、
前記負帰還フィードバックによる熱モデルが、交流モータの全損失をモータの熱量の基となる物理量として検出し、モータの全損失を指令、モータの単位時間当たりの放熱量を帰還量とし、指令と帰還量の差を偏差として積算し、
前記偏差の積算値を(モータ質量)×(モータの比熱)で除算し、
モータ枠の温度上昇値を制御量とし、前記モータ枠の温度上昇値からモータの周囲温度を減算し、
前記減算値に(モータの熱伝達係数)×(モータの表面積)を乗じることによりモータの単位時間当たりの放熱量を帰還量とする負帰還フィードバックループであるモータ電力変換装置。
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