WO2011070952A1 - Dispositif de transmission - Google Patents

Dispositif de transmission Download PDF

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Publication number
WO2011070952A1
WO2011070952A1 PCT/JP2010/071459 JP2010071459W WO2011070952A1 WO 2011070952 A1 WO2011070952 A1 WO 2011070952A1 JP 2010071459 W JP2010071459 W JP 2010071459W WO 2011070952 A1 WO2011070952 A1 WO 2011070952A1
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WIPO (PCT)
Prior art keywords
signal
pulse
modulation
amplitude
modulation signal
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PCT/JP2010/071459
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English (en)
Japanese (ja)
Inventor
和明 國弘
真一 堀
一実 椎熊
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日本電気株式会社
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Application filed by 日本電気株式会社 filed Critical 日本電気株式会社
Priority to US13/514,568 priority Critical patent/US8693578B2/en
Priority to JP2011545181A priority patent/JP5609890B2/ja
Publication of WO2011070952A1 publication Critical patent/WO2011070952A1/fr

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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
    • H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
    • H03F1/0288—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers using a main and one or several auxiliary peaking amplifiers whereby the load is connected to the main amplifier using an impedance inverter, e.g. Doherty amplifiers
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/32—Modifications of amplifiers to reduce non-linear distortion
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
    • H03F3/21—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only
    • H03F3/217—Class D power amplifiers; Switching amplifiers
    • H03F3/2173—Class D power amplifiers; Switching amplifiers of the bridge type
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
    • H03F3/24—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers of transmitter output stages

Definitions

  • the present invention relates to a transmission apparatus having a plurality of amplifiers.
  • modulation schemes such as QPSK (Quadrature Phase Shift Keying) and multi-level QAM (Quadrature Amplitude Modulation) are adopted.
  • a modulation signal having a large PAPR Peak-to-Average Power Ratio
  • PAPR Peak-to-Average Power Ratio
  • next-generation mobile phones wireless LANs, digital television broadcasts, and the like
  • OFDM orthogonal frequency division multiplexing
  • a Doherty-type amplifying device has been devised as an amplifying device that realizes high power efficiency even in an operation region with a large back-off.
  • FIG. 1 is a block diagram showing a configuration example of the Doherty amplification device 820.
  • the amplifier 822 has an input terminal connected to the power distributor 821 via the signal line 812 and an output terminal connected to the quarter wavelength transmission line 823.
  • One end of the transmission line 824 is connected to the power distributor 821 via the signal line 813, and the other end is connected to the amplifier 825.
  • the other end of the quarter wavelength transmission line 823 is connected to the amplifier 825 and the load resistor 826.
  • the input terminal 811 receives the modulation signal 891.
  • the power distributor 821 distributes the power of the modulation signal 891 from the input terminal 811 into two.
  • the power distributor 821 distributes the modulation signal 891, supplies one of the distributed modulation signals to the amplification unit 822 via the signal line 812, and supplies the other modulation signal via the signal line 813. Supply to transmission line 824.
  • the amplifier 822 is a main amplifier biased to class B.
  • the quarter wavelength transmission lines 823 and 824 are quarter wavelength impedance transformers having a characteristic impedance Z 0 .
  • the amplifier 825 is a peak amplifier biased to class C.
  • Load resistor 826 has a load impedance Z 0/2.
  • FIG. 2 is a diagram showing ideal power efficiency characteristics of the Doherty amplification device 820.
  • FIG. 2 shows a power efficiency characteristic 801 represented by a solid line and a probability density characteristic 809 represented by a dotted line.
  • the power efficiency characteristic 801 indicates the relationship between the normalized amplitude standardized based on the maximum amplitude of the modulation signal and the power efficiency of the Doherty amplification device 820.
  • the probability density characteristic 809 is an amplitude distribution of a modulation signal in typical wireless communication, and is a probability density characteristic based on a Rayleigh distribution having a peak at 8 dB backoff.
  • the amplifier 822 In the power efficiency characteristic 801, in the Doherty amplifier 820, only the amplifier 822 operates when the normalized amplitude is “0.5” or less. In this case, the amplifier 822 has a maximum power efficiency of 78.5% when the normalized amplitude is “0.5”. At this time, the load impedance when the load resistor 826 side is viewed from the output terminal of the amplifier 822 becomes “2Z 0 ” due to the impedance conversion characteristic of the 1 ⁇ 4 wavelength transmission line 823.
  • the output power P1 / 2 of the Doherty amplifier 820 when the normalized amplitude is “0.5” can be expressed by the following equation. Note that V DD is the power supply voltage of the amplifier 822, and Pmax is V DD 2 / (2Z 0 ).
  • the load impedance when the load resistance 826 is viewed from the output terminal of the amplifier 822 changes from “2Z 0 ” to “Z 0 ” due to the impedance conversion characteristic of the quarter wavelength transmission line 823.
  • the output power of both the amplifiers 822 and 825 when the normalized amplitude is “1.0” is the maximum Pmax, and the efficiency is also maximum. Therefore, the output power of the Doherty amplifier 820 when the normalized amplitude is “1.0” is 2Pmax.
  • the overall power efficiency of the Doherty amplification device 820 is 78.5% because both the amplifiers 822 and 825 operate at the saturation level.
  • the average power efficiency weighted based on the probability density characteristic 809 is 64%.
  • a class D amplifying device can be cited as another amplifying device that achieves high power efficiency in an operation region with a large back-off.
  • FIG. 3 is a diagram illustrating a configuration example of a voltage mode class D amplifier.
  • FIG. 3 shows a class D amplifier 830 and an output filter 840.
  • the switching element 832 has a control terminal connected to the output terminal of the inverter 831, one end connected to the power supply voltage V DD , and the other end connected to one end of the switching element 833 and the input terminal of the output filter 840. It is connected to the.
  • the switching element 833 has its control terminal connected to the input terminal 814 and the other end grounded.
  • the inverter 831 inverts a pulse signal that is a modulation signal.
  • Switching elements 832 and 833 switch connection / non-connection.
  • the switching elements 832 and 833 are realized by, for example, field effect transistors.
  • the output filter 840 removes the rectangular wave component of the modulation signal amplified by the class D amplifier 830.
  • the output filter 840 includes an inductor 841 and a capacitor 842 connected in series.
  • the switching element 833 is supplied with the input pulse signal 893 input to the input terminal 814, and the switching element 832 is supplied with the input pulse signal 893 inverted by the inverter 831. . Therefore, switching elements 832 and 833 operate in opposite phases.
  • switching elements 832 and 833 for example, when the switching element 832 is in a conductive (ON) state and a current flows through the switching element 832, no voltage is generated across the switching element 832. Conversely, when the switching element 832 is in a non-conduction (off) state and a voltage is generated across the switching element 832, no current flows through the switching element 832 itself.
  • the operation of the switching element 833 is the same.
  • the class D amplifier 830 can amplify the input pulse signal with ideally 100% power efficiency. Then, the original signal 894 is reproduced by removing the rectangular wave component by the output filter 840.
  • the input signal level supplied to the input terminal 814 of the class D amplifying device needs to be a binary (1 bit) pulse train signal of ON and OFF. .
  • a binary (1 bit) pulse train signal of ON and OFF.
  • FIG. 4 is a diagram illustrating a configuration example of a transmission device 850 using a class D amplification device.
  • the transmission device 850 includes a signal modulation unit 860, a class D amplifier 830, an output filter 840, and an antenna 856.
  • the class D amplifier 830 and the output filter 840 are the same as those shown in FIG.
  • the signal modulation unit 860 includes a signal generation unit 861, a polar coordinate conversion unit 862, a delta-sigma modulator 863, a frequency conversion unit 864, an integration unit 865, and a frequency oscillation unit 869.
  • the signal generator 861 converts the input signal into an I signal and a Q signal expressed by an I (in-phase) component and a Q (quadrature) component that are orthogonal to each other based on data to be transmitted.
  • the polar coordinate conversion unit 862 generates an amplitude component and a phase component of the input signal based on the I component and the Q component converted by the signal generation unit 861.
  • the delta-sigma modulator 863 converts the amplitude component from the polar coordinate conversion unit 862 into a pulse modulation signal that is a 1-bit (pulse) signal.
  • the frequency conversion unit 864 multiplies the carrier wave signal generated by the frequency oscillation unit 869 by the phase signal from the polar coordinate conversion unit 862.
  • the integrating unit 865 integrates the phase modulation signal from the frequency conversion unit 864 and the pulse modulation signal from the delta-sigma modulator 863. As a result, the accumulating unit 865 generates a modulation signal 854 in which the phase modulation signal 853 is on / off controlled by the output pulse modulation signal 852 of the delta sigma modulator 863.
  • the class D amplifier 830 Upon receiving the modulation signal 854, the class D amplifier 830 amplifies the modulation signal 854 with the ideal efficiency of the class D amplifier 100% while the pulse modulation signal 852 is on, and supplies power while the pulse modulation signal 852 is off. Do not consume. Therefore, the class D amplifier 830 ideally amplifies the modulation signal 854 with 100% efficiency.
  • the output filter 840 removes the switching component of the modulation signal amplified by the class D amplifier 830, and outputs the output signal 855, which is the original signal amplified with high efficiency, via the antenna 856.
  • Non-Patent Document 1 discloses a transmission device that performs delta-sigma modulation on both the I component and the Q component.
  • an example of the transmission device described in Non-Patent Document 1 will be briefly described with reference to the drawings.
  • FIG. 5 is a block diagram illustrating a configuration example of a transmission apparatus 870 that performs delta-sigma modulation on the I component and the Q component.
  • the transmission device 870 includes a signal modulation unit 880, a class D amplifier 830, an output filter 840, and an antenna 856.
  • the class D amplifier 830, the output filter 840, and the antenna 856 are the same as those shown in FIG.
  • the signal modulation unit 880 includes delta-sigma modulators 881 and 884, accumulators 882 and 886, a clock signal generator 883, a delay unit 885, and a modulation signal generation unit 887.
  • the I and Q signals orthogonal to each other are supplied to the input terminals 816 and 817, respectively.
  • the delta sigma modulators 881 and 884 respectively generate pulse signal trains 871 and 872 that are 1-bit signals by performing delta sigma modulation on the signals from the input terminals 816 and 817, respectively.
  • the clock signal generator 883 generates a clock signal having a frequency four times the carrier frequency.
  • the clock signal generator 883 generates a ternary clock signal whose amplitude levels are repeated in the order of “1”, “0”, “ ⁇ 1”, “0”. That is, the clock signal generator 883 generates a clock signal whose value repeatedly changes in the order of a (a is a positive number), 0, ⁇ a, 0.
  • the clock signal generator 883 supplies the generated clock signal to the accumulator 882 and the delay unit 885.
  • the delay unit 885 delays the clock signal from the clock signal generator 883 by one clock.
  • the accumulator 882 integrates the clock signal from the clock signal generator 883 with the pulse signal string 871 that is a 1-bit signal output from the delta-sigma modulator 881.
  • the accumulator 886 integrates the clock signal delayed by one clock from the delay unit 885 into the pulse signal sequence 872 which is a 1-bit signal output from the delta sigma modulator 884. Thereby, the orthogonal relationship between the I signal and the Q signal is maintained.
  • Modulation signal generation unit 887 adds signals from integrators 882 and 886. Accordingly, the signal modulation unit 880 converts the pulse signal sequence 873 in which the I signal and the Q signal are superimposed on the clock signal in the order of “I”, “Q”, “ ⁇ I”, and “ ⁇ Q”, to the modulation signal Can be generated as
  • the transmission devices 850 and 870 can amplify the modulation signal with high power efficiency in the class D amplifier 830 by generating the pulse signal sequence by the delta-sigma modulator.
  • Patent Document 1 describes a transmission device that changes the pulse height of a pulse modulation signal. This transmission apparatus reduces quantization noise generated by performing delta-sigma modulation.
  • the transmission device described in Patent Document 1 includes an amplitude calculation unit, a division unit, a delta-sigma modulation unit, a variable gain amplification unit, and an amplitude amplification unit.
  • the amplitude calculation unit outputs a plurality of discrete value signals according to the magnitude of the amplitude signal that is the amplitude component of the input signal.
  • the division unit outputs an amplitude signal obtained by dividing the amplitude signal by the discrete value signal.
  • the delta sigma modulation unit performs delta sigma modulation on the amplitude signal.
  • the variable gain amplification unit amplifies the output signal from the delta sigma modulation unit with a gain corresponding to the discrete value signal.
  • the amplitude amplifying unit supplies a voltage corresponding to the magnitude of the amplified output signal to the amplitude modulating unit.
  • the amplitude amplifying unit is a class D amplifier configured by a switching regulator and a switch regulator, for example.
  • the transmission device described in Patent Document 1 can reduce quantization noise because the delta-sigma modulation unit operates near the saturation level even when the amplitude signal is small.
  • switching loss a fixed power loss due to the on / off switching of the class D amplifier 830 or the like occurs. For this reason, as the amplitude of the input signal decreases, the ratio of the switching loss to the output power of the class D amplifier 830 increases. For this reason, when an input signal having a small amplitude is amplified, there is a problem that power efficiency is lowered.
  • the amplitude amplification unit is configured by a class D amplifier. Then, there existed a problem that power efficiency fell.
  • An object of the present invention is to provide a transmission apparatus that solves the above-described problems.
  • the transmission device of the present invention is a transmission device that amplifies and transmits an input signal including an amplitude component and a phase component, and changes a pulse width or a pulse density according to the magnitude of the amplitude component of the input signal.
  • pulse modulation signal generation means for generating a pulse modulation signal by discretely changing the height of the pulse according to the magnitude of the amplitude component of the input signal, and the phase of the pulse modulation signal and the input signal
  • a modulation signal generating means for generating a modulation signal whose amplitude level is discretely changed according to the pulse height of the pulse modulation signal by integrating the components; and the number of discrete amplitude levels of the modulation signal
  • the number of operation amplifying means for amplifying the modulation signal among the amplification means increases as the amplitude level of the modulation signal increases, and the operation amplification Including a power amplifying means for outputting the synthesized output of the stage, and a filter means for removing a square wave component from
  • a transmission device is a transmission device that amplifies and transmits an input signal that includes an I component and a Q component that are orthogonal to each other, and in which an amplitude component is defined by the I component and the Q component.
  • a pulse modulation signal of I component is generated by changing the height of the pulse discretely according to the magnitude of the amplitude component of the input signal while changing the pulse width or pulse density according to the amplitude.
  • Pulse modulation signal generation means for generating a pulse modulation signal; clock signal generation means for generating a clock signal whose amplitude level repeatedly changes in the order of a (a is a positive number), 0, -a, 0; A first integrated signal is generated by integrating the clock signal and the pulse modulation signal of the I component, and a second signal is integrated by integrating the signal obtained by delaying the clock signal by one clock and the pulse modulation signal of the Q component.
  • the amplitude level is discrete according to the pulse height of the pulse modulation signal of the I component and the Q component.
  • a plurality of amplifying means including a modulation signal generating means for generating a modulation signal that changes in a stepwise manner and a number of amplifying means that receive the modulation signal as input and that are equal to or greater than the number of discrete amplitude levels of the modulation signal.
  • the number of operation amplification means for amplifying the modulation signal increases as the amplitude level of the modulation signal increases, and power amplification means for synthesizing and outputting the output of the operation amplification means, Including.
  • FIG. 3 is a block diagram illustrating a configuration example of a Doherty amplifier 820.
  • FIG. 6 is a diagram illustrating power efficiency characteristics of the Doherty amplifier 820.
  • FIG. It is a block diagram which shows the example of 1 structure of a class D amplifier.
  • 10 is a block diagram illustrating a configuration example of a transmission device 850.
  • FIG. 10 is a block diagram illustrating a configuration example of a transmission device 870.
  • 5 is a diagram illustrating an example of an amplitude signal supplied to an amplitude modulation unit 230.
  • FIG. It is a figure which shows the pulse modulation signal produced
  • FIG. 3 is a block diagram illustrating a configuration example of an amplitude modulation unit 230.
  • FIG. 6 is a diagram illustrating a waveform of a ternary pulse modulation signal generated by an amplitude modulation unit 230.
  • FIG. 3 is a diagram illustrating power efficiency characteristics of a transmission device 100. It is a block diagram which shows the structural example of the signal modulation part 600 as a modification of 1st Embodiment. It is a figure which shows an example of the amplitude signal output from the amplitude calculation part 620.
  • FIG. 3 is a diagram illustrating power efficiency characteristics of a transmission device 100. It is a block diagram which shows the structural example of the signal modulation part 600 as a modification of 1st Embodiment. It is a figure which shows an example of the amplitude signal output from the amplitude calculation part 620.
  • FIG. 6 is a diagram illustrating a modulation signal generated by a modulation signal generation unit 690.
  • FIG. It is a block diagram which shows the structural example of the transmitter 110 in 2nd Embodiment.
  • 5 is a diagram illustrating an example of an amplitude signal supplied to an amplitude modulation unit 230.
  • FIG. 6 is a diagram illustrating power efficiency characteristics of a transmission device 110.
  • FIG. It is a block diagram which shows the structural example of the transmitter 120 in 3rd Embodiment. It is a block diagram which shows the structural example of the transmitter 130 in 4th Embodiment. 6 is a diagram illustrating an example of a modulation signal supplied to an amplifier 731.
  • FIG. 6 is a diagram illustrating an example of a modulation signal supplied to an amplifier 732.
  • FIG. 6 is a block diagram illustrating a configuration example of the transmission device according to the first embodiment of the present invention.
  • the transmission device 100 is a transmission device that amplifies and transmits an input signal including an amplitude component and a phase component.
  • the transmission apparatus 100 includes a signal modulation unit 200, a power amplification unit 300, an output filter 410, and an antenna 420.
  • the signal modulation unit 200 integrates a pulse modulation signal in which the magnitude of the amplitude component of the input signal is represented by the pulse width or pulse density and the height of a plurality of discrete pulses, and the phase component of the input signal. By doing so, a modulated signal is generated.
  • the signal modulation unit 200 includes a pulse modulation signal generation unit 201 and a modulation signal generation unit 202.
  • the pulse modulation signal generation unit 201 includes a signal generation unit 210, a polar coordinate conversion unit 220, and an amplitude modulation unit 230.
  • the modulation signal generation unit 202 includes a frequency conversion unit 240, an integration unit 250, and a frequency oscillation unit 290.
  • the pulse modulation signal generation unit 201 changes the pulse height or the pulse density according to the magnitude of the amplitude component of the input signal while changing the pulse width or the pulse density according to the magnitude of the amplitude component of the input signal. It is a pulse modulation signal generation means for generating a pulse modulation signal by changing to.
  • This pulse modulation signal is a pulse signal in which the pulse width or pulse density changes, and the pulse height is N (N is N) where the amplitude of the pulse is zero (predetermined value) and a value greater than zero. It is a pulse signal having (an integer greater than or equal to 2) amplitude levels (hereinafter referred to as “saturation level”).
  • the signal generator 210 generates an input signal based on data to be transmitted.
  • This input signal is a digital baseband signal and is a signal expressed by an I (in-phase) component and a Q (quadrature) component that are orthogonal to each other. Further, the signal generation unit 210 supplies the I component and the Q component of the generated input signal to the polar coordinate conversion unit 220 via the signal lines 218 and 219, respectively.
  • the polar coordinate conversion unit 220 calculates the amplitude component and the phase component of the input signal based on the I component and the Q component from the signal generation unit 210.
  • the polar coordinate conversion unit 220 calculates the amplitude component r and the phase component ⁇ based on the following equation, for example.
  • the polar coordinate conversion unit 220 supplies the calculated amplitude component as an amplitude signal to the amplitude modulation unit 230 via the signal line 229. At the same time, the polar coordinate conversion unit 220 supplies the calculated phase component to the frequency conversion unit 240 as a phase signal.
  • the amplitude modulation unit 230 converts the amplitude signal into a pulse modulation signal.
  • the amplitude modulation unit 230 changes the pulse width or the pulse density according to the magnitude of the amplitude signal, and discretely changes the pulse height according to the magnitude of the amplitude signal. Generate a signal.
  • the amplitude modulation unit 230 has a pulse height corresponding to the magnitude of the amplitude signal from the polar coordinate conversion unit 220 out of the predetermined N pulse heights (excluding zero), and the pulse width or The pulse density is modulated according to the magnitude of the amplitude signal.
  • the amplitude modulation unit 230 has a saturation level determined based on a predetermined N ⁇ 1 amplitude threshold value and the magnitude of the amplitude signal from the polar coordinate conversion unit 220, and delta-sigma modulation (pulse pulse) is applied to the amplitude signal. Density modulation) processing or pulse width modulation processing is performed.
  • the amplitude modulation unit 230 when the maximum height of the output pulse of the amplitude modulation unit 230 is normalized to “1.0”, the amplitude modulation unit 230 has “0.0”, “0.5”, and A pulse modulation signal having an amplitude level (pulse height) of “1.0” is generated based on the magnitude of the amplitude signal.
  • the amplitude modulation unit 230 standardizes the amplitude signal by setting the maximum value of the amplitude signal to “1.0”, the normalized amplitude (hereinafter referred to as “normalized amplitude”), and “0.5”. Is compared with the amplitude threshold value set in (1). When the normalized amplitude is “0.5” or less, the amplitude modulation unit 230 sets the saturation level of the amplitude modulation unit 230 to “0.5” and the normalized amplitude exceeds “0.5”. In this case, the saturation level of the amplitude modulation unit 230 is set to “1.0”.
  • the amplitude modulation unit 230 generates a pulse modulation signal having binary saturation levels of “0.5” and “1.0”.
  • the amplitude modulation unit 230 supplies the generated pulse modulation signal to the integration unit 250 via the signal line 239.
  • an example of the pulse modulation signal generated based on the amplitude signal by the amplitude modulation unit 230 is shown in FIG.
  • FIG. 7 a is a diagram illustrating an example of an amplitude signal supplied to the signal line 229.
  • FIG. 7b is a diagram illustrating an example of a pulse modulation signal generated based on the amplitude signal illustrated in FIG. 7a.
  • the horizontal axis is the time axis
  • the vertical axis is the amplitude.
  • the modulation signal generation unit 202 is a modulation signal generation unit that generates a modulation signal based on the pulse modulation signal supplied from the pulse modulation signal generation unit 201 and the phase component supplied from the polar coordinate conversion unit 220.
  • Modulation signal generation section 202 integrates the pulse modulation signal and the phase component to generate a modulation signal whose amplitude level changes discretely according to the pulse height of the pulse modulation signal.
  • the frequency conversion unit 240 is a multiplier that multiplies the carrier signal generated by the frequency oscillation unit 290 by the phase signal from the polar coordinate conversion unit 220. Thereby, the frequency converter 240 generates a phase modulation signal in which the frequency of the carrier signal is added (up-converted) to the frequency component of the phase signal.
  • the frequency conversion unit 240 supplies the generated phase modulation signal to the integration unit 250 via the signal line 249.
  • the integrating unit 250 integrates the phase modulation signal from the frequency conversion unit 240 and the pulse modulation signal from the amplitude modulation unit 230. Thereby, the integration unit 250 generates a modulation signal whose amplitude level changes discretely according to the pulse height of the pulse modulation signal.
  • This modulation signal is a burst signal in which the phase modulation signal is on / off controlled with a pulse modulation signal having a binary saturation level (pulse height), and has a binary discrete amplitude level.
  • FIG. 7 shows an example of the modulation signal generated by the integrating unit 250 based on the pulse modulation signal and the phase modulation signal.
  • FIG. 7 c is a diagram illustrating an example of the phase modulation signal supplied from the signal line 249.
  • FIG. 7d is a diagram illustrating an example of a modulation signal generated by the integrating unit 250 based on the pulse modulation signal and the phase modulation signal shown in FIGS. 7b and 7c, respectively.
  • the modulation signal is indicated by a solid line
  • the envelope of the modulation signal is indicated by a dotted line.
  • the horizontal axis is the time axis
  • the vertical axis is the amplitude.
  • the power amplification unit 300 is a power amplification unit that amplifies the modulation signal generated by the modulation signal generation unit 202.
  • the power amplifying unit 300 includes amplifiers (amplifiers 320 and 350) having the number of discrete amplitude levels of the modulation signal, that is, the number of saturation levels of the pulse modulation signal.
  • the number of amplifiers that amplify the modulation signal among the amplifiers 320 and 350 increases as the amplitude level of the modulation signal becomes higher.
  • the output of the amplifier is synthesized and output.
  • the operational amplifier can be generally referred to as operational amplification means.
  • one operational amplifier (amplifier 320) operates.
  • the power amplification unit 300 receives a modulation signal having an amplitude level corresponding to the pulse height “1.0” of the pulse modulation signal
  • the two operational amplifiers (amplifiers 320 and 350) operate to operate the power amplification unit. 300 synthesizes and outputs these outputs.
  • the power amplifying unit 300 includes a power distributor 310 and quarter wavelength transmission lines 330 and 340 in addition to the amplifiers 320 and 350.
  • the amplifier 320 has an input terminal connected to the power distributor 310 via the signal line 318 and an output terminal connected to the quarter wavelength transmission line 330.
  • the quarter wavelength transmission line 340 has one end connected to the power distributor 310 via the signal line 319 and the other end connected to the amplifier 350.
  • the other end of the quarter wavelength transmission line 330 is connected to the amplifier 350 and the combining unit 360.
  • the power amplifier 300 is a Doherty amplifier in which an amplifier 320 and a quarter wavelength transmission line 330, and a quarter wavelength transmission line 340 and an amplifier 350 are connected in parallel.
  • the power distributor 310 distributes the power of the modulation signal from the signal line 209 into two.
  • the power distributor 310 supplies one of the distributed modulation signals to the amplifying unit 320 via the signal line 318, and supplies the other modulation signal to the quarter wavelength transmission line 340 via the signal line 319. Supply.
  • the amplifier 320 is a main amplifier (or carrier amplifier) biased to class B.
  • the amplifier 320 is configured by a transistor as a switching element, for example, like the class D amplifier 830 shown in FIG.
  • the amplifier 320 is biased so as to operate when the modulation signal when the pulse height of the pulse modulation signal is “0.5” or more is supplied from the signal line 209. Furthermore, the amplifier 320 is set so that the power efficiency of the amplifier 320 is maximized when receiving a modulation signal when the pulse height of the pulse modulation signal is “0.5” or more.
  • the amplifier 320 amplifies the modulation signal when the pulse height of the pulse modulation signal is “0.5” or “1.0” with the maximum power efficiency.
  • the amplifier 320 operates on the modulation signal when the pulse height of the pulse modulation signal is “0.5” or “1.0” (on period), and the pulse height of the pulse modulation signal is “0”. .0 "does not operate on the modulated signal (off period).
  • a switching mode amplifier for example, a class D amplifier
  • a switching mode amplifier for example, a class D amplifier
  • the amplifier 320 outputs the amplified modulation signal to the output filter 410 via the quarter wavelength transmission line 330. It should be noted that amplifier 320 can be generally referred to as an amplifying means or an operational amplifying means.
  • Quarter-wave transmission line 330 is a quarter-wave impedance transformer having a characteristic impedance Z 0.
  • the quarter wavelength transmission line 330 outputs the modulation signal from the amplifier 320 to the output filter 410 via the synthesis unit 360.
  • Quarter-wave transmission line 340 is a quarter-wave impedance transformer having a characteristic impedance Z 0.
  • the quarter wavelength transmission line 340 outputs the modulation signal from the signal line 319 to the amplifier 350.
  • the amplifier 350 is a peak amplifier (peak amplifier) biased to class C.
  • the amplifier 350 is configured by, for example, a transistor that is a switching element.
  • the amplifier 350 is biased so as to operate when the modulation signal when the pulse height of the pulse modulation signal is “1.0” is supplied from the signal line 209. Furthermore, the amplifier 350 is set so that the power efficiency is maximized when receiving the modulation signal when the pulse height of the pulse modulation signal is “1.0”.
  • the amplifier 350 amplifies with the maximum power efficiency only when the modulation signal when the pulse height of the pulse modulation signal is “1.0” is received from the 1 ⁇ 4 wavelength transmission line 340.
  • the amplifier 350 operates on the modulation signal when the pulse height of the pulse modulation signal is “1.0”, and the pulse height of the pulse modulation signal is “0.0” or “0.5”. Does not operate on the modulated signal.
  • a switching mode amplifier may be used.
  • the amplifier 350 outputs the amplified modulated signal to the output filter 410 via the synthesis unit 360.
  • Amplifier 350 can be generally referred to as amplification means or operational amplification means.
  • the synthesizer 360 synthesizes the modulation signal from the quarter wavelength transmission line 330 and the modulation signal from the amplifier 350.
  • the output filter 410 removes a rectangular wave component from the output of the power amplifying unit 300 to output a modulation signal approximate to the waveform of the input signal to the antenna 420 as an output signal.
  • Output filter 410 can be generally referred to as filter means.
  • FIG. 7e is a diagram illustrating an example of the modulated signal from which the rectangular wave component has been removed by the output filter 410 after the modulated signal illustrated in FIG.
  • the modulation signal is indicated by a solid line
  • the envelope of the modulation signal corresponding to the waveform of the pulse modulation signal is indicated by a dotted line.
  • the waveform of the amplitude signal shown in FIG. 7a approximates the waveform of the envelope of the modulation signal shown by the dotted line in FIG. 7e.
  • the horizontal axis is the time axis
  • the vertical axis is the amplitude.
  • the antenna 420 converts an electric signal that is a modulation signal from the output filter 410 into a radio wave (electromagnetic wave).
  • FIG. 8 is a block diagram illustrating a configuration example of the amplitude modulation unit 230.
  • the amplitude modulation unit 230 includes a gain setting unit 231, gain multiplication units 232 and 233, and a delta-sigma modulator 260.
  • the delta sigma modulator 260 includes adders 261 and 263, integrators 262 and 264, a quantizer 265, a digital-to-analog converter (DAC) 266, and multipliers 267 and 268.
  • DAC digital-to-analog converter
  • the height of the pulse output from the delta sigma modulator 260 that is, the saturation level of the delta sigma modulator 260 is normalized to “1.0”.
  • the gain setting unit 231 Based on the magnitude of the amplitude signal from the signal line 229, the gain setting unit 231 sets one of N predetermined gain coefficients in the gain multiplication units 232 and 233. The gain setting unit 231 selects one of the N gain coefficients A based on the predetermined N ⁇ 1 amplitude thresholds. The gain setting unit 231 sets the selected gain coefficient A in the gain multiplication unit 232 and sets the inverse of the gain coefficient A ⁇ 1 in the gain multiplication unit 233.
  • the gain setting unit 231 normalizes the amplitude signal by setting the maximum level of the amplitude signal to “1.0”, and sets the normalized amplitude (hereinafter referred to as “normalized amplitude”) to “0.
  • the amplitude threshold value set to “5” is compared.
  • the gain setting unit 231 selects the gain coefficient A of “2.0” when the magnitude of the normalized amplitude is “0.5” or less.
  • gain setting section 231 sets “2.0” as gain multiplier 232 as the selected gain coefficient, and gain “0.5” as the reciprocal A ⁇ 1 of the gain coefficient.
  • the multiplier 233 sets the gain setting unit 231 processes the maximum amplitude signal of “0.5” supplied to the delta-sigma modulator 260 to “1.0” within the amplitude modulation unit 230, and then processes the gain.
  • the multiplication unit 233 sets the saturation level to “0.5”.
  • the gain setting unit 231 selects a gain coefficient of “1.0” when the magnitude of the normalized amplitude exceeds “0.5”. In this case, the gain setting unit 231 sets “1.0” as the selected gain coefficient A to the gain multiplication unit 232 and sets “1.0” as the reciprocal A ⁇ 1 of the gain coefficient.
  • the gain multiplier 233 is set.
  • the gain multiplication unit 232 multiplies the gain coefficient A set by the gain setting unit 231 by the amplitude signal from the signal line 229 to increase or decrease the magnitude of the amplitude signal.
  • the gain multiplier 232 is a first gain variable amplifying means for increasing the gain discretely as the amplitude component of the input signal decreases and amplifying the amplitude component of the input signal with the gain.
  • the gain multiplication unit 232 doubles the magnitude of the amplitude signal.
  • the gain multiplier 232 supplies the multiplied amplitude signal to the adder 261.
  • the gain multiplier 233 multiplies the gain coefficient reciprocal A ⁇ 1 set by the gain setting unit 231 by the signal from the quantizer 265 to obtain the level of the signal from the quantizer 265 as a signal. Set to a level corresponding to the amplitude signal from line 229.
  • the gain multiplier 233 amplifies the 1-bit signal output from the digital sigma modulator 260 with a gain corresponding to the reciprocal of the gain set in the gain multiplier 232, and generates a pulse modulated signal. Amplifying means.
  • the gain multiplier 233 multiplies the signal from the quantizer 265 by 0.5.
  • the gain multiplier 233 outputs the multiplied signal as a pulse modulation signal to the signal line 239 via the signal line 239.
  • the delta-sigma modulator 260 is a modulation unit that generates a binary 1-bit signal by performing delta-sigma modulation on the output of the gain multiplier 232.
  • the delta sigma modulator 260 is, for example, a secondary delta sigma modulator that performs pulse modulation processing on the signal from the gain multiplier 232.
  • the adder 261 subtracts the feedback signal from the multiplier 267 from the signal output from the gain multiplier 232.
  • the adder 261 outputs the subtracted signal to the integrator 262.
  • the integrator 262 integrates the output signal from the adder 261.
  • the integrator 262 outputs the integrated signal to the adder 263.
  • the adder 263 subtracts the feedback signal from the multiplier 268 from the signal output from the integrator 262.
  • the adder 263 outputs the subtracted signal to the integrator 264.
  • the integrator 264 integrates the output signal from the adder 263.
  • the integrator 264 outputs the integrated signal to the quantizer 265.
  • the quantizer 265 generates a 1-bit (binary) signal based on the magnitude of the signal output from the integral value 264.
  • the quantizer 265 generates a quantized signal indicating “1” or “0”. Further, the quantizer 265 outputs the generated quantized signal to the gain multiplier 233 and also outputs it to the digital-analog converter 266 as a feedback signal.
  • the digital-analog converter (DAC) 266 converts the 1-bit signal that is the feedback signal from the quantizer 265 into a numerical value corresponding to the amplitude signal that is an analog signal.
  • the digital / analog converter 266 outputs the converted feedback signal to the multipliers 267 and 268.
  • the multiplier 267 multiplies the feedback signal from the digital / analog converter 266 by a predetermined weight coefficient a 1 .
  • Multiplier 267 outputs the multiplied feedback signal to adder 261.
  • Multiplier 268 the weighting coefficient a 2 predetermined, to multiply the feedback signal from the digital-to-analog converter 266.
  • the multiplier 268 outputs the multiplied feedback signal to the adder 263.
  • the gain setting unit 231 sets the gain coefficient according to the magnitude of the amplitude signal, whereby the signal level from the gain multiplication unit 232 approaches the saturation level of the delta-sigma modulator 260. For this reason, the amplitude modulation unit 230 can reduce quantization noise caused by delta-sigma modulation.
  • the pulse modulation method of the amplitude modulation unit 230 is not limited to the configuration shown in FIG. Further, the order and parameters of the delta-sigma modulator 260 may be changed as appropriate according to the system to which the present embodiment is applied. Further, a pulse width modulator or the like may be used instead of the delta sigma modulator 260.
  • the example in which the amplitude threshold is set to “0.5” has been described, but another value may be set.
  • the gain coefficient A of the gain setting unit 231 or the circuit scale (size) of the amplifiers 320 and 350 may be adjusted.
  • FIG. 9 is a diagram relating to a simulation result of the pulse modulation signal generated by the amplitude modulation unit 230.
  • FIG. 9a is a diagram showing a waveform of a general binary (0, 1) pulse modulation signal.
  • FIG. 9 b is a diagram illustrating a waveform of a ternary pulse modulation signal generated by the amplitude modulation unit 230.
  • the amplitude signal is a 2 MHz sine wave, and the frequency of the sampling clock signal of the amplitude modulator 230 is 200 MHz.
  • the saturation level of the pulse modulation signal 238 is “1.0”.
  • the saturation level of the pulse modulation signal 238 is “0.5”. During this period, it can be seen that the average duty ratio of the pulse modulation signal 238 is larger in the region of the amplitude level of “0.5” than the pulse modulation signal 891 shown in FIG.
  • the duty ratio of the pulse modulation signal 238 is larger than that in FIG. 9a.
  • the delta-sigma modulator 260 operates in the vicinity of the saturation level during the period when the saturation level of the pulse modulation signal 238 is “0.5”, a high S / N ratio can be ensured.
  • FIG. 10 is a conceptual diagram related to the operation of the power amplifying unit 300.
  • the modulation signal 301 is supplied from the signal line 209.
  • FIG. 10 c is a diagram illustrating an example of the modulation signal 301 supplied from the signal line 209 to the power amplification unit 300.
  • a pulse signal string is indicated by a solid line
  • an envelope of the modulation signal is indicated by a dotted line.
  • the envelope of this modulation signal corresponds to the pulse height of the pulse modulation signal.
  • FIG. 10 a is a diagram illustrating an operation of the power amplification unit 300 that amplifies the modulation signal 301 when the pulse height of the pulse modulation signal is “0.5”.
  • the amplifier 350 does not operate and only the amplifier 320 operates as shown in FIG. 10a. .
  • the output power of the amplifier 320 is 0.5 ⁇ Pmax as described in FIG.
  • FIG. 10B is a diagram illustrating an operation of the power amplification unit 300 that amplifies the modulation signal 301 when the pulse height of the pulse modulation signal is “1.0”.
  • the modulation signal 301 when the pulse height of the pulse modulation signal is “1.0” is supplied to the power amplifying unit 300, both the amplifiers 320 and 350 operate as shown in FIG. 10b.
  • the output power of the power amplifying unit 300 is saturated power 2 ⁇ Pmax.
  • FIG. 11 is a diagram showing a characteristic of power efficiency with respect to the normalized amplitude in the transmission device 100.
  • FIG. 11 shows a power efficiency characteristic 101 of the transmission apparatus 100, a power efficiency characteristic 801 of a conventional Doherty amplifier, and a probability density characteristic 809.
  • the horizontal axis is the normalized amplitude of the input signal.
  • This normalized amplitude is a value obtained by dividing the amplitude signal by the maximum amplitude of the amplitude signal.
  • the power efficiency characteristic 101 indicates the characteristic of the power efficiency with respect to the normalized amplitude of the amplitude signal in the transmission apparatus 100.
  • the power efficiency characteristic 101 is assumed to have a maximum efficiency of 78.5% in comparison with the power efficiency characteristic 801, and further, with respect to each saturated output power when each of the amplifying units 320 and 350 is a class D amplifier. It is a power efficiency characteristic when switching loss is assumed to be 20%.
  • the power efficiency characteristic 101 shows higher efficiency than the efficiency of the Doherty amplifier 820 because only the amplifier 320 operates in a range where the normalized amplitude is “0.5” or less.
  • the power efficiency characteristic 101 assumes that the switching loss is 20%, the power efficiency gradually decreases as the normalized amplitude decreases, and sharply decreases from around “0.1”. This is because the ratio of the switching loss of the amplifier 320 to the output power of the power amplification unit 300 increases because the duty ratio of the pulse modulation signal decreases as the normalized amplitude decreases.
  • the duty ratio of the pulse modulation signal is 100%.
  • the output power of the power amplifying unit 300 is 0.5 ⁇ Pmax, and the power efficiency is maximized.
  • both of the amplifiers 320 and 350 operate at the maximum power efficiency.
  • the normalized amplitude is “1.0”
  • the duty ratio of the pulse modulation signal is 100%
  • the power amplification unit 300 reaches the saturation power of 2 ⁇ Pmax. Therefore, the power efficiency is maximized.
  • the average power efficiency based on the probability density characteristic 809 is 72%, which is extremely higher than the average power efficiency (64%) of the Doherty amplifier 820 described in FIG. This is because the power efficiency corresponding to the normalized amplitude having a high appearance frequency is improved.
  • the pulse modulation signal generation unit 201 changes the pulse height or the pulse density according to the amplitude component while changing the pulse width or the pulse density according to the amplitude component of the input signal. By changing to, a pulse modulation signal is generated.
  • the pulse modulation signal generation unit 201 can reduce quantization noise generated when the pulse modulation signal is generated, and can generate a pulse modulation signal that becomes an output signal with a high S / N ratio. That is, the transmission apparatus 100 can generate an output signal with a high S / N ratio over a wide dynamic range.
  • the pulse modulation signal generation unit 201 changes the saturation level of the amplitude modulation unit 230 from “1.0” to “0.5” in the range where the normalized amplitude of the input signal is “0.5” or less. ”. For this reason, the transmission apparatus 100 can modulate an amplitude signal on conditions with a high SN ratio. As a result, the transmission apparatus 100 can output an output signal with a good S / N ratio even in the range where the normalized amplitude is “0.5” or less, as compared with the delta-sigma modulator 863 shown in FIG.
  • the pulse modulation signal generation unit 201 generates a pulse modulation signal having three pulse heights of “0.0”, “0.5”, and “1.0”. Therefore, the transmission apparatus 100 can improve the resolution of the amplitude signal from 1.0 bit to 1.5 bits as compared with the delta-sigma modulator 863 shown in FIG.
  • the transmission device 100 can improve the SN ratio of the output signal output from the transmission device 100 by about 3 dB. Therefore, even if the frequency of the sampling clock supplied to the delta sigma modulator 260 is reduced by half, the transmission apparatus 100 can ensure the same SN ratio as the delta sigma modulator 863 shown in FIG. Power consumption can be suppressed.
  • the power amplifying unit 300 further includes amplifiers (amplifiers 320 and 350) having the number of discrete amplitude levels of the modulation signal, and the operation of amplifying the modulation signal among the amplifiers 320 and 350.
  • the number of amplifiers increases as the amplitude level of the modulation signal increases.
  • the power amplifying unit 300 includes the plurality of amplifiers 320 and 350, so that the fixed power loss caused by the switching loss generated in the entire power amplifying unit 300 can be distributed to the two amplifiers. .
  • the power amplifier 300 can reduce the power loss of the power amplifier 300 by reducing the number of operational amplifiers as the discrete amplitude level of the modulation signal decreases.
  • the power amplification unit 300 when receiving the modulation signal when the pulse height of the pulse modulation signal is “0.5”, the power amplification unit 300 amplifies the modulation signal only by the amplifier 320. Therefore, in the power amplifying unit 300, only the amplifier 320 amplifies the modulation signal when the normalized amplitude is “0.5” or less. For this reason, the power amplifying unit 300 can improve the power efficiency of the power amplifying unit 300. Therefore, the transmission apparatus 100 can operate the power amplification unit 300 with high power efficiency even in a range where the normalized amplitude of the input signal is small.
  • the transmission device 100 can generate an output signal having high power efficiency and a small waveform distortion in an operation region where the back-off is large in the power amplification unit 300.
  • the power amplification unit 300 when receiving the modulation signal when the pulse height of the pulse modulation signal is “1.0”, the power amplification unit 300 amplifies the modulation signal by the amplifier 350 in addition to the amplifier 320. Thereby, the transmission apparatus 100 can operate the power amplification unit 300 with high power efficiency even in a range where the normalized amplitude of the input signal is large. Therefore, the transmitter 100 can amplify the input signal with high efficiency over a wide dynamic range.
  • the gain multiplier 232 increases the gain as the amplitude component of the input signal decreases, and amplifies the amplitude component of the input signal with the gain. Then, the delta sigma modulator 260 generates a 1-bit signal by performing delta sigma modulation or pulse width modulation on the output of the gain multiplier 232.
  • the gain multiplication unit 233 amplifies the 1-bit signal that is the output of the delta sigma modulator 260 with a gain corresponding to the inverse of the gain of the gain multiplication unit 232 to generate a pulse modulation signal.
  • the amplitude modulation unit 230 can operate the delta-sigma modulator 260 near the saturation level even if the amplitude component of the input signal is small. For this reason, quantization noise generated by the delta-sigma modulation unit 260 can be suppressed.
  • FIG. 12 is a block diagram showing a modification of the signal modulation unit 200 in the first embodiment of the present invention.
  • the transmission apparatus 100 is a transmission apparatus that includes an I component and a Q component that are orthogonal to each other, and amplifies and transmits an input signal that defines the I component and the Q component.
  • the signal modulation unit 600 includes a pulse modulation signal generation unit 601, a clock signal generator 650, an integration signal generation unit 602, and a modulation signal generation unit 690.
  • the pulse modulation signal generation unit 601 includes a signal generation unit 610, an amplitude calculation unit 620, an in-phase component modulation unit 630, and a quadrature component modulation unit 660.
  • the integration signal generation unit 602 includes integrators 640 and 670 and a delay unit 680.
  • the pulse modulation signal generation unit 601 represents each of the pulse modulation signals representing the magnitudes of the I component and the Q component included in the input signal by the pulse width or pulse density and the discrete pulse height, respectively. There is a pulse modulation signal generating means for generating.
  • the pulse modulation signal generating unit 601 changes the pulse height discretely according to the magnitude of the amplitude component of the input signal while changing the pulse width or pulse density according to the magnitude of the I component. Thus, an I-component pulse modulation signal is generated.
  • the pulse modulation signal generation unit 601 discretely adjusts the pulse height according to the magnitude of the amplitude component of the input signal while changing the pulse width or pulse density according to the magnitude of the Q component. By changing, a pulse modulation signal of Q component is generated.
  • integrators 640 and 670, the clock signal generator 650, the delay device 680, and the modulation signal generator 690 are the integrators 882 and 886, the clock signal generator 883, and the delay device shown in FIG. 885 and the modulation signal generation unit 887 are the same, and the description thereof is omitted here.
  • Clock signal generator 650 can be generally referred to as clock signal generating means.
  • Modulation signal generation section 690 can be generally referred to as modulation signal generation means.
  • the signal generation unit 610 is the same as the signal generation unit 210 shown in FIG.
  • the signal generation unit 610 supplies an I signal, which is an I component of the input signal, to the amplitude calculation unit 620 and the in-phase component modulation unit 630 via the signal line 618. Further, the signal generation unit 610 supplies a Q signal that is a Q component of the input signal to the amplitude calculation unit 620 and the quadrature component modulation unit 660 via the signal line 619.
  • the amplitude calculation unit 620 calculates the I component from the signal generation unit 610 and the amplitude component of the input signal defined by the Q generation.
  • the amplitude calculation unit 620 calculates the amplitude component of the input signal based on Equation 1, for example.
  • the amplitude calculation unit 620 supplies the calculated amplitude component to the in-phase component modulation unit 630 and the quadrature component modulation unit 660 as an amplitude signal.
  • the in-phase component modulation unit 630 converts the I signal supplied from the signal generation unit 610 into a pulse modulation signal.
  • the in-phase component modulator 630 is the same as the amplitude modulator 230 shown in FIG.
  • the in-phase component modulation unit 630 discretely adjusts the pulse height according to the amplitude component supplied from the amplitude calculation unit 620 while changing the pulse width or pulse density according to the I signal size. To generate a pulse in-phase signal which is a pulse modulation signal.
  • the in-phase component modulation unit 630 generates a pulse in-phase signal by performing delta sigma modulation processing or pulse width modulation processing on the I signal at a saturation level corresponding to the magnitude of the amplitude signal.
  • the in-phase component modulation unit 630 can be realized by, for example, the same configuration as the amplitude modulation unit 230 illustrated in FIG. In this case, the amplitude signal from the signal line 629 is supplied to the gain setting unit 231, and the I signal from the signal line 618 is supplied to the gain multiplication unit 232.
  • the gain setting unit 231 compares the standardized amplitude magnitude obtained by standardizing the amplitude signal with the maximum level of the amplitude signal being “1.0” and the amplitude threshold set to “0.5”. Then, the gain setting unit 231 sets “2.0” to the gain multiplication unit 232 and sets “0.5” to the gain multiplication unit 233 when the normalized amplitude is “0.5” or less. Set.
  • the gain setting unit 231 selects a gain coefficient of “1.0” when the magnitude of the normalized amplitude exceeds “0.5”. In this case, gain setting section 231 sets “1.0” as gain multiplier 232 as the selected gain coefficient, and gain multiplier 233 as the inverse of the gain coefficient. Set to.
  • gain multipliers 232 and 233 can be generally referred to as first gain variable amplification means and second gain variable amplification means.
  • Delta sigma modulator 260 can be generally referred to as first modulation means.
  • FIG. 1 an example of the pulse in-phase signal generated based on the amplitude signal by the in-phase component modulator 630 is shown in FIG.
  • FIG. 13 a is a diagram illustrating an example of an amplitude signal supplied to the signal line 629. This amplitude signal shows the same waveform as the amplitude signal shown in FIG. 7a.
  • FIG. 13 b is a diagram illustrating an example of the I signal supplied to the signal line 618.
  • FIG. 13c is a diagram illustrating an example of a pulse in-phase signal generated based on the I signal illustrated in FIG. 13b and the amplitude signal illustrated in FIG. 13a.
  • the horizontal axis is the time axis
  • the vertical axis is the amplitude.
  • the orthogonal component modulation unit 660 converts the Q signal supplied from the signal generation unit 610 into a pulse modulation signal.
  • the quadrature component modulation unit 660 is the same as the amplitude modulation unit 230 shown in FIG.
  • the quadrature component modulator 660 changes the pulse height or the pulse density according to the magnitude of the amplitude component supplied from the amplitude calculator 620 while changing the pulse width or pulse density according to the magnitude of the I signal. To generate a pulse quadrature signal that is a pulse modulation signal.
  • the quadrature component modulation unit 660 generates a pulse quadrature signal by performing delta-sigma modulation processing or pulse width modulation processing on the Q signal at a saturation level corresponding to the magnitude of the amplitude signal.
  • the quadrature component modulation unit 660 can be realized, for example, by the same configuration as the amplitude modulation unit 230 shown in FIG. In this case, the amplitude signal from the signal line 629 is supplied to the gain setting unit 231, and the orthogonal signal from the signal line 619 is supplied to the gain multiplication unit 232.
  • the gain multipliers 232 and 233 constituting the quadrature component modulator 660 can be generally referred to as third gain variable amplifying means and fourth gain variable amplifying means.
  • Delta sigma modulator 260 can be generally referred to as second modulation means.
  • FIG. 13 shows an example of the pulse quadrature signal generated by the quadrature component modulation unit 660 based on the amplitude signal.
  • FIG. 13 d is a diagram illustrating an example of the Q signal supplied to the signal line 619.
  • FIG. 13e is a diagram illustrating an example of a pulse orthogonal signal generated based on the Q signal illustrated in FIG. 13d and the amplitude signal illustrated in FIG. 13a.
  • FIG. 13f is a diagram illustrating a modulation signal generated by the modulation signal generation unit 690.
  • the horizontal axis is the time axis
  • the vertical axis is the amplitude.
  • the integration signal generation unit 602 integrates the clock signal from the clock signal generation unit 650 and the pulse in-phase signal from the in-phase component modulation unit 630 to generate a first integration signal, and the clock signal from the clock signal generation unit 650 Is an integrated signal generating means for integrating the signal delayed by 1 clock and the pulse orthogonal signal from the orthogonal component modulation section 660 to generate a second integrated signal.
  • Modulation signal generation section 690 adds the first integration signal and second integration signal from integration signal generation section 602, and the amplitude level is discrete according to the pulse height of the pulse modulation signal of the I component and Q component. A modulation signal that changes to
  • the in-phase component modulation unit 630 and the quadrature component modulation unit 660 generate a pulse in-phase signal and a pulse quadrature signal based on the magnitude of the amplitude signal. Accordingly, the signal modulation unit 600 can generate a modulated signal having a binary discrete amplitude level.
  • the I signal and the Q signal are superimposed on the clock in the order of “I”, “Q”, “ ⁇ I”, and “ ⁇ Q”, and have a discrete binary amplitude level.
  • a modulated signal can be generated.
  • the modulation signal generation unit 690 adds the first integration signal and the second integration signal from the integration signal generation unit 602, thereby obtaining a binary value.
  • a pulse modulated signal having discrete amplitude levels can be generated.
  • the modulation signal generation unit 690 can reduce quantization noise generated when generating the pulse modulation signal, and can generate a modulation signal with a high S / N ratio.
  • FIG. 14 is a block diagram illustrating a configuration example of the transmission device 110.
  • Transmitting apparatus 110 includes power amplifying section 500 instead of power amplifying section 300 in transmitting apparatus 100 shown in FIG.
  • the saturation level of the digital sigma modulator 260 when the saturation level of the digital sigma modulator 260 is normalized to “1.0”, the amplitude modulation unit 230 is “0.0”, “0.25”, “0.5”. A pulse modulated signal having four amplitude levels of “1.0” and “1.0” is generated based on the magnitude of the amplitude signal.
  • the amplitude modulation unit 230 generates a pulse modulation signal having ternary saturation levels of “0.25”, “0.5”, and “1.0” according to the magnitude of the amplitude signal.
  • the amplitude modulation unit 230 can be realized, for example, by the configuration shown in FIG. In this case, the gain setting unit 231 normalizes the maximum level of the amplitude signal to “1.0”, and the normalized amplitude magnitude thus normalized, and “0.25” and “0.5”. Compare the two amplitude thresholds.
  • the gain setting unit 231 selects the gain coefficient of “4.0” when the size of the normalized amplitude is “0.25” or less.
  • the gain setting unit 231 sets the selected gain coefficient “4.0” in the gain multiplication unit 232 and sets the reciprocal “0.25” of the gain coefficient in the gain multiplication unit 233.
  • the gain setting unit 231 selects a gain coefficient of “0.5” when the size of the normalized amplitude is larger than “0.25” and equal to or smaller than “0.5”.
  • the gain setting unit 231 sets the selected gain coefficient “2.0” in the gain multiplication unit 232 and sets the reciprocal number “0.5” of the gain coefficient in the gain multiplication unit 233.
  • the gain setting unit 231 selects a gain coefficient of “1.0” when the magnitude of the normalized amplitude exceeds “0.5”.
  • the gain setting unit 231 sets the selected gain coefficient “1.0” in the gain multiplication unit 232 and sets the reciprocal “1.0” of the gain coefficient in the gain multiplication unit 233.
  • the configuration other than the gain setting unit 231 is the same as the function described with reference to FIG.
  • the power amplifying unit 500 is power amplifying means for amplifying the modulation signal whose amplitude level changes discretely according to the ternary saturation level of the pulse modulation signal from the modulation signal generation unit 202.
  • the power amplifying unit 300 includes three amplifiers 520, 550, and 570 corresponding to the number of discrete amplitude levels of the modulation signal, that is, the number of saturation levels of the pulse modulation signal.
  • the power amplifier 500 increases the number of operational amplifiers that amplify the modulated signal among the amplifiers 520, 550, and 570 as the amplitude level of the modulated signal increases, and synthesizes the outputs of the operational amplifiers. Output.
  • one operational amplifier (amplifier 520) operates.
  • the power amplifying unit 500 receives a modulation signal having an amplitude level corresponding to the pulse height “0.5” of the pulse modulation signal
  • the two operational amplifiers (amplifiers 520 and 550) operate to output these signals. Are combined and output.
  • the power amplification unit 500 when receiving a modulation signal having an amplitude level corresponding to the pulse height “1.0” of the pulse modulation signal, the power amplification unit 500 operates three operational amplifiers (amplifiers 520, 550, and 570). Are combined and output.
  • the power amplifying unit 500 includes a power distributor 510, quarter wavelength transmission lines 530, 540, and 580, and a half wavelength transmission line 560.
  • the amplifier 520 has an input terminal connected to the power distributor 510 and an output terminal connected to one end of the quarter wavelength transmission line 530.
  • the quarter wavelength transmission line 540 has one end connected to the power distributor 510 and the other end connected to the input end of the amplifier 550.
  • one end of the 1 ⁇ 2 wavelength transmission line 560 is connected to the power distributor 510, and the other end is connected to the input end of the amplifier 570.
  • One end of the quarter wavelength transmission line 580 is connected to the other end of the quarter wavelength transmission line 530 and the output end of the amplifier 550 via the synthesis unit 591, and the other end is connected to the amplifier 570 via the synthesis unit 590. Connected to the output end and output filter 410.
  • the power amplification unit 500 is a 3-way Doherty amplifier.
  • the amplifiers 520 and 550, the quarter wavelength transmission lines 530 and 540, and the combining unit 591 are the amplifiers 320 and 350, the quarter wavelength transmission lines 330 and 340, and the combining unit 360 shown in FIG. Since this is the same as that described above, description thereof is omitted here.
  • the amplifier 520 is biased so as to operate when the modulation signal when the pulse height of the pulse modulation signal is “0.25” or more is supplied from the signal line 209. .
  • the amplifier 520 is set so that the power efficiency is maximized when the modulation signal when the pulse height of the pulse modulation signal is “0.25” or more is received.
  • the amplifier 550 is biased so as to operate when the modulation signal when the pulse height of the pulse modulation signal is “0.5” or more is supplied from the signal line 209.
  • the amplifier 550 is set so that the power efficiency is maximized when the modulation signal when the pulse height of the pulse modulation signal is “0.5” or more is supplied.
  • the power distributor 510 distributes the power of the modulation signal from the signal line 209 into three.
  • the power distributor 510 supplies the three modulated signals thus distributed to the amplifier 520, the quarter wavelength transmission line 540, and the half wavelength transmission line 560 via signal lines 517 to 519, respectively.
  • the 1/2 wavelength transmission line 560 is a 1/2 wavelength impedance transformer.
  • the transmission line 560 outputs the modulation signal from the signal line 519 to the amplifier 570.
  • the quarter wavelength transmission line 580 is a quarter wavelength impedance transformer.
  • the transmission line 580 outputs the modulation signals from the signal lines 517 and 518 to the output filter 410 via the synthesis unit 590.
  • the amplifier 570 is a peak amplifier (peak amplifier) biased to class C.
  • the amplifier 570 has the same configuration as the amplifier 350.
  • the amplifier 570 is biased so as to operate when the modulation signal when the pulse height of the pulse modulation signal is “1.0” is supplied from the signal line 209.
  • the amplifier 570 is set so that the power efficiency is maximized when the modulation signal when the pulse height of the pulse modulation signal is “1.0” is received. Therefore, the amplifier 570 amplifies the modulation signal when the pulse height of the pulse modulation signal is “1.0” with the maximum power efficiency.
  • the amplifier 570 operates on the modulation signal when the pulse height of the pulse modulation signal is “1.0”, and the pulse height of the pulse modulation signal is “0.0”, “0.25”, or It does not operate for the modulation signal at “0.5”.
  • a switching mode amplifier may be used.
  • the amplifier 570 outputs the amplified modulated signal to the output filter 410 via the synthesis unit 590.
  • Amplifier 570 can generally be referred to as an amplifying means or an operational amplifying means.
  • the synthesizing unit 590 synthesizes the modulation signal from the quarter wavelength transmission line 580 and the modulation signal from the amplifier 570.
  • FIG. 15 is a diagram illustrating an example of a waveform of a signal generated by the transmission device 110.
  • the horizontal axis is the time axis
  • the vertical axis is the amplitude.
  • FIG. 15 a is a diagram illustrating an example of an amplitude signal supplied to the signal line 229.
  • FIG. 15b is a diagram illustrating an example of a pulse modulation signal generated based on the amplitude signal illustrated in FIG. 15a.
  • FIG. 15 c is a diagram illustrating an example of a phase modulation signal supplied from the signal line 249.
  • FIG. 15d is a diagram illustrating an example of a modulation signal generated based on the pulse modulation signal and the phase modulation signal illustrated in FIGS. 15b and 15c, respectively, in the integration unit 250.
  • the modulation signal is indicated by a solid line
  • the envelope of the modulation signal is indicated by a dotted line.
  • FIG. 15e is a diagram illustrating an example of the modulated signal from which the rectangular wave component has been removed by the output filter 410 after the power of the modulated signal illustrated in FIG.
  • the modulation signal is indicated by a solid line
  • the envelope of the modulation signal is indicated by a dotted line.
  • the waveform of the amplitude signal shown in FIG. 15a approximates the waveform of the envelope of the modulation signal shown by the dotted line in FIG. 15e.
  • FIG. 16 is a diagram showing the power efficiency characteristics with respect to the normalized amplitude of the amplitude signal in the transmission apparatus 110.
  • FIG. 16 shows a power efficiency characteristic 111 of the transmitter 110, a power efficiency characteristic 802 of a conventional 3-way Doherty amplifier for comparison with the power efficiency characteristic 111, and a probability density characteristic 809. .
  • a power efficiency characteristic 802 indicates a power efficiency characteristic in a three-way Doherty amplifier that amplifies a modulation signal whose envelope changes continuously.
  • the power efficiency characteristic 111 indicates the characteristic of the power efficiency with respect to the normalized amplitude of the amplitude signal in the transmission device 110. In comparison with the power efficiency characteristic 802, the power efficiency characteristic 111 assumes that the maximum efficiency of the transmission apparatus 110 is 78.5%, and further, each saturation when each of the amplifiers 520, 550, and 570 is a class D amplifier. It is a power efficiency characteristic when switching loss with respect to output power is assumed to be 20%.
  • the power efficiency in the range where the normalized amplitude is “0.00” or more and “0.25” or less is higher than the power efficiency characteristic 802.
  • the normalized amplitude is “0.25 (12 dB back-off in terms of power)”
  • the duty ratio of the pulse modulation signal whose pulse height is “0.25” is 100%. For this reason, the power efficiency of the transmission apparatus 110 becomes the maximum (78.5%).
  • the pulse height of the pulse modulation signal is set to “0.5”. In this range, both amplifiers 520 and 550 operate.
  • the transmission apparatus 110 can obtain higher power efficiency than the power efficiency characteristic 802. Furthermore, when the normalized amplitude is “0.5 (6 dB back-off in terms of power)”, the duty ratio of the pulse modulation signal is 100%, so that the power efficiency is maximized (78.5%).
  • the pulse height of the pulse modulation signal is set to “1.0”, and all of the amplifiers 520, 550 and 570 operate. For this reason, even if the switching loss when the amplifiers 520, 550, and 570 are class D amplifiers is assumed to be 20%, the transmission apparatus 110 can ensure higher power efficiency than the power efficiency characteristic 802.
  • the duty ratio of the pulse modulation signal is 100%, and the power efficiency is maximum (78.5%).
  • the pulse modulation signal generation unit 201 generates a pulse modulation signal having a ternary saturation level based on the amplitude signal, so that the amplitude modulation unit can be compared with the first embodiment.
  • the quantization noise associated with the delta-sigma modulation at 230 can be further suppressed. Therefore, the transmission apparatus 110 can further improve the SN ratio of the output signal output from the antenna 420.
  • the pulse modulation signal generation unit 201 sets the saturation level of the amplitude modulation unit 230 to “0.25” or “0” in the range where the normalized amplitude of the input signal is “0.5” or less. .5 ", the amplitude signal can be modulated under a high S / N ratio.
  • the transmission apparatus 110 can output an output signal with a good S / N ratio even in the range where the normalized amplitude is “0.5” or less, as compared with the delta-sigma modulator 863 shown in FIG.
  • the amplitude modulation unit 230 when the amplitude modulation unit 230 generates a pulse modulation signal having four values of pulse heights “0.00”, “0.25”, “0.50”, and “1.00”, Compared with the delta-sigma modulator 863, the resolution of the amplitude signal can be improved from 1 bit to 2 bits.
  • the transmission apparatus 110 can improve the SN ratio of the output signal by about 6 dB. Therefore, even if the frequency of the sampling clock supplied to the delta sigma modulator 260 is set to 1 ⁇ 4, the same SN ratio as that of the delta sigma modulator 863 shown in FIG. Electric power can be suppressed.
  • the power amplifier 500 further includes the three amplifiers 520, 550, and 570, so that the output power loss due to the switching loss of the power amplifier 500 can be further dispersed. . Therefore, the transmission apparatus 110 can further improve the power efficiency in the range where the normalized amplitude is “0.0” to “0.5” compared to the first embodiment.
  • the transmission apparatus 110 generates an output signal having higher power efficiency and smaller waveform distortion in the operation region where the back-off is large in the power amplifying unit 500 compared to the first embodiment. Can do.
  • FIG. 17 is a block diagram illustrating a configuration example of the transmission device 120 according to the third embodiment of the present invention.
  • the transmission device 120 includes a power amplification unit 700 instead of the power amplification unit 300 in the transmission device 100 illustrated in FIG. Since the output filter 410 and the antenna 420 are the same as those shown in FIG. 6, the same reference numerals are given and description thereof is omitted here.
  • the signal modulation unit 200 includes a pulse modulation signal obtained by performing delta sigma modulation on the amplitude component at a saturation level corresponding to the amplitude component of the input signal among the binary saturation levels, a phase modulation signal, Is used to generate a modulated signal.
  • This modulation signal is a signal whose amplitude level changes discretely according to the binary pulse heights of “0.5” and “1.0” which the pulse modulation signal has.
  • the power amplification unit 700 is a power amplification unit that amplifies the modulation signal generated by the signal modulation unit 200.
  • the power amplification unit 700 includes a signal switching unit 430, a power distributor 710, a supply unit 720, amplifiers 731 and 732, and a power combiner 740.
  • the supply unit 720 includes switches 721 and 722.
  • the power distributor 710 is the same as the power distributor 310 shown in FIG.
  • the signal switching unit 430 determines whether to amplify the modulation signal by the amplifier based on the pulse height (amplitude level) of the pulse modulation signal corresponding to the discrete amplitude level of the modulation signal.
  • the signal switching unit 430 generates a control signal for switching whether or not the switches 721 and 722 are connected based on the pulse height of the pulse modulation signal from the signal line 239. That is, the signal switching unit 430 generates a control signal based on the amplitude level of the modulation signal corresponding to the pulse height of the pulse modulation signal.
  • the signal switching unit 430 conducts a conduction signal for bringing the switch 721 into a conduction state and a non-conduction for bringing the switch 722 into a non-conduction state.
  • the signal is supplied as a control signal to switches 721 and 722, respectively.
  • the signal switching unit 430 conducts a conduction signal for making the switch 721 conductive and a conduction for making the switch 722 conductive.
  • the signal is supplied as a control signal to switches 721 and 722, respectively.
  • the supplying unit 720 supplies a modulation signal to the amplifiers 731 and 732 according to the control signal from the signal switching unit 430.
  • the switch 721 switches the presence / absence of connection between the power distributor 710 and the amplifier 731.
  • the switch 721 receives a conduction signal from the signal switching unit 430, the switch 721 connects between the power distributor 710 and the amplifier 731. That is, the switch 721 supplies the modulation signal from the signal line 718 to the amplifier 731 when receiving the conduction signal from the signal switching unit 430.
  • the switch 721 when the switch 721 receives a non-conduction signal from the signal switching unit 430, the switch 721 disconnects the connection between the power distributor 710 and the amplifier 731. That is, when the switch 721 receives a non-conduction signal from the signal switching unit 430, the switch 721 suppresses supplying the modulation signal from the signal line 718 to the amplifier 731.
  • the switch 722 switches the presence / absence of connection between the power distributor 710 and the amplifier 732.
  • the switch 722 receives a conduction signal from the signal switching unit 430, the switch 722 connects the power distributor 710 and the amplifier 732. That is, the switch 721 supplies the modulation signal from the signal line 719 to the amplifier 732 when receiving the conduction signal from the signal switching unit 430.
  • the switch 722 when the switch 722 receives a non-conduction signal from the signal switching unit 430, the switch 722 disconnects the connection between the power distributor 710 and the amplifier 732. That is, the switch 722 suppresses supply of the modulation signal from the signal line 719 to the amplifier 732 when the non-conduction signal is received from the signal switching unit 430.
  • the amplifiers 731 and 732 are amplification means or operation amplification means for amplifying the modulation signals supplied from the switches 721 and 722, respectively.
  • the amplifiers 731 and 732 are set so that the power efficiency is maximized when the modulation signal when the pulse height of the pulse modulation signal is “0.5” is supplied.
  • the amplifiers 731 and 732 are realized by, for example, class D amplifiers.
  • the amplifiers 731 and 732 supply each amplified modulated signal to the power combiner 740.
  • the power combiner 740 combines the modulated signals from the amplifiers 731 and 732.
  • the power combiner 740 outputs the modulated signal combined with the power to the output filter 410.
  • the signal switching unit 430 supplies the conduction signal only to the switch 721 so that only the amplifier 731 amplifies the modulation signal. be able to.
  • the signal switching unit 430 supplies a conduction signal to both the switches 721 and 722, whereby both the amplifiers 731 and 732 modulate the modulation signal. Can be amplified.
  • the signal switching unit 430 supplies the modulation signal to the amplifiers 731 and 732 based on the pulse height of the pulse modulation signal corresponding to the discrete amplitude level of the modulation signal. To control. Therefore, when receiving the modulation signal when the pulse height of the pulse modulation signal is “0.5”, the power amplification unit 700 can amplify the modulation signal with only one operational amplifier (amplifier 731).
  • the power amplifying unit 700 is a region in which the amplitude component of the input signal is small as compared to the case where the modulated signal is amplified by one class D amplifier as in the transmission devices 850 and 870 shown in FIGS. Even so, the power efficiency can be improved.
  • the transmitters 850 and 870 amplify the modulation signal by one class D amplifier 830 from a region where the amplitude component of the input signal is large to a region where the amplitude component is small. This is because it becomes relatively large and the efficiency is remarkably lowered. Therefore, in the transmission apparatus 120 according to the third embodiment, since only the amplifier 731 on one side operates in a region where the amplitude component of the input signal is small, the fixed power loss can be reduced.
  • the power amplifying unit 700 can improve the average power efficiency weighted based on the probability density characteristic 809 as compared with the case where the modulation signal is amplified by one class D amplifier.
  • the discrete amplitude level of the modulation signal is set to three or more. It may be set. In this case, an amplifier and a switch are added to the power amplification unit 700 according to the number of discrete amplitude levels.
  • FIG. 18 is a block diagram illustrating a configuration example of the transmission device 130 according to the fourth embodiment of the present invention.
  • the transmission device 130 includes a power amplification unit 750 having a signal switching unit 440 instead of the power amplification unit 300 in the transmission device 100 illustrated in FIG. 6. Since the output filter 410 and the antenna 420 are the same as those shown in FIG. 6, the same reference numerals are given and description thereof is omitted here.
  • the signal modulation unit 200 includes a pulse modulation signal obtained by performing delta sigma modulation on the amplitude component at a saturation level corresponding to the amplitude component of the input signal among the binary saturation levels, a phase modulation signal, Is used to generate a modulated signal.
  • This modulated signal is a signal whose amplitude level changes discretely according to binary pulse heights of “0.5” and “1.0” of the pulse modulated signal.
  • the power amplification unit 750 is a power amplification unit that amplifies the modulation signal generated by the signal modulation unit 200.
  • the power amplifying unit 750 includes a signal switching unit 440, amplifiers 731 and 732, and a power combiner 740. Since the power combiner 740 is the same as that shown in FIG. 17, the same reference numerals are given and description thereof is omitted here.
  • the amplifiers 731 and 732 are amplification means or operation amplification means similar to those shown in FIG.
  • the amplifier 731 amplifies the modulation signal when the pulse height of the pulse modulation signal is “0.5” or more.
  • the amplifier 731 is an amplifier corresponding to the modulation signal when the pulse height of the pulse modulation signal is “0.5” or more.
  • the amplifier 732 amplifies the modulation signal when the pulse height of the pulse modulation signal is “1.0”.
  • the amplifier 732 is an amplifier corresponding to the modulation signal when the pulse height of the pulse modulation signal is “1.0” or more.
  • the signal switching unit 440 is a supply unit that generates signals to be supplied to the amplifiers 731 and 732 based on the amplitude level of the modulation signal from the signal line 209, respectively.
  • the signal switching unit 440 supplies the modulation signal from the signal line 209 to the amplifier 731 via the signal line 448.
  • the signal switching unit 440 extracts only the modulation signal when the pulse height of the pulse modulation signal is “1.0” via the signal line 449, and sends the extracted modulation signal to the amplifier 732. Supply.
  • the signal switching unit 440 detects the amplitude level of the modulation signal from the signal line 209, for example.
  • the signal switching unit 440 sets the pulse height of the pulse modulation signal to “0”. ... ”Is supplied to the amplifier 732.
  • the signal switching unit 440 determines whether the pulse height of the pulse modulation signal is “1.0”. The modulation signal is supplied to the amplifier 732.
  • the signal switching unit 440 supplies the modulation signal when the pulse height of the pulse modulation signal is “0.5” or more to the amplifier 731 and the modulation when the pulse height of the pulse modulation signal is “1.0” or more.
  • the signal is supplied to amplifier 732.
  • an example of the modulation signal supplied from the signal switching unit 440 to the signal lines 448 and 449 is shown in FIG.
  • FIG. 19 a is a diagram illustrating an example of a modulation signal supplied from the signal switching unit 440 to the signal line 448.
  • FIG. 19B is a diagram illustrating an example of the modulation signal supplied from the signal switching unit 440 to the signal line 449.
  • the horizontal axis is a common time axis, and the vertical axis is the amplitude.
  • the signal switching unit 440 sends a modulation signal equal to or higher than the corresponding amplitude level to the amplifiers 731 and 732 corresponding one-to-one with the discrete amplitude level of the modulation signal.
  • the transmission device 130 operates only on one side of the amplifier 731 in a region where the amplitude component of the input signal is small compared to the case where the modulation signal is amplified by one class D amplifier. Therefore, the fixed power loss is reduced, and high power efficiency can be obtained.
  • the fourth embodiment it is not necessary to provide the switches 721 and 722 as compared with the third embodiment, so that the circuit scale of the power amplifying unit 750 can be suppressed. That is, high power efficiency can be maintained even with a large back-off.
  • the transmission device in each embodiment of the present invention changes the number of amplifiers that operate according to the magnitude of the amplitude of the input signal, and operates only one amplifier when the amplitude of the input signal is small, As the amplitude of the input signal increases, the number of operating amplifiers can be increased. Thereby, it is possible to optimally switch the saturation output power of the entire power amplification unit (or the size of the entire power amplification unit) according to the magnitude of the amplitude of the input signal.
  • each amplifier is class D.
  • the class D amplifier amplifies the modulation signal with an efficiency of 100% ideally when the input signal is on, and does not consume power during the off period. Therefore, ideally, the transmission apparatus always operates at an efficiency of 100% even as the entire transmission apparatus.
  • the number of operational amplifiers is optimally changed according to the amplitude of the input signal. It can be made relatively small.
  • the example in which the signal modulation units 200 and 600 generate modulation signals having binary and ternary discrete amplitude levels based on the amplitude component of the input signal has been described.
  • a modulated signal having the above discrete amplitude levels may be generated. Thereby, the waveform distortion of the output signal output from the antenna 420 can be further reduced.
  • the power amplification unit includes an amplifier equal to the number of discrete amplitude levels of the modulation signal.
  • the power amplification unit is equal to or greater than the number of discrete amplitude levels of the modulation signal. You may have several amplifiers. Even in this case, the power amplifier can reduce the power loss due to the switching of the amplifier in the power amplifier by reducing the number of operational amplifiers as the input signal becomes smaller. For this reason, the transmission device can suppress a decrease in power efficiency of the power amplification unit.

Abstract

Afin de produire un signal de sortie avec une efficacité de puissance élevée y compris dans des zones de fonctionnement ayant une réduction de puissance d'entrée importante et ayant une distorsion minimale, le dispositif de transmission selon la présente invention inclut une unité de production de signal de modulation par impulsion qui produit un signal de modulation par impulsion en modifiant la largeur d'impulsion ou la densité d'impulsions en réponse à la dimension des composantes d'amplitude dans un signal d'entrée et en modifiant discrètement la hauteur d'impulsions en réponse à la dimension des composants d'amplitude ; une unité de production de signal de modulation qui produit un signal de modulation en intégrant le signal de modulation par impulsion et la composante de phase du signal d'entrée ; une unité d'amplification de puissance qui est équipée d'un nombre d'amplificateurs qui est supérieur ou égal au nombre de niveaux discrets d'amplitude du signal de modulation, qui modifie le nombre d'amplificateurs qui amplifient le signal de modulation en fonction de la valeur des niveaux d'amplitude du signal de modulation, et qui synthétise et fournit la sortie de l'amplificateur ; et un filtre de sortie qui supprime les composantes d'onde carrée de la sortie de l'unité d'amplification de puissance.
PCT/JP2010/071459 2009-12-08 2010-12-01 Dispositif de transmission WO2011070952A1 (fr)

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Cited By (12)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2013042754A1 (fr) * 2011-09-23 2013-03-28 日本電気株式会社 Dispositif d'amplification de puissance électrique
JP2014033404A (ja) * 2012-08-06 2014-02-20 Toshiba Corp 増幅装置
WO2014042270A1 (fr) * 2012-09-14 2014-03-20 日本電気株式会社 Émetteur
EP2582039A3 (fr) * 2011-09-19 2014-04-16 Infineon Technologies AG Système et procédé pour générer un signal modulé à largeur d'impulsion de fréquence radio
US8878622B2 (en) 2011-04-07 2014-11-04 Infineon Technologies Ag System and method for generating a pulse-width modulated signal
WO2015008449A1 (fr) * 2013-07-18 2015-01-22 パナソニック株式会社 Modulateur orthogonal
WO2015133003A1 (fr) * 2014-03-06 2015-09-11 日本電気株式会社 Émetteur et procédé d'émission
JP5900630B2 (ja) * 2012-09-14 2016-04-06 日本電気株式会社 送信機、信号合成回路、信号合成方法
JP2016530739A (ja) * 2013-10-25 2016-09-29 三菱電機株式会社 送信機
KR20170117497A (ko) * 2015-02-15 2017-10-23 스카이워크스 솔루션즈, 인코포레이티드 감소된 크기를 갖는 도허티 전력 증폭기
KR20170117498A (ko) * 2015-02-15 2017-10-23 스카이워크스 솔루션즈, 인코포레이티드 강화된 열적 견고성을 위해 스태거형 캐스코드 레이아웃을 갖는 전력 증폭기
KR20170117550A (ko) * 2015-02-15 2017-10-23 스카이워크스 솔루션즈, 인코포레이티드 캐스코드 전류 스티어링을 통해 향상된 증폭기 효율

Families Citing this family (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP6032203B2 (ja) * 2011-09-09 2016-11-24 日本電気株式会社 Ｒｆ信号生成回路、及び送信機
JP2014082749A (ja) * 2012-09-28 2014-05-08 Fordan Kk 複合電力増幅器を有する複合送信機
US9488722B2 (en) * 2013-06-05 2016-11-08 Samsung Electronics Co., Ltd. Time-of-flight ranging system and method with extended range
US9548880B2 (en) * 2013-09-18 2017-01-17 Nec Corporation Transmitter and its control method
US9077321B2 (en) * 2013-10-23 2015-07-07 Corning Optical Communications Wireless Ltd. Variable amplitude signal generators for generating a sinusoidal signal having limited direct current (DC) offset variation, and related devices, systems, and methods
JP6620757B2 (ja) * 2014-11-19 2019-12-18 日本電気株式会社 送信機、信号合成回路および信号合成方法
WO2017037880A1 (fr) * 2015-09-01 2017-03-09 日本電気株式会社 Modulateur δς, émetteur et intégrateur
WO2019026412A1 (fr) * 2017-08-04 2019-02-07 日本電気株式会社 Dispositif de génération de signal rf et procédé de génération de signal rf
US10284202B1 (en) 2018-04-02 2019-05-07 Raytheon Company Generating analog output from a field programmable gate array by combining scaled digital outputs

Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2002057732A (ja) * 2000-05-30 2002-02-22 Matsushita Electric Ind Co Ltd 送信回路装置
JP2004048703A (ja) * 2002-05-13 2004-02-12 Matsushita Electric Ind Co Ltd 増幅回路、送信装置、増幅方法、および送信方法
JP2004128542A (ja) * 2002-09-30 2004-04-22 Hitachi Kokusai Electric Inc 増幅装置
JP2006238256A (ja) * 2005-02-28 2006-09-07 Pioneer Electronic Corp 増幅装置
JP2006525751A (ja) * 2003-05-05 2006-11-09 クリー マイクロウエイブ リミテッド ライアビリティ カンパニー 選択された位相長および出力インピーダンスを用いた増加されたバックオフ能力および電力付加効率を持つｎウェイｒｆ電力増幅器回路
WO2008136080A1 (fr) * 2007-04-20 2008-11-13 Fujitsu Limited Appareil amplificateur

Family Cites Families (11)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP3369481B2 (ja) 1998-08-06 2003-01-20 シャープ株式会社 ディジタルスイッチングアンプ
JP2002135060A (ja) 2000-10-19 2002-05-10 Matsushita Electric Ind Co Ltd 電力増幅装置及び方法
JP2004100358A (ja) 2002-09-12 2004-04-02 Cleanup Corp 浴室床
ATE435521T1 (de) * 2004-10-28 2009-07-15 Camco Prod & Vertriebs Gmbh Geschalteter leistungsverstärker und verfahren zur verstärkung eines digitalen signals
JP2006203673A (ja) 2005-01-21 2006-08-03 Matsushita Electric Ind Co Ltd 送信増幅回路
US7576606B2 (en) * 2007-07-25 2009-08-18 D2Audio Corporation Digital PWM amplifier having a low delay corrector
KR100710509B1 (ko) * 2006-04-11 2007-04-25 남상욱 펄스면적변조를 이용한 고효율 선형 전력증폭기 시스템
JP2007300400A (ja) 2006-04-28 2007-11-15 Matsushita Electric Ind Co Ltd 送信回路、送信方法、及びそれを用いた通信機器
JP4938597B2 (ja) 2006-09-19 2012-05-23 パナソニック株式会社 送信回路及び通信機器
JP2008124540A (ja) 2006-11-08 2008-05-29 Advanced Telecommunication Research Institute International 通信装置
EP2229726B1 (fr) * 2007-12-07 2014-02-26 Nxp B.V. Emetteur qui comprend un modulateur de durée et de position d'impulsions et procédé destiné à celui-ci

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2002057732A (ja) * 2000-05-30 2002-02-22 Matsushita Electric Ind Co Ltd 送信回路装置
JP2004048703A (ja) * 2002-05-13 2004-02-12 Matsushita Electric Ind Co Ltd 増幅回路、送信装置、増幅方法、および送信方法
JP2004128542A (ja) * 2002-09-30 2004-04-22 Hitachi Kokusai Electric Inc 増幅装置
JP2006525751A (ja) * 2003-05-05 2006-11-09 クリー マイクロウエイブ リミテッド ライアビリティ カンパニー 選択された位相長および出力インピーダンスを用いた増加されたバックオフ能力および電力付加効率を持つｎウェイｒｆ電力増幅器回路
JP2006238256A (ja) * 2005-02-28 2006-09-07 Pioneer Electronic Corp 増幅装置
WO2008136080A1 (fr) * 2007-04-20 2008-11-13 Fujitsu Limited Appareil amplificateur

Cited By (23)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US9337821B2 (en) 2011-04-07 2016-05-10 Infineon Technologies Ag System and method for generating a pulse-width modulated signal
US8878622B2 (en) 2011-04-07 2014-11-04 Infineon Technologies Ag System and method for generating a pulse-width modulated signal
EP2582039A3 (fr) * 2011-09-19 2014-04-16 Infineon Technologies AG Système et procédé pour générer un signal modulé à largeur d'impulsion de fréquence radio
US8971398B2 (en) 2011-09-19 2015-03-03 Infineon Technologies Ag System and method for generating a radio frequency pulse-width modulated signal
WO2013042754A1 (fr) * 2011-09-23 2013-03-28 日本電気株式会社 Dispositif d'amplification de puissance électrique
JPWO2013042754A1 (ja) * 2011-09-23 2015-03-26 日本電気株式会社 電力増幅装置
US9236838B2 (en) 2011-09-23 2016-01-12 Nec Corporation Power amplification device
JP2014033404A (ja) * 2012-08-06 2014-02-20 Toshiba Corp 増幅装置
WO2014042270A1 (fr) * 2012-09-14 2014-03-20 日本電気株式会社 Émetteur
JPWO2014042270A1 (ja) * 2012-09-14 2016-08-18 日本電気株式会社 送信機
JP5900630B2 (ja) * 2012-09-14 2016-04-06 日本電気株式会社 送信機、信号合成回路、信号合成方法
WO2015008449A1 (fr) * 2013-07-18 2015-01-22 パナソニック株式会社 Modulateur orthogonal
US9331635B2 (en) 2013-07-18 2016-05-03 Panasonic Corporation Quadrature modulator
JP2016530739A (ja) * 2013-10-25 2016-09-29 三菱電機株式会社 送信機
WO2015133003A1 (fr) * 2014-03-06 2015-09-11 日本電気株式会社 Émetteur et procédé d'émission
JPWO2015133003A1 (ja) * 2014-03-06 2017-04-06 日本電気株式会社 送信機、送信方法
US9793862B2 (en) 2014-03-06 2017-10-17 Nec Corporation Transmitter and transmission method
KR20170117497A (ko) * 2015-02-15 2017-10-23 스카이워크스 솔루션즈, 인코포레이티드 감소된 크기를 갖는 도허티 전력 증폭기
KR20170117498A (ko) * 2015-02-15 2017-10-23 스카이워크스 솔루션즈, 인코포레이티드 강화된 열적 견고성을 위해 스태거형 캐스코드 레이아웃을 갖는 전력 증폭기
KR20170117550A (ko) * 2015-02-15 2017-10-23 스카이워크스 솔루션즈, 인코포레이티드 캐스코드 전류 스티어링을 통해 향상된 증폭기 효율
KR102563231B1 (ko) * 2015-02-15 2023-08-04 스카이워크스 솔루션즈, 인코포레이티드 캐스코드 전류 스티어링을 통해 향상된 증폭기 효율
KR102579277B1 (ko) * 2015-02-15 2023-09-14 스카이워크스 솔루션즈, 인코포레이티드 강화된 열적 견고성을 위해 스태거형 캐스코드 레이아웃을 갖는 전력 증폭기
KR102603312B1 (ko) * 2015-02-15 2023-11-17 스카이워크스 솔루션즈, 인코포레이티드 감소된 크기를 갖는 도허티 전력 증폭기

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US20130016795A1 (en) 2013-01-17

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