WO2011040283A1 - モータ制御装置 - Google Patents
モータ制御装置 Download PDFInfo
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- WO2011040283A1 WO2011040283A1 PCT/JP2010/066304 JP2010066304W WO2011040283A1 WO 2011040283 A1 WO2011040283 A1 WO 2011040283A1 JP 2010066304 W JP2010066304 W JP 2010066304W WO 2011040283 A1 WO2011040283 A1 WO 2011040283A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/10—Arrangements for controlling torque ripple, e.g. providing reduced torque ripple
Definitions
- the present invention relates to a motor control device, for example, a motor control device capable of driving a synchronous motor having a plurality of coils without using a sensor.
- Patent Document 1 detects a motor voltage phase at the time of motor current zero crossing, detects a motor current phase based on this voltage phase, and detects the motor current phase. A method of calculating a voltage command or a frequency command so that the current phase becomes a desired current phase is shown.
- FIG. 10 shows a configuration of a conventional general motor control device.
- an inverter device in order to drive synchronous motor 100 having a plurality of (three-phase) coils in a stator and a permanent magnet in a rotor, an inverter device includes an inverter 150, a converter circuit 130, an AC power supply 160, A coil 170, a current sensor 180, and a controller 110 are included.
- the AC power supply 160 is 200 V and 50 Hz.
- the synchronous motor 100 is driven by an inverter 150, and a DC voltage obtained by converting an AC power supply 160 into a DC voltage from a converter circuit 130 is applied to the inverter 150.
- converter circuit 130 includes a diode full-wave rectifier circuit 120 formed of diodes 122 to 128 and a smoothing capacitor 140 between buses, and the capacitance of the smoothing capacitor can improve the ripple of the DC voltage waveform. Large enough.
- the converter circuit 130 converts the AC voltage of the AC power supply 160 into a DC voltage and supplies it to the inverter 150.
- the coil 170 is provided for the purpose of improving the power factor of the AC power supplied to the converter circuit 130.
- FIG. 11 is a diagram for explaining the relationship between the waveform of the DC voltage and the U-phase motor current. As shown in FIG. 11A, when the capacity of the smoothing capacitor 140 is sufficiently large, the ripple of the DC voltage waveform is improved and a constant DC voltage is supplied to the inverter 150.
- FIG. 11B is a diagram for explaining the U-phase motor current waveform detected by the current sensor 180.
- the ripple of the DC voltage waveform is improved and a constant DC voltage is supplied to the inverter 150, the U-phase motor current that drives the synchronous motor 100 from the inverter 150 has a constant amplitude. It is detected as a stable waveform.
- Patent Document 2 Japanese Patent Laid-Open No. 2002-51589
- Patent Document 2 Japanese Patent Laid-Open No. 2002-51589
- a ripple with a frequency twice that of the power supply is intentionally generated in the DC voltage.
- a method for improving the input current waveform and increasing the power factor has been proposed.
- the output frequency of the inverter when the rotational speed of the motor is 2800 rpm is 93.3 Hz because it is a 4-pole motor.
- the inverter frequency approaches the ripple frequency of the DC voltage, a large pulsation occurs in the motor current on the inverter output side as shown in FIG. 12B, and the rotation of the motor becomes unstable. Vibration, noise increase, efficiency deteriorates, and in the worst case, step-out is stopped.
- the present invention has been made to solve the above problems, and provides a motor control device capable of position sensorless sinusoidal energization that ensures stability even when the ripple of the DC voltage is large. It is.
- a motor control device is connected to a rectifier circuit that receives a single-phase AC power source and a rectifier circuit, converts DC power obtained by the rectifier circuit into three-phase AC power, and drives the motor.
- the controller includes a rotation speed setting means for setting the rotation speed of the motor, and a rotation for correcting the rotation speed of the motor set by the rotation speed setting means in accordance with an elapsed time from the detection of the zero cross point of the zero cross point detection circuit. Number correction means.
- the rotation speed correction means corrects the target rotation speed based on a correction rate in a correction rate data table defined in advance according to an elapsed time from the detection of the zero cross point.
- the correction factor is defined as a value at which the sum of the correction factors defined in the correction factor data table for the target rotational speed is approximately zero.
- a correction rate data table is provided for each target rotational speed.
- the motor control device of the present invention is provided with a rotation speed correction means for correcting the rotation speed of the motor set by the rotation speed setting means in accordance with the elapsed time from the detection of the zero cross point of the zero cross point detection circuit.
- the rotational speed of the motor is corrected in accordance with the elapsed time since the detection of the zero cross point.
- FIG. 1 is used to explain a block diagram of a motor control device according to an embodiment of the present invention.
- a motor control device includes a synchronous motor 1 including a multi-phase (three-phase) coil in a stator and a permanent magnet in a rotor, an inverter 2, a converter circuit 3, an AC power supply 4, It comprises a current sensor 5, a motor current detection amplifier 6, a zero cross detection unit 30, a voltage sensor 32, and a controller 7 which is a microcomputer.
- the synchronous motor 1 is driven by an inverter 2, and the AC voltage of the AC power supply 4 from the converter circuit 3 is converted into DC and given to the inverter 2.
- the converter circuit 3 includes a plurality of diodes 22 to 28, and a full-wave rectifier circuit 20 is formed.
- a small-capacitance capacitor 40 is provided between the buses.
- the small capacitor 40 is 100 ⁇ F or less.
- a capacitor of about 10 to 20 ⁇ F can be used in consideration of prevention of breakdown of the semiconductor element of the inverter 2 due to regenerative energy of the synchronous motor 1 on the load side.
- the current sensor 5 detects a motor current a flowing in a specific phase (U phase in FIG. 1) among the motor coil terminals U, V, and W.
- the motor current detected by the current sensor 5 is given to the motor current detection amplifier 6.
- the motor current detection amplifier 6 amplifies the motor current signal b by a predetermined amount and adds the offset to the controller 7.
- the voltage sensor 32 detects the voltage of the AC power supply 4. The AC voltage detected by the voltage sensor 32 is given to the zero cross detector 30.
- the zero-cross detection unit 30 monitors the AC voltage detected by the voltage sensor 32, generates a zero-cross point signal when it crosses 0V, and gives it to the controller 7.
- the controller 7 includes a phase difference detection unit 8, a target phase difference information storage unit 9, an addition unit 10, a PI calculation unit 11, a rotation speed setting unit 12, a sine wave data table 13, and a sine wave data creation unit. 14, the PWM creation unit 15, the correction rate data extraction unit 16, and the rotation speed correction rate data table 17 are processed in software.
- phase control is executed by a method similar to the phase control method described in JP-A-2001-112287. This point will be described later.
- the phase difference detection unit 8 takes in and converts the motor current signal given from the motor current detection amplifier 6 by A / D conversion at a predetermined timing, and integrates each current sampling data sampled every two motor drive voltage phase periods. Then, the motor current signal area is obtained, and the area ratio of both motor current signal areas is output as phase difference information.
- Target phase difference information is stored in the target phase difference information storage unit 9. Error data between the target phase difference information and the phase difference information is calculated by the adding unit 10.
- the PI calculation unit 11 calculates proportional error data and integral error data with respect to the calculated error data and outputs a duty reference value.
- the addition unit 10 and the PI calculation unit 11 constitute a phase difference control unit.
- the rotation speed setting unit 12 sets a rotation speed command that is the target of the synchronous motor 1, and the sine wave data table 13 includes a table of a predetermined number of data.
- the rotation speed correction rate data table 17 stores correction rate data for a target rotation speed.
- the correction rate data extraction unit 16 extracts correction rate data corresponding to the elapsed time of the zero cross point signal generated by the zero cross detection unit 30 from the rotation rate correction rate data table, and outputs the correction rate data to the correction rotation rate generation unit 18.
- the corrected rotation speed generation unit 18 corrects the rotation speed set by the rotation speed setting unit 12 in accordance with the correction rate data extracted by the correction rate data extraction unit 16, and outputs the corrected rotation speed to the sine wave data creation unit 14.
- the sine wave data creation unit 14 reads out sine wave data corresponding to each phase of the motor coil terminals U, V, and W from the sine wave data table 13 according to the rotation speed command output from the correction rotation speed generation unit 18 and the passage of time. At the same time, the U-phase motor drive voltage phase information c is output from the U-phase sine wave data.
- the PWM generator 15 outputs a PWM waveform to the drive element of the inverter 2 for each phase from the sine wave data and the duty reference value.
- the current sensor 5 may be a so-called current sensor composed of a coil and a Hall element, or a current transformer.
- the sine wave data may be created by calculation instead of being created based on the sine wave data table 13.
- constituent elements of the constituent elements 8 to 17 are processed by the controller 7 in a software manner, the present invention is not limited to this and may be configured as a hardware configuration as long as the same processing is performed.
- the motor drive waveform is a sine wave
- a smooth motor current can be supplied by using a sine waveform, so that vibration and noise can be reduced.
- the present invention is not limited to this, and if a drive waveform that provides a motor current that matches the magnetic flux of the motor rotor is energized, a more efficient drive is possible.
- the area ratio of the two motor current signal areas detected in the two motor drive voltage phase periods is calculated by the phase difference detector 8, and this result is used as phase difference information.
- the PI calculation unit 11 performs a PI calculation on the error amount between the phase difference information and the target phase difference information, and the PWM generation unit 15 determines the output from the duty reference value and the sine wave data separately obtained from the rotation command.
- the synchronous motor 1 is driven by calculating the output duty ratio in each case, creating a PWM signal, and applying it to the motor coil via the inverter 2.
- the magnitude of the drive voltage (duty width of the PWM duty) is determined by a phase difference control feedback loop for controlling the motor current phase difference with respect to the motor drive voltage (output duty) to be constant, and the synchronous motor 1 is rotated in a desired rotation.
- the number of rotations is determined by sine wave data output at a desired frequency in order to rotate the number.
- the motor can be driven and controlled with a desired phase difference and a desired rotation speed.
- each phase is forcibly energized, a rotating magnetic field is applied, forced excitation is performed, and control is performed by the above method during normal driving.
- the synchronous motor can be driven and controlled by the phase difference control of the present invention.
- phase difference control method of the present invention will be described first with respect to the phase difference control method.
- the U-phase motor current a has a substantially sinusoidal waveform centered on the 0 level.
- the motor current a is amplified by the motor current detection amplifier 6 and is offset to create a motor current signal b. This is performed to adjust the motor current a to a convertible voltage range (for example, 0 to +5 V) of the A / D converter built in the controller 7.
- the U-phase motor drive voltage phase information c is created from the U-phase sine wave data by the sine wave data creation unit 14.
- the motor drive voltage phase information c does not actually need to be a sine wave waveform, and only the phase information needs to be known.
- the motor current signal b as shown in FIG. 2 (b) and the motor drive voltage phase information c shown in FIG. 2 (c) are input to the phase difference detector 8.
- the phase difference detection unit 8 samples the motor current signal b in a predetermined phase period ⁇ 0, ⁇ 1 determined in advance from the motor drive voltage phase information c by n at a predetermined sampling phase (sampling timing) s0 to s3 per phase period. 2 times (in the case of FIG. 2), the motor current signal areas in the respective phase periods ⁇ 0 and ⁇ 1 are IS0 and IS1, respectively, and sampled and current sampling data are integrated.
- FIG. 3 is a flowchart illustrating a phase difference detection routine for detecting phase difference information in the controller 7.
- FIG. 3 is a flowchart for explaining a sampling start routine (timer interrupt routine) for detecting whether the sampling timing has arrived or not by using a timer value or the like and starting sampling.
- a sampling start routine timer interrupt routine
- step S2 the sampling timing of sampling phase s0 is set as an interrupt value for the sampling start routine from the motor rotation speed and timer count cycle, and each variable such as sampling count n is initialized. Turn into. This is performed only once immediately after the start of motor rotation, immediately after the phase period ⁇ 0 or before the phase period ⁇ 0, and subsequent sampling timing setting is performed in the sampling start routine.
- Step S4 and subsequent steps are loop processing, and after step S2, the loop processing is repeated until the detection of the phase difference information is completed, and the loop processing is performed again in the next phase period ⁇ 0.
- the phase difference detector 8 detects whether the sampling commanded to start in the sampling start routine has ended. If completed, the process proceeds to step S8. If not completed, the following processing is performed. However, since loop processing is being performed, it is continuously detected whether sampling has ended.
- the current sampling value is read (step S8).
- the phase difference detection unit 8 reads the sampling value of the current output from the motor current detection amplifier 6.
- the sampling count is updated once in step S12. Specifically, the subsequent processing is executed in the phase difference detection unit 8.
- step S14 it is determined whether the current phase period is ⁇ 0 or ⁇ 1, and the processing of step S16 or S22 is performed depending on the determination result. This determination may be made based on the number of samplings n.
- step S16 or S22 it is determined whether the number of times of sampling has reached a predetermined number (2 times or 4 times). If the number of times of sampling is a predetermined number of times (2 times or 4 times), the process of step S18 or S24 is performed.
- step S18 or S24 the sampling of the current sampling data is performed (I0 + I1, I2 + I3), and the motor current signal area Is0 or Is1 is calculated, assuming that sampling in each phase period has ended.
- step S20 it is determined whether the calculation of both the motor current signal areas Is0 and Is1 is completed. If not completed, the process returns to the loop processing.
- step S26 assuming that the calculation of the motor current signal areas Is0 and Is1 has been completed, the ratio (Is0 / Is1) of both area data is calculated and used as phase difference information.
- phase difference information is stored (step S28). Then, a series of phase difference detection routines (loop processing) ends.
- step S6 determines whether the motor voltage is less than the predetermined voltage (NO in step S6). If it is determined in step S6 that the motor voltage is less than the predetermined voltage (NO in step S6), then the current sampling value is invalidated (step S9). Then, the processing of the phase difference detection routine ends.
- the motor voltage is less than a predetermined voltage, the amplitude of the motor current is small and the influence of the error is large. Therefore, since phase control with high accuracy is difficult with the phase difference information using the sampling value of the motor current having a large influence of error, the processing of the phase difference detection routine is terminated. In this case, phase control is executed based on the stored phase difference information. That is, the phase difference information is not updated, and phase control based on the updated phase difference information is executed when the motor voltage is equal to or higher than a predetermined voltage in the next phase difference detection routine.
- sampling start routine timer interrupt routine
- step S40 sampling is started in accordance with the sampling phase in which the next sampling timing is determined in advance. Set as interrupt value for routine.
- step S42 the A / D converter is instructed to start current sampling, and the process ends.
- the next sampling timing is set in the sampling start routine processing because the current timer count value is known ( ⁇ the current timer interrupt value) and the current motor voltage phase is known. In this way, it is not necessary to refer to the timer count value and the motor voltage phase again, and efficient processing becomes possible.
- the current timer interrupt value and the current sampling phase are values at the time of occurrence of the interrupt, and are slightly different from the timer count value and the motor voltage phase at the time of performing step S40. End up. Therefore, it is desirable to refer to the timer count value and the motor voltage phase each time a strict sampling timing needs to be set.
- the sampling timing of the motor current can be arbitrarily determined by setting a timer interrupt value to a predetermined value each time from the motor rotation speed and the timer cycle according to a predetermined sampling phase.
- the setting method is as follows. For example, when the motor rotates once in two cycles of sine wave, and sampling is started when the motor rotation speed is 3000 rpm and the motor voltage phase is 30 °, the motor voltage phase is 0 °. If the current sampling timer count resolution is 1 ⁇ sec, the time until the motor voltage phase changes from 0 ° to 30 ° is 10 msec for one cycle of the sine wave.
- each sampling timing is always sampled at the same phase of the motor voltage, and one rotor stator relative position or one phase difference information There is no problem as long as the driving voltage (output duty) can be obtained.
- the phase is symmetrical about the motor voltage phase 90 ° (the phase from the phase 90 ° to each sampling timing is the same at the sampling timing in each phase period).
- the phase of the motor current signal is detected as the same value
- current sampling in each phase period facilitates the phase difference control design.
- phase periods of the motor voltage phase need not be gathered.
- the integrated value of I0 and I5 is the motor current signal area of the first phase period
- the integrated value of I2 and I7 is the second value. It may be divided from the motor current signal area of the phase period, which can be determined from the margin of the processing time of the control system.
- phase difference detection after detecting the phase difference information (Is0 / Is1) in the phase periods ⁇ 0 and ⁇ 1 is faster by calculating the phase difference information (Is2 / Is1) using the phase periods ⁇ 1 and ⁇ 2. It is possible to detect the phase difference information.
- FIG. 5 is a waveform diagram of the motor current signal b and the motor drive voltage phase information c.
- a large ripple may occur in the DC voltage as described with reference to FIG.
- the AC power supply 4 is 200 V and the frequency is 50 Hz.
- the motor rotational speed command value (the rotational speed before correction) is 2800 rpm.
- the output frequency of the inverter is 93.3 Hz because it is a 4-pole motor.
- FIG. 6 (b) shows a DC voltage waveform with respect to the AC voltage waveform of FIG. 6 (a).
- a large ripple is generated in the DC voltage waveform. That is, a ripple with a frequency of 100 Hz that is twice that of the AC power supply occurs.
- FIG. 6C shows a zero cross point signal corresponding to the AC voltage waveform shown in FIG.
- the zero cross detection unit 30 monitors the AC power supply 4 and outputs a zero cross point signal in which the AC voltage crosses 0 in the AC voltage waveform.
- the time when the rising edge of the zero cross point signal occurs is set to 0, and the elapsed time from this time is measured by the controller 7 which is a microcomputer.
- the correction factor data extraction unit 16 reads the rotation number correction factor data table 17 and extracts correction factor data according to the passage of time. Then, the extracted correction rate data is output to the correction rotation speed generation unit 18.
- the corrected rotational speed generation unit 18 outputs the target rotational speed set by the rotational speed setting unit 12 to the sine wave data generation unit 14 as a target rotational speed obtained by correcting the value calculated by multiplying the correction rate data. .
- FIG. 7 shows the numerical values of the rotation speed correction rate data table according to the embodiment of the present invention.
- a numerical value every 0.2 ms is shown with 10 ms as one cycle.
- the numerical values in the rotation speed correction rate data table are obtained in advance by experiments to reduce the pulsation of the motor current so that the motor can be driven stably.
- FIG. 6D is a rotation speed correction rate data line based on the correction rate data of FIG. 7 with 0% as a reference.
- the rotation speed correction rate data line is a data line that matches the DC voltage waveform, and is set so that the rotation speed correction rate is maximized in the case of the zero cross point.
- the rotation speed before correction is 2800 rpm and the elapsed time is 5.0 ms
- the output frequency of the inverter at the rotation speed of 1999 rpm is a 4-pole motor, it is 66.63 Hz. Therefore, the frequency of the inverter is set to a value far away from the frequency (100 Hz) of the DC voltage ripple.
- the zero cross point is detected, the correction rate data when the DC voltage drops to 0 V at the zero cross point is maximized, and the value is far away from the frequency of the DC voltage ripple.
- FIG. 8 is a diagram showing the relationship between the DC voltage waveform and the U-phase motor current in the embodiment of the present invention using FIG.
- FIG. 8 (a) a large ripple is generated in the DC voltage as shown in FIG. 12 (a).
- FIG. 8 (a) By correcting the target rotational speed according to the method described above, FIG. ), The pulsation of the motor current can be greatly reduced.
- the case where the current value of the U-phase motor current is within the range of ⁇ 10A to 10A is shown.
- FIG. 6E shows the relationship between the rotation speed before correction and the rotation speed after correction.
- the rotation speed correction rate data table shown in FIG. 7 is set so that the average value of the correction rate data is approximately zero. Specifically, in the vicinity of the zero cross point, while reducing the rotational speed, increasing the rotational speed in a period away from the zero cross point, the average rotational speed (average value of the corrected rotational speed) and the motor rotational speed command The difference in value (rotation speed before correction) can be almost eliminated.
- one rotation number correction rate data table has been described as an example.
- a rotation number correction rate data table may be provided according to the target rotation number.
- FIG. 9 shows a plurality of rotation speed correction rate data tables that can be changed according to the motor rotation speed command value (rotation speed before correction).
- the range of the correction factor data can be reduced. is there.
- the values of the rotation speed correction rate data table described above can be determined by conducting experiments in advance so that the motor current fluctuations can be reduced and the motor can be driven stably.
- a coil is not used as in the conventional configuration, and a capacitor having a small capacity of about 1/100 of a conventional smoothing capacitor can be used between the buses of the inverter. Even under the condition that a large ripple is generated in the DC voltage, stable driving of the motor can be realized, vibration and noise can be reduced, and deterioration of efficiency can be suppressed. In addition, the motor output can be controlled with high accuracy.
- the rotor position is detected in motor drive by 180 degree energization including low noise, low vibration and high efficiency sinusoidal energization. Therefore, it is possible to perform stable rotation without using a sensor.
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Abstract
Description
図10を参照して、ステータに複数相(3相)のコイル、ロータに永久磁石を備えた同期モータ100を駆動するために、インバータ装置は、インバータ150とコンバータ回路130と交流電源160と、コイル170と、電流センサ180と、コントローラ110とから構成されている。なお、本例においては、交流電源160は、200V、50Hzであるものとする。
図11(a)に示されるように、平滑コンデンサ140の容量が十分大きい場合には、直流電圧波形のリプルが改善されて、一定の直流電圧がインバータ150に供給される。
好ましくは、回転数補正手段は、ゼロクロス点の検出からの経過時間に従って予め規定された補正率データテーブルの補正率に基づいて目標回転数を補正する。
図2(a)を参照して、U相のモータ電流aは0レベルを中心としたほぼ正弦波状の波形とする。このモータ電流aをモータ電流検出アンプ6によって増幅し、オフセット設定してモータ電流信号bを作成する。これはモータ電流aをコントローラ7に内蔵されているA/D変換器の変換可能電圧範囲(たとえば0~+5V)に合せるために行なわれる。
Is0=I0+I1
Is1=I2+I3
そして、各モータ電流信号面積Is0,Is1の比を計算してこれを位相差情報とする。
このように、サンプリング開始ルーチンの処理の中で次回のサンプリングタイミングの設定を行なうのは、現在のタイマカウント値がわかっている(≒今回のタイマ割込値)、現在のモータ電圧位相がわかっている(≒今回のサンプリング位相)ためであり、このようにすることで改めてタイマカウント値、モータ電圧位相を参照する必要がなくなり、効率的な処理が可能となる。
0.01[s]*30[°]/360[°]=833[μsec]
であり、電流サンプリングタイマのカウントとしては、
833[μsec]/1[μsec/カウント]=833[カウント]
となる。つまり、モータ電圧位相0°のときのタイマのカウント値に833を加算し、これをタイマ割込値とすれば、モータ電圧位相30°でタイマ割込が発生して電流のサンプリングが開始される。なお、前述のようにモータ回転数は正弦波データの周期によって決まる、つまりコントローラ7側で決まるものであるので、正確なモータ電圧位相でのサンプリングが可能となる。
図5において、モータ駆動電圧位相情報cに基づく所定の位相期間θ0,θ1間でのサンプリング回数はそれぞれ3回としている。ここで注目すべきは、各位相期間内での電流サンプリングタイミングを同じ値のサンプリング期間θs=aにしている、つまり同じ間隔でサンプリングを行なうことである。
当該回転数補正率データテーブルの数値は、モータ電流の脈動を低減し、モータが安定して駆動できる値を予め実験により求めたものである。
また、経過時間10msすなわち0msの場合には、図7より補正率データが-31.83%であるため回転数補正値は、2800rpm×(-31.83%)=約-891rpmとなる。
ここで、回転数1999rpm時のインバータの出力周波数は4極モータであるため、66.63Hzとなる。したがって、インバータの周波数は直流電圧のリプルの周波数(100Hz)よりもかなり離れた値に設定される。
ここで、図7に示す回転数補正率データテーブルは、補正率データの平均値が概ね0となるように設定する。具体的には、ゼロクロス点近傍においては、回転数を下げる一方、ゼロクロス点から離れている期間において回転数を上げることにより、平均回転数(補正後回転数の平均値)とモータの回転数指令値(補正前回転数)の差を概ね無くすことができる。
Claims (5)
- 単相交流電源を入力とする整流回路(20)と、
前記整流回路と接続され、前記整流回路で得られた直流電力を三相交流電力に変換して、モータ(1)を駆動するインバータ(2)と、
前記インバータを制御する制御装置(7)と、
前記単相交流電源のゼロクロス点を検出するゼロクロス点検出回路(30)とを備え、
前記制御装置(7)は、
前記モータの回転数を設定する回転数設定手段(12)と、
前記ゼロクロス点検出回路の前記ゼロクロス点の検出からの経過時間に応じて、前記回転数設定手段により設定される前記モータの回転数を補正する回転数補正手段(18)とを含む、モータ制御装置。 - 前記インバータの母線間には極めて小容量のコンデンサ(40)を接続する、請求の範囲1に記載のモータ制御装置。
- 前記回転数補正手段は、前記ゼロクロス点の検出からの経過時間に従って予め規定された補正率データテーブルの補正率に基づいて目標回転数を補正する、請求の範囲1または2に記載のモータ制御装置。
- 前記補正率は、前記目標回転数に対する前記補正率データテーブルに規定された補正率の合計が概ね0となる値に規定される、請求の範囲3記載のモータ制御装置。
- 前記補正率データテーブルは、目標回転数毎に設けられる、請求の範囲3または4記載のモータ制御装置。
Priority Applications (5)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
CA2774843A CA2774843C (en) | 2009-09-29 | 2010-09-21 | Motor control device |
EP10820402A EP2485387A1 (en) | 2009-09-29 | 2010-09-21 | Motor control device |
CN201080043587.4A CN102577083B (zh) | 2009-09-29 | 2010-09-21 | 电动机控制装置 |
US13/498,534 US8704471B2 (en) | 2009-09-29 | 2010-09-21 | Motor control device |
EG2012030555A EG26851A (en) | 2009-09-29 | 2012-03-27 | Engine control device |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
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JP2009224339A JP4678699B2 (ja) | 2009-09-29 | 2009-09-29 | モータ制御装置 |
JP2009-224339 | 2009-09-29 |
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WO2011040283A1 true WO2011040283A1 (ja) | 2011-04-07 |
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PCT/JP2010/066304 WO2011040283A1 (ja) | 2009-09-29 | 2010-09-21 | モータ制御装置 |
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US (1) | US8704471B2 (ja) |
EP (1) | EP2485387A1 (ja) |
JP (1) | JP4678699B2 (ja) |
CN (1) | CN102577083B (ja) |
CA (1) | CA2774843C (ja) |
EG (1) | EG26851A (ja) |
MY (1) | MY155807A (ja) |
WO (1) | WO2011040283A1 (ja) |
Families Citing this family (15)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP5292363B2 (ja) * | 2010-06-30 | 2013-09-18 | 株式会社日立製作所 | 交流電動機の制御装置及び制御方法 |
KR101251509B1 (ko) * | 2010-12-01 | 2013-04-05 | 기아자동차주식회사 | 하이브리드 자동차의 고장진단장치 및 방법 |
JP5875265B2 (ja) * | 2011-07-04 | 2016-03-02 | キヤノン株式会社 | ステッピングモータの駆動制御装置および駆動制御方法、駆動制御システムならびに光学機器 |
JP5648654B2 (ja) * | 2012-04-23 | 2015-01-07 | 株式会社デンソー | 回転機の制御装置 |
CN103580557B (zh) * | 2012-08-06 | 2017-05-03 | 台达电子工业股份有限公司 | 用以撷取反应电动势的撷取系统及撷取方法 |
KR101397785B1 (ko) * | 2012-12-17 | 2014-05-20 | 삼성전기주식회사 | 모터 구동 장치 및 방법 |
DE102014217005A1 (de) * | 2014-08-26 | 2016-03-03 | BSH Hausgeräte GmbH | Verfahren zum Bremsen eines Verdichters und Verdichter eines Kältegerätes, Klimageräts oder einer Wärmepumpe sowie Kältegerätes, Klimageräts oder Wärmepumpe damit |
TWI551027B (zh) * | 2014-10-01 | 2016-09-21 | de-san Chen | Motor control circuit system |
CN105743408B (zh) * | 2014-12-12 | 2018-06-26 | 陈德三 | 马达的控制电路系统 |
CN107508513B (zh) * | 2015-07-06 | 2020-03-06 | 湖南工业大学 | 一种单相电源线发送步进电机调速信号的方法 |
CN106026729A (zh) * | 2016-08-07 | 2016-10-12 | 黎辉 | 一种交流电机隔离驱动电源装置 |
US10218234B2 (en) | 2016-12-02 | 2019-02-26 | Rockwell Automation Technologies, Inc. | Electric motor with asymmetric design for improved operation |
CN106787994B (zh) * | 2016-12-23 | 2019-04-09 | 峰岹科技(深圳)有限公司 | 无刷直流电机的速度检测电路及其方法 |
CN112040624B (zh) * | 2019-06-04 | 2023-08-22 | 合肥美亚光电技术股份有限公司 | X射线管的控制系统及方法、x射线成像设备 |
CN110231512B (zh) * | 2019-07-04 | 2024-06-14 | 深圳曼顿科技有限公司 | 单火线电能计量装置 |
Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH05236789A (ja) | 1992-02-19 | 1993-09-10 | Daikin Ind Ltd | ブラシレスdcモータの駆動装置 |
JPH09264260A (ja) * | 1996-03-29 | 1997-10-07 | Mitsubishi Electric Corp | 送風機の制御装置、及び温風暖房機の制御装置 |
JP2001112287A (ja) | 1999-08-05 | 2001-04-20 | Sharp Corp | モータ制御装置 |
JP2002051589A (ja) | 2000-07-31 | 2002-02-15 | Isao Takahashi | モータ駆動用インバータの制御装置 |
JP2004180489A (ja) * | 2002-11-15 | 2004-06-24 | Daikin Ind Ltd | ブラシレスdcモータ制御方法およびその装置 |
Family Cites Families (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DE19843106B4 (de) * | 1998-09-21 | 2005-08-18 | Ebm-Papst Mulfingen Gmbh & Co. Kg | System zur Drehzahlsteuerung von Wechselstrom-Motoren |
DE10037972B4 (de) | 1999-08-05 | 2005-09-15 | Sharp K.K. | Vorrichtung und Verfahren zur Elektromotorsteuerung |
JP4614382B2 (ja) * | 2004-10-29 | 2011-01-19 | キヤノン株式会社 | 電力供給装置及び加熱装置及び画像形成装置 |
US7723964B2 (en) * | 2004-12-15 | 2010-05-25 | Fujitsu General Limited | Power supply device |
US8823303B2 (en) * | 2008-12-01 | 2014-09-02 | Mitsubishi Electric Corporation | Alternating-current direct-current converter and electric motor driver |
JP5424663B2 (ja) * | 2009-01-30 | 2014-02-26 | キヤノン株式会社 | 電源装置及び画像形成装置 |
JP2010288331A (ja) | 2009-06-09 | 2010-12-24 | Sharp Corp | インバータ装置 |
-
2009
- 2009-09-29 JP JP2009224339A patent/JP4678699B2/ja not_active Expired - Fee Related
-
2010
- 2010-09-21 US US13/498,534 patent/US8704471B2/en not_active Expired - Fee Related
- 2010-09-21 MY MYPI2012001388A patent/MY155807A/en unknown
- 2010-09-21 WO PCT/JP2010/066304 patent/WO2011040283A1/ja active Application Filing
- 2010-09-21 EP EP10820402A patent/EP2485387A1/en not_active Withdrawn
- 2010-09-21 CA CA2774843A patent/CA2774843C/en not_active Expired - Fee Related
- 2010-09-21 CN CN201080043587.4A patent/CN102577083B/zh not_active Expired - Fee Related
-
2012
- 2012-03-27 EG EG2012030555A patent/EG26851A/en active
Patent Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPH05236789A (ja) | 1992-02-19 | 1993-09-10 | Daikin Ind Ltd | ブラシレスdcモータの駆動装置 |
JPH09264260A (ja) * | 1996-03-29 | 1997-10-07 | Mitsubishi Electric Corp | 送風機の制御装置、及び温風暖房機の制御装置 |
JP2001112287A (ja) | 1999-08-05 | 2001-04-20 | Sharp Corp | モータ制御装置 |
JP2002051589A (ja) | 2000-07-31 | 2002-02-15 | Isao Takahashi | モータ駆動用インバータの制御装置 |
JP2004180489A (ja) * | 2002-11-15 | 2004-06-24 | Daikin Ind Ltd | ブラシレスdcモータ制御方法およびその装置 |
Also Published As
Publication number | Publication date |
---|---|
JP4678699B2 (ja) | 2011-04-27 |
CN102577083B (zh) | 2014-11-26 |
CA2774843C (en) | 2015-05-19 |
MY155807A (en) | 2015-11-30 |
EG26851A (en) | 2014-10-30 |
US20120181960A1 (en) | 2012-07-19 |
CA2774843A1 (en) | 2011-04-07 |
US8704471B2 (en) | 2014-04-22 |
CN102577083A (zh) | 2012-07-11 |
EP2485387A1 (en) | 2012-08-08 |
JP2011078153A (ja) | 2011-04-14 |
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