WO2010058617A1 - Débitmètre-masse à effet de coriolis - Google Patents

Débitmètre-masse à effet de coriolis Download PDF

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Publication number
WO2010058617A1
WO2010058617A1 PCT/JP2009/060720 JP2009060720W WO2010058617A1 WO 2010058617 A1 WO2010058617 A1 WO 2010058617A1 JP 2009060720 W JP2009060720 W JP 2009060720W WO 2010058617 A1 WO2010058617 A1 WO 2010058617A1
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Prior art keywords
output
phase
signal
converter
data
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PCT/JP2009/060720
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English (en)
Japanese (ja)
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嶋田英樹
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株式会社オーバル
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Application filed by 株式会社オーバル filed Critical 株式会社オーバル
Priority to US12/746,874 priority Critical patent/US8442781B2/en
Priority to CN2009801006286A priority patent/CN101910804B/zh
Priority to EP09827398.0A priority patent/EP2256467B1/fr
Priority to KR1020107009698A priority patent/KR101163888B1/ko
Publication of WO2010058617A1 publication Critical patent/WO2010058617A1/fr

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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01F—MEASURING VOLUME, VOLUME FLOW, MASS FLOW OR LIQUID LEVEL; METERING BY VOLUME
    • G01F1/00—Measuring the volume flow or mass flow of fluid or fluent solid material wherein the fluid passes through a meter in a continuous flow
    • G01F1/76—Devices for measuring mass flow of a fluid or a fluent solid material
    • G01F1/78—Direct mass flowmeters
    • G01F1/80—Direct mass flowmeters operating by measuring pressure, force, momentum, or frequency of a fluid flow to which a rotational movement has been imparted
    • G01F1/84—Coriolis or gyroscopic mass flowmeters
    • G01F1/845—Coriolis or gyroscopic mass flowmeters arrangements of measuring means, e.g., of measuring conduits
    • G01F1/8468—Coriolis or gyroscopic mass flowmeters arrangements of measuring means, e.g., of measuring conduits vibrating measuring conduits
    • G01F1/8472—Coriolis or gyroscopic mass flowmeters arrangements of measuring means, e.g., of measuring conduits vibrating measuring conduits having curved measuring conduits, i.e. whereby the measuring conduits' curved center line lies within a plane
    • G01F1/8477—Coriolis or gyroscopic mass flowmeters arrangements of measuring means, e.g., of measuring conduits vibrating measuring conduits having curved measuring conduits, i.e. whereby the measuring conduits' curved center line lies within a plane with multiple measuring conduits
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01F—MEASURING VOLUME, VOLUME FLOW, MASS FLOW OR LIQUID LEVEL; METERING BY VOLUME
    • G01F1/00—Measuring the volume flow or mass flow of fluid or fluent solid material wherein the fluid passes through a meter in a continuous flow
    • G01F1/76—Devices for measuring mass flow of a fluid or a fluent solid material
    • G01F1/78—Direct mass flowmeters
    • G01F1/80—Direct mass flowmeters operating by measuring pressure, force, momentum, or frequency of a fluid flow to which a rotational movement has been imparted
    • G01F1/84—Coriolis or gyroscopic mass flowmeters
    • G01F1/8409—Coriolis or gyroscopic mass flowmeters constructional details
    • G01F1/8431—Coriolis or gyroscopic mass flowmeters constructional details electronic circuits
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01F—MEASURING VOLUME, VOLUME FLOW, MASS FLOW OR LIQUID LEVEL; METERING BY VOLUME
    • G01F1/00—Measuring the volume flow or mass flow of fluid or fluent solid material wherein the fluid passes through a meter in a continuous flow
    • G01F1/76—Devices for measuring mass flow of a fluid or a fluent solid material
    • G01F1/78—Direct mass flowmeters
    • G01F1/80—Direct mass flowmeters operating by measuring pressure, force, momentum, or frequency of a fluid flow to which a rotational movement has been imparted
    • G01F1/84—Coriolis or gyroscopic mass flowmeters
    • G01F1/8409—Coriolis or gyroscopic mass flowmeters constructional details
    • G01F1/8436—Coriolis or gyroscopic mass flowmeters constructional details signal processing

Definitions

  • the present invention relates to a Coriolis flowmeter that obtains a mass flow rate and / or density of a fluid to be measured by detecting a phase difference and / or vibration frequency proportional to the Coriolis force acting on the flow tube.
  • a Coriolis flowmeter supports one or both ends of a flow tube through which a fluid to be measured flows, and when vibration is applied in a direction perpendicular to the flow direction of the flow tube around the support point, This is a mass flow meter utilizing the fact that the Coriolis force acting on the flow tube to be added is called a flow tube) is proportional to the mass flow rate.
  • Coriolis flowmeters are well known, and the shape of the flow tube in the Coriolis flowmeter is roughly divided into a straight tube type and a curved tube type.
  • the Coriolis flowmeter supports the measurement tube through which the fluid to be measured flows at both ends, and when the central portion of the supported measurement tube is alternately driven in a direction perpendicular to the support line, It is a mass flow meter that detects a phase difference signal proportional to the mass flow rate at a symmetrical position with respect to the central portion.
  • the phase difference signal is an amount proportional to the mass flow rate, but if the driving frequency is constant, the phase difference signal can be detected as a time difference signal at the observation position of the measurement tube. If the frequency of the alternating drive of the measuring tube is made equal to the natural frequency of the measuring tube, a constant driving frequency corresponding to the density of the fluid to be measured can be obtained, and it is possible to drive with low driving energy.
  • the measurement tube is driven at the natural frequency, and the phase difference signal is detected as a time difference signal.
  • the straight pipe type Coriolis flowmeter is a straight pipe that is supported by the Coriolis force between the straight pipe support section and the center section when vibration is applied in the direction perpendicular to the straight pipe axis of the straight pipe center supported at both ends.
  • a displacement difference of the tube, that is, a phase difference signal is obtained, and the mass flow rate is detected based on the phase difference signal.
  • Such a straight tube type Coriolis flowmeter has a simple, compact and robust structure. However, it also has a problem that high detection sensitivity cannot be obtained.
  • the curved tube type Coriolis flow meter is superior to the straight tube type Coriolis flow meter in that it can select the shape to effectively extract the Coriolis force. Can be detected.
  • a curved tube type Coriolis flow meter one provided with one flow tube (for example, see Japanese Patent Publication No. 4-55250) or one provided with two parallel flow tubes (for example, Japanese Patent No. 2939242). (Refer to Japanese Patent Publication No. 29951651) or the like prepared in a state where a single flow tube is looped.
  • a driving means for driving the flow tube it is generally used in a combination of a coil and a magnet.
  • the coil and the magnet it is preferable to attach the coil and the magnet at a position that is not offset with respect to the vibration direction of the flow tube in order to minimize the deviation of the positional relationship between the coil and the magnet.
  • the coil and the magnet are sandwiched. Therefore, the design is made such that the distance between the two opposing flow tubes is at least as long as the coil and the magnet are sandwiched.
  • a general Coriolis flow meter 1 has a detector 4 and a transducer 5 of two U-shaped tubes 2 and 3 as shown in FIG.
  • a vibration exciter 6, a speed sensor 7, and a temperature sensor 8 are attached to the measurement tubes 2 and 3 of the detector 4, and are connected to the converter 5.
  • the Coriolis flowmeter converter 5 includes a phase measurement unit 11, a temperature measurement unit 12, and a drive control unit 13.
  • the phase measurement unit 11 is configured as follows.
  • the phase measurement 11 of the Coriolis flowmeter performs A / D conversion on the signals of the pair of speed sensors and performs digital conversion processing, and then obtains the phase difference between the converted signals.
  • a measurement method of the temperature measurement unit 12 will be described.
  • the Coriolis flow meter is provided with a temperature sensor for compensating the tube temperature. In general, a resistance type temperature sensor is used, and the temperature is calculated by measuring a resistance value.
  • the drive control unit 13 sends a signal of a predetermined mode to the vibrator 6 attached to the measurement tube so that the tubes 2 and 3 can resonate.
  • the pick-off input signal is full-wave rectified in the full-wave rectifier circuit 21 constituting the amplitude measuring unit 20, and the pick-off input signal that is full-wave rectified in the full-wave rectifying circuit 21 is low-pass constituting the amplitude measuring unit 20. Input to the filter 22.
  • the amplitude measurement unit 20 obtains the amplitude value of the input waveform of the pick-off input signal input to the low-pass filter 22.
  • the amplitude value obtained by the amplitude measurement unit 20 is subtracted from the reference voltage value Vref input to the adder 23 by the adder 23, and the pick-off input signal input to the amplitude measurement unit 20 by the multiplier 24. Multiply.
  • the input signal multiplied by the multiplier 24 is input to the drive output amplifier 25. Then, the drive output amplifier 25 outputs it as a drive signal.
  • the drive output amplifier 25 outputs it as a drive signal.
  • the amplitude value of the input signal does not reach a certain level
  • the output of the start circuit 26 is switched, the gain of the output amplifier 25 is switched, the level of the drive signal increases, and the input signal quickly converges to a certain level.
  • the drive circuit is composed of an analog circuit, so there is a merit that it is very responsive to changes in the input signal, but the following disadvantages: There is also.
  • the object of the present invention is to enable the design of a common drive circuit by digitizing the drive circuit, changing individual differences of the drive circuit itself, and drive parameters, and further incorporating the drive circuit inside the arithmetic unit.
  • An object of the present invention is to provide a Coriolis flow meter that can be incorporated and can easily realize additional functions such as cost reduction and self-diagnosis.
  • the Coriolis flowmeter of the present invention according to claim 1, which has been made to solve the above-described problems, is configured to face a pair of flow tubes constituting a flow tube for measurement, and to operate the electromagnetic oscillator by a driving device to By alternately driving in the rotational direction to vibrate the pair of flow tubes and detecting a phase difference and / or vibration frequency proportional to the Coriolis force acting on the pair of flow tubes by electromagnetic pickoff, In a Coriolis flow meter to obtain mass flow and / or density,
  • the drive device An OP amplifier for amplifying an analog input signal from the electromagnetic pickoff; An A / D converter for converting an analog signal output from the OP amplifier into a digital signal; A D / A converter that digitally processes a digital signal output from the A / D converter based on phase detection in a DSP (digital signal processor
  • the Coriolis flowmeter of the present invention comprises a DSP (digital signal processor), An amplitude measurement unit that calculates the amplitude using the spectrum intensity of the resonance frequency as an amplitude value using FFT; A zero cross calculation unit that measures how many times the sign bit of the digital data input from the A / D converter changes per unit time and outputs the value as zero cross data; A drive waveform generation unit that determines an amplitude of an output waveform based on an output from the PLL and amplitude data from the amplitude measurement unit, and generates an output waveform; A frequency calculation unit for calculating a frequency based on phase data output from the PLL; A PLL (phase synchronization circuit) that performs phase detection from output data of the zero-cross data and the A / D converter; It is characterized by comprising.
  • DSP digital signal processor
  • An amplitude measurement unit that calculates the amplitude using the spectrum intensity of the resonance frequency as an amplitude value using FFT
  • a zero cross calculation unit that measures how many times the sign bit
  • the Coriolis flowmeter of the present invention according to claim 3, which has been made to solve the above-described problem, is a PLL (phase synchronization circuit), Based on a digital signal obtained by A / D-converting an input analog signal from the electromagnetic pickoff, a drive signal for driving the coil is generated based on a transmission frequency synchronized with the input signal from a transmission frequency obtained by phase detection. It is characterized by that.
  • the Coriolis flowmeter of the present invention according to claim 4 which has been made to solve the above-mentioned problem, comprises a PLL (phase synchronization circuit) including a multiplier, a low-pass filter, and a phase control type oscillator.
  • the multiplier is configured to compare phases of a digital signal output from the A / D converter and a digital output signal output from the phase control type oscillator, and output the difference signal and a sum signal.
  • the low-pass filter is configured to extract only a low frequency signal from the output signal from the multiplier.
  • the phase control oscillator generates phase data of a basic output waveform based on zero cross data from the zero cross section, and further calculates so that output data from the low pass filter becomes 0, and the calculated phase It is characterized in that it is configured to generate and output a waveform based on the above.
  • the Coriolis flowmeter of the present invention which has been made to solve the above problem, amplifies an output signal output from an analog switch by an OP amplifier connected to an output terminal of the analog switch, and drives output
  • the circuit is configured to output as a signal, and the gain of the OP amplifier can be switched by the analog switch.
  • FIG. 1 is a diagram showing a configuration diagram of a PLL (Phase-Locked Loop).
  • FIG. 2 is a block diagram of a Coriolis flow meter drive circuit using the PLL principle shown in FIG.
  • FIG. 3 is a block diagram of a Coriolis flow meter drive circuit using the principle of a DSP (Digital Signal Processor).
  • FIG. 4 is a diagram showing a flowchart of synchronous feedback and frequency calculation.
  • FIG. 5 is a diagram showing a flowchart of drive control.
  • FIG. 6 is a configuration diagram of a general Coriolis flow meter to which the present invention is applied.
  • FIG. 7 is a diagram for explaining the operating principle of the drive circuit of the Coriolis flow meter shown in FIG.
  • PLL Phase-locked loop phase locked loop
  • FIG. 1 shows a circuit configuration diagram of a PLL (Phase-Locked Loop) 30.
  • PLL Phase-Locked Loop
  • the PLL 30 in FIG. 1 includes a phase comparator 31, a loop filter 32, a VCO (voltage control transmission circuit) 33, and a frequency divider 34.
  • the PLL 30 shown in FIG. 1 is an electronic circuit that outputs a signal having the same frequency and the same phase as the input AC signal from another oscillator by feedback control.
  • the PLL 30 is synchronized by feeding back to the VCO 33 the phase difference between the output signal of the VCO (voltage controlled oscillation circuit) 33 whose frequency changes according to the voltage and the input (reference frequency).
  • a signal obtained by multiplying the frequency of the input signal can be generated by using a frequency-divided output signal of the VCO (voltage controlled oscillation circuit) 33.
  • FIG. 2 shows a block diagram of a Coriolis flow meter drive circuit using the principle of the PLL 30.
  • the drive circuit 40 includes an OP amplifier 41, an A / D converter 42, a D / A converter 43, and an analog switch 44.
  • a pair of flow tubes constituting a flow tube for measurement are opposed to each other, an electromagnetic oscillator is operated by a driving device to alternately drive the flow tubes in the rotation direction, and a drive output signal for vibrating the pair of flow tubes is an analog switch.
  • the output signal from the D / A converter 43 and the phase difference and / or vibration frequency proportional to the Coriolis force generated in the pair of flow tubes when the flow tubes are driven alternately in the rotational direction are detected by electromagnetic pick-off.
  • the two signals of the input signal output from the OP amplifier 41 can be switched and output to the drive output amplifier 45, respectively.
  • the analog switch 44 is configured so that the gain of the drive output amplifier 45 can be switched at the same time by switching by the analog switch 44.
  • An output signal from the A / D converter 42 is input to a DSP (Digital Signal Processor) 50 connected to the A / D converter 42.
  • FIG. 3 shows a block diagram of a Coriolis flow meter drive circuit using the principle of a DSP (Digital Signal Processor).
  • a DSP (Digital Signal Processor) 50 is a microprocessor specialized in digital signal processing. Next, the internal configuration of the DSP 50 will be described.
  • the DSP 50 includes an amplitude measurement unit 51, a zero cross calculation unit 52, a drive waveform generation unit 53, a frequency calculation unit 54, and a PLL 55 (a multiplier 56, a low-pass filter 57, and a phase control type transmitter 58). ing. Each component constituting the DSP 50 will be described next.
  • Amplitude measuring unit 51 The amplitude measurement unit 51 calculates an amplitude. In the calculation of the amplitude, the spectrum intensity of the resonance frequency is used as an amplitude value by using FFT for calculation inside the amplitude measurement unit 51.
  • the zero-cross calculator 52 is configured to detect a phase difference proportional to a Coriolis force generated in the pair of flow tubes when the flow tubes detected by the electromagnetic pick-off output from the A / D converter 42 are alternately driven in the rotation direction, and / or This is to measure how many times the sign bit of the vibration frequency input data (sin ⁇ ) changes per unit time.
  • the zero cross calculator 52 sends the measured value to the phase control type transmitter 58 as zero cross data.
  • the drive waveform generation unit 53 outputs the output waveform in the drive waveform generation unit 53 based on the phase of the output waveform based on the phase data ⁇ output from the phase control type transmitter 58 and the amplitude data X MAG output from the amplitude measurement unit 51. The amplitude of the waveform is determined, and an output waveform output from the drive waveform generation unit 53 is generated.
  • Frequency calculation unit 54 The frequency calculation unit 54 calculates a vibration frequency proportional to the Coriolis force detected by the electromagnetic pick-off based on the phase data ⁇ output from the phase control type transmitter 58.
  • Multiplier 56 The multiplier 56 detects the phase difference and / or vibration frequency proportional to the Coriolis force generated in the pair of flow tubes when the flow tubes are driven alternately in the rotation direction by an electromagnetic pick-off, and amplifies them by the OP amplifier 41. Then, the input data (sin ⁇ ) converted into a digital value in the A / D converter 42 is compared with the phase of the output signal cos ⁇ output from the phase control type transmitter 58, and the low-pass filter 57 is used as the difference signal and the sum signal. Is output.
  • Low-pass filter 57 The low-pass filter 57 is a circuit that extracts only the low-frequency signal from the output signal output from the multiplier 56 through the frequency filter.
  • Phase control type transmitter 58 The phase control type oscillator 58 generates phase data ⁇ of the output waveform based on the zero cross data ( ⁇ 0 ) output from the zero cross section (zero cross calculation section 52).
  • the phase control type oscillator 58 outputs an output signal cos ⁇ to the multiplier 56, and in the multiplier 56, the phase of the input data (sin ⁇ ) converted into a digital value in the A / D converter 42, and The phase of the output signal cos ⁇ is compared, the difference signal and the sum signal are output from the low-pass filter 57, and the output data Vn of only the difference component filtered out by the low-pass filter 57 is calculated to be 0,
  • the calculated phase data ⁇ is output to the drive waveform generator 53.
  • the drive waveform generator 53 generates a waveform based on the phase data ⁇ output from the phase control type transmitter 58 and outputs the waveform to the D / A converter 43 as output data (X AMP sin ⁇ ).
  • a drive start method of a DSP (Digital Signal Processor) 50 will be described.
  • the pair of flow tubes constituting the opposing measurement flow tubes are not driven alternately by the electromagnetic oscillator, and the pair of flow tubes are not vibrating. Therefore, no input signal is input to the OP amplifier 41 of the drive circuit 40 and no output signal is output from the OP amplifier 41 of the drive circuit 40, and therefore no drive output signal is output from the amplifier 45.
  • the gain of the output amplifier 45 is switched by the analog switch 44 shown in FIG.
  • An input signal input to the A / D converter 42 output from the OP amplifier 41 is connected so as to be directly input to the amplifier 45, and is output as an output signal output from the amplifier 45, whereby initial vibration is applied to the drive coil. give.
  • the input input to the A / D converter 42 output from the OP amplifier 41 of the analog switch 44 The connection state in which the signal is directly input to the amplifier 45 is restored to the normal drive state.
  • Amplitude measurement unit 51 In the amplitude measurement unit 51, the phase difference and / or vibration frequency proportional to the Coriolis force generated in the pair of flow tubes when the flow tubes are driven alternately in the rotation direction are detected by electromagnetic pick-off. Then, the real component and the imaginary component of the input data (sin ⁇ ) amplified by the OP amplifier 41 and converted into a digital value in the A / D converter 42 are stopped by the calculation of FFT (fast Fourier transform). The amplitude value X MAG is obtained from the power spectrum of the input signal.
  • the value obtained by the zero cross calculation unit 52 is sent to the phase control type transmitter 58 as a phase ⁇ 0 as a base calculated from the zero cross data.
  • the zero cross measurement time is not limited to 0.5 sec, and may be 1 sec, for example.
  • Multiplier 56 In the multiplier 56 of the PLL 55, the phase difference and / or vibration frequency proportional to the Coriolis force generated in the pair of flow tubes when the flow tubes are alternately driven in the rotation direction is detected by an electromagnetic pick-off, and the OP amplifier 41
  • the input data (sin ⁇ ) signal amplified by the A / D converter 42 and converted into a digital value by the A / D converter 42 is multiplied by the output waveform of the output signal output from the phase control type transmitter 58.
  • the calculation (sin ⁇ ⁇ cos ⁇ ) in the multiplier 56 is [Formula 2] It is expressed.
  • phase control type transmitter 58 In this phase control type oscillator 58, when the transmission frequency is changed by the output signal Vn output from the low pass filter 57, the input frequency and the phase control type are changed according to the conditions of the approximate expressions of the expressions (3) to (4).
  • the output frequency of the transmitter is in phase as described above. However, it is necessary to increase the locking time under conditions where phase control is not established, for example, in an initial control state where anti-phase cannot be achieved or in anti-lock.
  • a sin function is applied to generate a transmission waveform, shifted by ⁇ / 2
  • the output cos ⁇ obtained by the equation (7) is input to the multiplier described above.
  • Fx and Fa represent functions for generating the amplitude and phase of the output waveform, respectively.
  • Fx in Expression (8) and Fa in Expression (9) are different functions depending on the diameter and model of the Coriolis detector.
  • step 101 the signal is amplified by the OP amplifier 41 to the multiplier 56 of the PLL 55 and converted into a digital value in the A / D converter 42.
  • Data acquisition of the converted input data (sin ⁇ ) and data acquisition of the phase data ⁇ 0 output from the zero cross measurement unit 52 to the phase control type transmitter 58 of the PLL 55 are performed.
  • the initial phase ⁇ 0 , the initial set value ⁇ n ⁇ 1 of the phase data ⁇ and the low pass filter 57 of the PLL 55 are obtained in step 102.
  • the initial phase ⁇ 0 the initial phase ⁇ 0 , the initial set value ⁇ n ⁇ 1 of the phase data ⁇ and the low pass of the PLL 55 are obtained in step 103.
  • the phase of the output signal cos ⁇ n output from the phase control type transmitter 58 to the multiplier 56 is calculated.
  • step 104 obtaining the output signal V n to be actually output from the low-pass filter 57 through a low-pass filter. That is, in the low-pass filter 57, the output data output from the multiplier 56 is passed through the low-pass filter, so that only a low frequency component is extracted and used as the output signal Vn output from the A / D converter 42.
  • the calculation can be performed at a very high speed by calculating the frequency F using the value ⁇ n at the time of the phase comparison calculation.
  • the amplitude value X MAG of the input signal to the frequency calculation unit 54 at the time of calculating the frequency F is calculated at step 106. That is, since the frequency calculation unit 54 calculates the amplitude value X MAG of the input signal at the time of calculating the frequency F, it can be determined whether or not the period is accurately taken based on the amplitude value X MAG of the input signal.
  • the calculation of the amplitude value X MAG of the input signal when calculating the frequency F is performed using FFT (Fast Fourier Transform). However, the same result can be obtained even if the moving average of the input waveform is performed.
  • step 106 When the amplitude value X MAG of the input signal to the frequency calculation unit 54 at the time of calculation of the frequency F is calculated in step 106, the process returns to step 101, and the calculation from step 101 to step 106 is repeated, so that more accurate and faster Frequency calculation can be performed.
  • the frequency (phase) converges to the input frequency by repeating the maintenance loop calculation. If the drive frequency is locked or does not converge to a frequency different from the input signal, the amplitude value calculation result will be very small, so determine whether the phase is locked or not based on the amplitude value calculation result. can do.
  • drive control processing will be described based on the flowchart shown in FIG. In FIG.
  • step 200 a DSP (Digital Signal Processor) 50 is activated to initialize the DSP 50, that is, the phase data ⁇ output from the phase-controlled oscillator 58 of the PLL 55, and the PLL 55
  • step 201 input data (sin ⁇ ) converted into a digital value in the A / D converter 42 is input to the amplitude measurement unit 51 of the DSP 50, and the span of the A / D converter 42 is input. Is calculated as to what percentage the amplitude value is.
  • phase difference and / or vibration frequency proportional to the Coriolis force generated in the pair of flow tubes when the flow tubes are driven alternately in the rotation direction are detected by an electromagnetic pick-off, amplified by the OP amplifier 41, and A
  • the input data (sin ⁇ ) converted into a digital value in the / D converter 42 is obtained by the FFT (fast Fourier transform) calculation in the amplitude measuring unit 51 and converted into a digital value in the A / D converter 42.
  • the power spectrum of the input signal is obtained.
  • step 201 the input data (sin ⁇ ) converted into a digital value in the A / D converter 42 is input to the amplitude measuring unit 51 of the DSP 50, and the amplitude value X MAG of the input data (sin ⁇ ) is converted into the A / D converter 42. It is calculated what percentage of the span is.
  • step 202 when calculating the percentage of the amplitude value X MAG of the input data (sin ⁇ ) input to the amplitude measuring unit 51 of the DSP 50 in step 201 with respect to the span of the A / D converter 42, in step 202 It is determined whether or not the amplitude value X MAG of the input data (sin ⁇ ) is 90% or more with respect to the span of the A / D converter 42.
  • step 203 If it is determined in step 202 that the amplitude value X MAG of the input data (sin ⁇ ) input to the amplitude measuring unit 51 of the DSP 50 is 90% or more with respect to the span of the A / D converter 42, in step 203, the drive The amplitude value X AMP output from the waveform generation unit 53 is set to zero. That is, the drive waveform generation unit 53 determines the amplitude of the output signal (X AMP sin ⁇ ) based on the amplitude value X MAG input from the amplitude measurement unit 51, and outputs an output signal ( X AMP sin ⁇ ).
  • step 202 it is determined that the amplitude value X MAG of the input data (sin ⁇ ) input to the amplitude measuring unit 51 of the DSP 50 is 90% or more with respect to the span of the A / D converter 42.
  • step 203 the drive waveform generating unit When the amplitude value X AMP output from 53 is set to 0, the routine proceeds to step 201.
  • step 204 If it is determined in step 204 that the amplitude value X MAG of the input data (sin ⁇ ) input to the amplitude measuring unit 51 of the DSP 50 is 10% or more with respect to the span of the A / D converter 42, the drive in step 205
  • the amplitude value X AMP output from the waveform generator 53 is calculated and determined based on the amplitude value X MAG of the input waveform (sin ⁇ ) converted into a digital value by the A / D converter 42.
  • step 204 it is determined that the amplitude value X MAG of the input data (sin ⁇ ) input to the amplitude measuring unit 51 of the DSP 50 is 10% or more with respect to the span of the A / D converter 42.
  • step 205 the drive waveform generating unit
  • the amplitude value X AMP output from 53 is calculated based on the amplitude value X MAG of the input waveform (sin ⁇ ) converted into a digital value by the A / D converter 42
  • the process proceeds to step 201.
  • step 206 when it is determined in step 206 that the amplitude value X MAG of the input data (sin ⁇ ) input to the amplitude measuring unit 51 of the DSP 50 is 5% or more with respect to the span of the A / D converter 42, in step 207, The amplitude value X AMP output from the drive waveform generator 53 is set to the maximum value.
  • the drive waveform generation unit 53 determines the amplitude of the output signal (X AMP sin ⁇ ) based on the amplitude value X MAG input from the amplitude measurement unit 51, and outputs an output signal ( X AMP sin ⁇ ).
  • step 206 it is determined that the amplitude value X MAG of the input data (sin ⁇ ) input to the amplitude measuring unit 51 of the DSP 50 is 5% or more with respect to the span of the A / D converter 42.
  • the drive waveform generating unit When the amplitude value X AMP output from 53 is set to the maximum value, the routine proceeds to step 201.
  • step 208 if the amplitude value X MAG of the input waveform (sin ⁇ ) converted into a digital value in the A / D converter 42 is small, it is determined that synchronization is not established, and the analog switch 44 of the drive circuit 40 is switched. Perform startup processing. In this way, when the amplitude width of the input waveform (sin ⁇ ) that is converted into a digital value and input by the A / D converter 42 is 90% or more with respect to the span of the A / D converter, the input may be saturated. If the amplitude value of the drive output is reduced, and the amplitude width of the drive output is increased when the input amplitude is less than 10% and 5% or more, the value is smaller than that (the magnitude of the input amplitude).
  • the determination of the amplitude value of the amplitude value is 90%, 10%, and 5%, but this is a specific example. It is preferable to select an optimum value according to the system configuration and required conditions. Further, the calculation of the amplitude value of the drive output signal output from the drive waveform generation unit 53 calculates the difference between the target value (setting value) and the amplitude value of the input waveform, calculates the drive waveform according to the difference, The drive output is controlled so that the amplitude value of the input waveform becomes the target value.
  • the Hilbert transform (90 ° shift calculation) and TAN -1 calculation can be eliminated, so that the calculation can be greatly speeded up and driven.
  • the low-pass filter is used, so that it is resistant to noise.
  • the present system can greatly increase the calculation speed. Therefore, since the feedback loop is always synchronized and the operation is performed, the frequency measurement is stable and converged to the limit. For example, in a normal measurement, the capacity can be reduced significantly compared with the case where about 100 msec is required, and the capability of 1 msec can be extracted.
  • the control function can be digitally expressed. As a result, it provides a way for drive-driven diagnostics and self-diagnosis, and it is possible to meet customer needs that are currently desired. This is a very big point of view and has the greatest advantage.

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  • Measuring Volume Flow (AREA)

Abstract

Dispositif d'excitation permettant de faire fonctionner un oscillateur électromagnétique, comprenant : un amplificateur opérationnel destiné à amplifier un signal analogique d'entrée provenant d'un détecteur électromagnétique ; un convertisseur A/N destiné à convertir le signal analogique fourni par l'amplificateur opérationnel en un signal numérique ; un convertisseur N/A destiné à soumettre le signal numérique fourni par le convertisseur A/N à un traitement numérique en fonction d'une détection de phase dans un circuit DSP, et à convertir le signal numérique en un signal analogique ; et un convertisseur N/A destiné à soumettre le signal numérique fourni par le convertisseur N/A à un traitement numérique en fonction d'une détection de phase dans le circuit DSP, et à convertir le signal numérique en un signal analogique.
PCT/JP2009/060720 2008-11-18 2009-06-05 Débitmètre-masse à effet de coriolis WO2010058617A1 (fr)

Priority Applications (4)

Application Number Priority Date Filing Date Title
US12/746,874 US8442781B2 (en) 2008-11-18 2009-06-05 Coriolis flowmeter
CN2009801006286A CN101910804B (zh) 2008-11-18 2009-06-05 科氏流量计
EP09827398.0A EP2256467B1 (fr) 2008-11-18 2009-06-05 Débitmètre à effet coriolis
KR1020107009698A KR101163888B1 (ko) 2008-11-18 2009-06-05 코리올리 유량계

Applications Claiming Priority (2)

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JP2008-294355 2008-11-18
JP2008294355A JP4469008B1 (ja) 2008-11-18 2008-11-18 コリオリ流量計

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WO2010058617A1 true WO2010058617A1 (fr) 2010-05-27

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US (1) US8442781B2 (fr)
EP (1) EP2256467B1 (fr)
JP (1) JP4469008B1 (fr)
KR (1) KR101163888B1 (fr)
CN (1) CN101910804B (fr)
WO (1) WO2010058617A1 (fr)

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JP2011109222A (ja) * 2009-11-13 2011-06-02 Sinfonia Technology Co Ltd Ａ／ｄ変換装置、制振装置及びこれらを搭載した車両
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CN102832888B (zh) * 2012-08-31 2016-05-18 太原太航科技有限公司 科氏力质量流量计驱动放大器
JP6406043B2 (ja) * 2015-02-05 2018-10-17 横河電機株式会社 測定装置の共振回路
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CN105784036B (zh) * 2016-04-06 2018-10-02 合肥工业大学 一种科氏质量流量计驱动系统中的差分式功率放大电路
CN116337191B (zh) * 2023-04-18 2024-03-15 淮阴工学院 过零检测和正交解调混合的科氏流量计相位差计算方法

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See also references of EP2256467A4

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KR20100087311A (ko) 2010-08-04
EP2256467A1 (fr) 2010-12-01
CN101910804A (zh) 2010-12-08
EP2256467B1 (fr) 2013-04-24
JP2010121996A (ja) 2010-06-03
KR101163888B1 (ko) 2012-07-09
US8442781B2 (en) 2013-05-14
CN101910804B (zh) 2012-11-07
EP2256467A4 (fr) 2010-12-29
JP4469008B1 (ja) 2010-05-26
US20100268484A1 (en) 2010-10-21

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