WO2010050086A1 - 電力変換装置 - Google Patents
電力変換装置 Download PDFInfo
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- WO2010050086A1 WO2010050086A1 PCT/JP2009/002349 JP2009002349W WO2010050086A1 WO 2010050086 A1 WO2010050086 A1 WO 2010050086A1 JP 2009002349 W JP2009002349 W JP 2009002349W WO 2010050086 A1 WO2010050086 A1 WO 2010050086A1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
- H02M7/53875—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current with analogue control of three-phase output
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
- H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
- H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
- H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
- H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
Definitions
- the present invention relates to a power conversion device that converts DC power into AC power of variable frequency and variable voltage, and in particular, a converter and its DC output voltage are input and converted to AC of variable frequency and variable voltage.
- the present invention relates to an AC-AC power converter equipped with an inverter.
- the PWM converter used for electric railway vehicles uses a single-phase AC power source between the overhead line and the rail as an AC side input via a pantograph and a transformer, and performs AC / DC conversion so that a predetermined DC voltage is obtained.
- a capacitor for smoothing the voltage is provided on the DC side of the PWM converter.
- An inverter that drives the induction motor is connected to the capacitor. The voltage of the capacitor is detected by a voltage detector, and a DC input voltage to the inverter is detected.
- a current detector is provided on the AC output side of the inverter.
- the output frequency reference of the inverter is generated by adding the rotation frequency that is the output of the rotation frequency detection means of the induction motor and the slip frequency reference that is the output of the slip frequency control by an adder.
- the output current detection value by the current detector is input by the effective current value calculating means, and the effective current value is calculated and given to the adder together with the current command value, and the slip frequency control means determines the slip frequency reference.
- the DC input voltage to the inverter is detected by the voltage detector, and only the pulsation component is extracted by the voltage pulsation detection means. Further, the DC input voltage to the inverter is input by the voltage DC component detecting means, and only the DC component is extracted.
- the pulsation rate of the DC input voltage is calculated by dividing the pulsation by the DC component
- the inverter frequency correction amount is calculated by multiplying by the inverter frequency reference in the multiplier.
- the inverter frequency is calculated by adding the inverter frequency reference amount and the inverter frequency correction amount with an adder. This inverter frequency is given to the voltage control means, and a PWM control signal is given from the PWM control circuit to the inverter. (See FIG. 1 of Patent Document 1 and its description)
- FIG. 7 of Non-Patent Document 1 describes DC power supply pulsation characteristics of a vehicle PWM converter.
- the relationship between the DC capacitor capacity and the effect of suppressing the beat phenomenon in Non-Patent Document 1, the beat rate indicating how many times the fluctuation range of the inverter output current is no beat
- the DC voltage pulsation rate ratio of DC average voltage to DC pulsation width
- the DC capacitor capacity must be set to about 30 mF or more (3750 ⁇ F per one motor) per 8 motors (output about 3000 kW).
- the pulsation rate of the DC input voltage is calculated by dividing the pulsation component by the DC component, and is multiplied by the inverter frequency reference to calculate the inverter frequency correction amount.
- the inverter frequency is adjusted according to the pulsation of the DC input voltage, thereby reducing current pulsation and torque pulsation.
- the capacity of the capacitor is determined so that the pulsation rate of the DC voltage can be reduced. There is a problem subject to the restrictions.
- the DC capacitor capacity is determined so that the pulsating component of the DC voltage is 10% or less at that frequency.
- the capacitance of the capacitor increases due to a specific frequency point at which the beat phenomenon becomes the largest.
- the present invention has been made to solve the above-described problems.
- the DC capacitor capacity of the power converter is reduced. The purpose is to make it smaller.
- a power converter includes a converter that converts AC power from an AC power source into DC power, a capacitor that stores DC power output from the converter, and DC power stored in the capacitor is converted into AC power.
- An inverter a voltage control unit for controlling the inverter so as to obtain a command value of the AC voltage output by the inverter and outputting the command value, a current measuring device for measuring the AC current output by the inverter, A pulsation detection unit for detecting a pulsation of active power output from the inverter by inputting an AC voltage command value required by the voltage control unit and an alternating current measured by the current measuring instrument, and a voltage for measuring the voltage of the capacitor A measuring instrument, and a DC voltage command unit for obtaining a command value of the voltage of the capacitor according to the frequency of the AC voltage output by the inverter; A DC voltage control unit that controls the converter so that a voltage measured by the voltage measuring instrument and a command value required by the DC voltage command unit are input and a voltage of the capacitor becomes a command
- a power converter includes a converter that converts AC power from an AC power source into DC power, a capacitor that stores DC power output from the converter, and DC power stored in the capacitor is converted into AC power.
- An inverter a voltage control unit for controlling the inverter so as to obtain a command value of the AC voltage output by the inverter and outputting the command value, a current measuring device for measuring the AC current output by the inverter, A pulsation detection unit for detecting a pulsation of active power output from the inverter by inputting an AC voltage command value required by the voltage control unit and an alternating current measured by the current measuring instrument, and a voltage for measuring the voltage of the capacitor A measuring instrument, and a DC voltage command unit for obtaining a command value of the voltage of the capacitor according to the frequency of the AC voltage output by the inverter; A DC voltage control unit that controls the converter so that a voltage measured by the voltage measuring instrument and a command value required by the DC voltage command unit are input and a voltage of the capacitor becomes a command
- the control unit is characterized in that the pulsation component output from the pulsation detection unit is input and obtains the command value of the AC voltage output from the inverter so as to suppress the pulsation component.
- the capacitor capacity of the power converter is reduced. Effect of reduction there.
- FIG. 7 (a) shows a torque waveform when the first embodiment is implemented
- FIG. 7 (b) shows a torque waveform when control for reducing torque pulsation is not performed.
- FIG. 7 (a) shows a torque waveform when the first embodiment is implemented
- FIG. 7 (b) shows a torque waveform when control for reducing torque pulsation is not performed.
- FIG. 7 (a) shows a torque waveform when the first embodiment is implemented
- FIG. 7 (b) shows a torque waveform when control for reducing torque pulsation is not performed.
- FIG. 7 (a) shows a torque waveform when the first embodiment is implemented
- FIG. 7 (b) shows a torque waveform when control for reducing torque pulsation is not performed.
- FIG. 1 is a block diagram showing a configuration example of a power conversion device according to Embodiment 1 of the present invention.
- the power converter includes a converter 2 that converts AC power from a single-phase AC power source 1 into DC power, a capacitor 3 that stores DC power rectified by the converter 2, and DC power stored in the capacitor 3 that has three frequencies. It has an inverter 4 for converting into phase alternating current.
- the inverter 4 drives an induction machine 5 that is an AC rotating machine.
- the converter 2 performs PWM (Pulse width modulation) control from a commercial frequency AC power source 1 to convert it into DC power.
- the inverter 4 performs variable voltage variable frequency (VVVF) control in the low speed range, and performs constant voltage variable frequency (CVVF) control in the high speed range.
- VVVF variable voltage variable frequency
- CVVF constant voltage variable frequency
- Current detectors 6a, 6b, 6c which are current measuring devices on the AC side, detect phase currents iu, iv, iw flowing through induction machine 5.
- the current detection unit 6 on the AC side is described as detecting the current flowing through the connection connecting the inverter 4 and the induction machine 5 by CT or the like, but using other known methods, The phase current may be detected using a current flowing inside the power conversion device such as a bus current.
- the magnitude of the AC voltage output from the inverter 4 is determined by the voltage controller 7 based on the torque current command value Iq * , the magnetic flux current command value Id * , and the rotational angular frequency ⁇ of the AC rotating machine.
- the angular frequency ⁇ speed information obtained by attaching a speed sensor to the induction machine 5 may be used, or a speed control system has a speed command value ⁇ * , and therefore the speed command value ⁇ * is set as the angular frequency ⁇ . Also good.
- the angular frequency ⁇ may be a speed estimated value calculated by speed sensorless control without attaching a speed sensor.
- FIG. 2 is a diagram illustrating a configuration of pulsation detecting unit 8 in the power conversion device according to Embodiment 1 of the present invention.
- the pulsation detection unit 8 that detects the pulsation due to the converter 2 converting the alternating current into the direct current is output from the phase currents iu, iv, iw detected by the current detection unit 6 and the inverter 4 required by the voltage control unit 7.
- the multiplier 9a multiplies Vu * and iu
- the multiplier 9b multiplies Vv * and iv
- the multiplier 9c multiplies Vw * and iw.
- the active power calculation unit 11 for calculating the active power P output from the inverter 4 and the band for extracting the pulsation of the active power P output from the active power calculation unit 11
- a pass filter 12 is provided.
- the active power P which is the output of the active power calculation unit 11, includes the motor current caused by the pulsation caused by the converter 2 converting AC to DC. It will contain a pulsating component. Note that the active power may be calculated by using the values of the voltage and current in rotation orthogonal coordinates.
- the pulsation accompanying converter 2 converting AC to DC becomes 120 Hz or 100 Hz, which is twice the frequency of the single-phase AC power supply.
- the band-pass filter 12 is configured assuming that the frequency of the single-phase AC power supply is 60 Hz.
- FIG. 3 is a diagram for explaining the band-pass filter.
- the band-pass filter 12 includes a high-pass filter (HPF) 13 that passes a frequency higher than the frequency corresponding to the time constant T 1 that is the first time constant, and a time constant T 2 that is the second time constant.
- a low-pass filter (LPF) 14 that passes a frequency lower than the corresponding frequency is combined.
- T 1 1 / (2 ⁇ ⁇ 60) (2)
- T 2 1 / (2 ⁇ ⁇ 180) (3)
- gain characteristics and phase characteristics in frequency when the bandpass filter 12 of FIG. 3 is configured with the time constants of the expressions (2) and (3) are shown in FIG. It becomes like this. It can be seen from the characteristics shown in FIG. 4 that the gain characteristics allow a frequency centered at 120 Hz to pass through with almost no attenuation. Therefore, the band-pass filter 12 can extract a 120 Hz component that is a pulsation due to the converter 2 converting AC to DC, and can output a pulsation component P_BEET.
- a command for the DC voltage Vc which is the voltage of the capacitor 3 that is charged by the converter 2 when the rotational angular frequency ⁇ of the AC rotating machine is input and is measured by the DC voltage detector 15 that is a voltage measuring instrument.
- a DC voltage command section 16 for outputting a value Vc *, to match the command value Vc *, a DC voltage control unit 17 for controlling the converter 2, the power conversion apparatus according to the invention has.
- the DC voltage command unit 16 increases the DC voltage only during a period in which the angular frequency ⁇ output from the inverter 4 has a large influence on torque or the like due to pulsation of the DC voltage.
- the input power Pin of the converter 2 can be expressed by the following equation.
- the pulsating power component in the equation (6) is Pin ⁇
- Pin ⁇ E ⁇ I ⁇ (cos (2 ⁇ t + ⁇ ) (7)
- the voltage Vc of the capacitor 3 is called a DC voltage.
- Equation (10) assuming that ((E ⁇ I) / (2 ⁇ C ⁇ Vcav 2 )) is sufficiently smaller than 1, an approximation of ⁇ (1 + ⁇ ) ⁇ 1 + ⁇ / 2 for ⁇ sufficiently smaller than 1 is used. ing.
- the second term of equation (10) represents the pulsating component of the DC voltage Vc. It can be seen that the pulsation component is twice the frequency of the power supply frequency, and its magnitude is inversely proportional to the average value of the capacitor capacitance C and the DC voltage Vc. Note that (E ⁇ I) is electric power input to the converter 2 and is kept constant even when the DC voltage Vc changes.
- the current ic flowing through the DC capacitor is obtained by the following equation.
- the DC voltage steadily increases the rated voltage of the switching elements constituting the inverter 4 and also uses the elements with higher voltage ranks of the switching elements, which may increase the cost. There is. Even when the voltage rank of the switching element does not increase, using the switching element at a voltage higher than the rated voltage shortens the life of the switching element. Considering these points, the DC voltage is increased only during the period in which the inverter 4 outputs the angular frequency ⁇ that has a large effect on the torque and the like due to the pulsation of the DC voltage. As will be described in detail later, when the inverter is operating in the 1 pulse mode, the effect on the switching element is not affected even if the DC voltage is higher than the rated voltage, compared to the case of the multi-pulse mode. Get smaller.
- FIG. 5 is a diagram showing a DC voltage command unit in the power conversion apparatus according to Embodiment 1 of the present invention.
- the DC voltage command unit 16 includes an absolute value unit 18 that converts an absolute value of the angular frequency ⁇ and a DC voltage value setting table 19.
- the absolute value unit 18 takes the absolute value of the angular frequency ⁇ so as to have only a positive value in order to simplify the DC voltage value setting table 19 because the input angular frequency ⁇ is signed with a positive or negative sign.
- the DC voltage command value to be output is shown on the vertical axis with the angular frequency ⁇ that is an absolute value on the horizontal axis. As shown in FIG.
- the DC voltage value setting table 19 shows that the voltage of the capacitor 3 pulsates, that is, twice the AC power frequency where the beat phenomenon is large (in this case, 120 Hz, but according to the AC power source,
- the frequency may be 100 Hz or the like (in this embodiment, 115 Hz or more and 125 Hz or less) and the DC voltage is increased to 3600 V, and the previous range (60 Hz or more and 115 Hz or less).
- the DC voltage is gradually increased, and gradually decreased in the subsequent range (range of 125 Hz to 180 Hz).
- the DC voltage is increased within a predetermined range (range of 60 Hz to 180 Hz).
- the range in which the DC voltage is maximum is a range of 115 Hz to 125 Hz.
- the predetermined range in which the DC voltage is higher than normal is determined so that the beat rate ⁇ is within an allowable range.
- ⁇ (ba) / a (A) according to the following calculation formula:
- b the fluctuation width of the inverter output current
- a the fluctuation width of the inverter output current at the output frequency.
- the upper limit value of the predetermined frequency range that makes the DC voltage higher than normal needs to be a value that allows the beat rate when the DC voltage value is a normal value. The same applies to the lower limit value of the predetermined frequency range.
- the frequency range in which the DC voltage is higher than usual it is necessary to make the beat rate acceptable at the DC voltage value at that frequency. If the frequency range in which the DC voltage is made higher than usual is wide, the beat rate can be surely kept within the allowable range.
- the predetermined range may be determined by an index different from the beat rate. Any method may be used as long as the pulsation component of the active power output from the inverter can be suppressed within an allowable range.
- the frequency range for making the DC voltage higher than normal takes into consideration the allowable beat rate ⁇ , the target value of the pulsation rate ⁇ at a frequency twice the AC power supply frequency, the ratio between the normal value and the maximum value of the DC voltage, etc. Decide appropriately.
- the pulsation rate at twice the frequency of the AC power supply frequency is 10%, and the ratio between the normal value and the maximum value of the DC voltage is 1.2 As described above, it is sufficient to set the width of the frequency range that maximizes the DC voltage to 10 Hz.
- the DC voltage value setting table 19 sets table data so that the DC voltage command value Vc * does not exceed the overvoltage setting value of the inverter 4. Further, the maximum value when raising the DC voltage of 3600 V is set in consideration of the rated voltage and characteristics by the switching elements constituting the inverter 4.
- a DC voltage command value Vc * that is an output of the DC voltage command unit 16 and a DC voltage Vc detected by the DC voltage detection unit 15 are input to the DC voltage control unit 17.
- the DC voltage control unit 17 obtains a difference between the DC voltage command value Vc * and the DC voltage Vc, and controls the converter 2 so that this difference becomes zero.
- the voltage control unit 7 calculates a slip angular frequency command value ⁇ s * from the torque current command value Iq * and the magnetic flux current command value Id * by the equation (13).
- ⁇ s * (Iq * / Id * ) ⁇ (Rr / Lr) (13)
- the inverter 4 subtracts the correction amount F_BEET obtained by multiplying the slip angular frequency command value ⁇ s * , the angular frequency ⁇ , and the predetermined coefficient Kf of the pulsation amount P_BEET obtained from the pulsation detection unit 8 to the frequency of the output voltage.
- the corresponding inverter angular frequency ⁇ inv is calculated. That is, the inverter angular frequency ⁇ inv is calculated by the equation (14).
- ⁇ inv ⁇ + ⁇ s * -F_BEET (14)
- F_BEET Kf ⁇ P_BEET (15)
- the frequency of the voltage output from the inverter 4 is corrected based on the pulsation component obtained from the pulsation detection unit 8.
- the torque current command value Iq * and the magnetic flux current command value Id *
- the d-axis voltage command value Vd * and the q-axis voltage command value Vq * on the two rotation axes are expressed by the following (16), (17 ) Expression.
- Vd * Rs ⁇ Id * ⁇ inv ⁇ ⁇ ⁇ Ls ⁇ Iq *
- Vq * Rs * Iq * + ⁇ inv * Ls * Id * (17)
- a control coordinate axis is required when performing coordinate conversion of a three-phase voltage or a three-phase current to two rotation orthogonal axes.
- the phase of the control coordinate axis which is a rotating biaxial coordinate, is ⁇ .
- This phase ⁇ is obtained by the equation (18) by integrating the inverter angular frequency ⁇ inv.
- the inverter 4 converts direct current into alternating current based on the three-phase voltage command values Vu * , Vv * , Vw * obtained from the voltage control unit 7 obtained by the equation (20). Since the frequency of the voltage output from the inverter 4 is corrected based on the pulsation component obtained from the pulsation detection unit 8, the motor current and torque pulsation on the output side of the inverter 4 can be suppressed.
- the inverter angular frequency ⁇ inv is adjusted to decrease and output from the voltage control unit 7.
- the frequencies of the three-phase voltage command values Vu * , Vv * , Vw * are reduced.
- the pulsation component P_BEET obtained from the pulsation detection unit 8 is negative, the inverter angular frequency ⁇ inv is adjusted to increase, and the three-phase voltage command values Vu * , Vv * , Vw * output from the voltage control unit 7 are adjusted .
- the frequency of increases As a result, control can be performed according to the motor current and torque pulsation on the output side of the inverter 4, and the motor current and torque pulsation on the output side of the inverter 4 can be suppressed.
- FIG. 7 is a diagram showing the effect of reducing torque pulsation by the power conversion device according to Embodiment 1 of the present invention.
- FIG. 7 (a) shows a torque waveform when the first embodiment is implemented
- FIG. 7 (b) shows a torque waveform when control for reducing torque pulsation is not performed.
- FIG. 7 shows a torque waveform by simulation when the DC voltage is 3600 V and the inverter frequency is 115 Hz.
- FIG. 7B when the control for reducing the torque pulsation is not performed, the torque waveform pulsates at 120 Hz, which is twice the single-phase power supply frequency.
- FIG. 7A in which the first embodiment is implemented, it can be confirmed that the torque waveform has almost no pulsation.
- FIG. FIG. 8 is a block diagram illustrating a configuration example of the power conversion device according to the power conversion device according to the second embodiment.
- FIG. 9 is a diagram illustrating the configuration of the pulsation detecting unit in the power conversion device according to Embodiment 2 of the present invention.
- the pulsation detection unit 8A, the voltage control unit 7A, and the DC voltage command unit 16A are different from those in the first embodiment.
- the active power is calculated from the three-phase voltage command value and the three-phase current
- the pulsation component is detected from the effective power
- the frequency is corrected by the pulsation component.
- the pulsation detection unit 8A calculates active power from the dq-axis voltage command value and the dq-axis current, and the voltage control unit 7A corrects the amplitude of the voltage command value according to the pulsation component of the active power. . Further, the DC voltage command unit 16A operates the DC voltage according to the calculated value of the active power, and when the active power P is small and the beat phenomenon is allowable, the DC voltage command unit 16A sets the DC voltage to a normal value. Operate.
- Other configurations are the same as those of the first embodiment, and the drawings are also denoted by the same reference numerals, and only different portions will be described here.
- the pulsation detection unit 8A for detecting the pulsation accompanying the conversion of the alternating current into the direct current by the converter 2 includes the phase calculation unit 20, the three-phase dq axis conversion calculation unit. 21 and an active power calculator 11A.
- the phase calculation unit 20 calculates the phase ⁇ by integrating the ⁇ inv calculated as described later with the angular frequency ⁇ as input, as shown in the equation (18).
- the three-phase dq axis conversion calculation unit 21 calculates the dq axis currents Id and Iq from the phase currents iu, iv and iw detected by the current detection unit 6 using the phase ⁇ .
- the active power calculator 11A uses the dq-axis currents Id and Iq calculated by the three-phase dq-axis conversion calculator 21 and the dq-axis voltage command values Vd * and Vq * calculated by the voltage controller 7A to The active power P is calculated by the equation.
- P Vd * .Id + Vq * .Iq (21)
- the active power calculation unit 11A includes multipliers 22a and 22b and an adder 23.
- the multiplier 22a multiplies Vd * and Id
- the multiplier 22b multiplies Vq * and Iq, adds the multiplied values by the adder 23, and outputs the output of the adder 23 as the active power P.
- the active power P which is the output of the active power calculation unit 11A, includes motor current pulsation and torque pulsation components due to pulsation due to the converter 2 converting AC to DC.
- the active power P calculated by the active power calculator 11A is input to the band pass filter 12, and the output P_BEET of the band pass filter is input to the voltage controller 7A.
- the subtractor 24 subtracts the output P_BEET of the band pass filter from the output of the active power calculation unit 11A, and outputs the output of the subtractor 24 to the DC voltage command unit 16A as active power P that does not include a pulsation component.
- the voltage control unit 7A calculates the slip angular frequency command value ⁇ s * from the torque current command value Iq * and the magnetic flux current command value Id * using the motor constant of the induction machine. That is, the slip angular frequency command value ⁇ s * is calculated by the equation (13) as in the first embodiment.
- the inverter 4 calculates an inverter angular frequency ⁇ inv corresponding to the frequency of the output voltage. That is, the inverter angular frequency ⁇ inv is calculated by the following equation (22).
- ⁇ inv ⁇ + ⁇ s * (22)
- the torque current command value Iq * , and the magnetic flux current command value Id * , the d-axis voltage command value Vd * and the q-axis voltage command value Vq * on the two rotation axes can be calculated. That is, the d-axis voltage command value Vd * and the q-axis voltage command value Vq * are calculated by the equations (16) and (17) as in the first embodiment. Since the voltage phase ⁇ v of the voltage command value is slightly advanced from the phase ⁇ , it is calculated from the equation (19) as in the first embodiment.
- the three-phase voltage command values Vu * , Vv * , and Vw * are calculated by the equation (21) from the voltage phase ⁇ v and the d-axis voltage command value Vd * and the q-axis voltage command value Vq * obtained by the equation (19).
- the amplitude of the three-phase voltage command value is reduced by V_BEET obtained by multiplying the pulsation component P_BEET of active power by a predetermined coefficient Kv.
- V_BEET Kv ⁇ P_BEET (24)
- the DC voltage cannot be maximized even in the frequency region where the constant voltage variable frequency (CVVF) control is performed, and is necessary for suppressing pulsation. It is necessary to make it smaller than the maximum value by an amount corresponding to the control amount.
- Active power P and angular frequency ⁇ excluding the pulsation which is the output of the pulsation detection unit 8A, are input to the DC voltage command unit 16A.
- the absolute value device 18 and the DC voltage value setting table 19 of the DC voltage command unit 16A are the same as those in the first embodiment.
- the DC voltage command unit 16A changes the width for increasing the voltage according to the active power, thereby changing the inverter 4 It aims at reducing the burden of the switching element which comprises.
- the present embodiment is based on the fact that the beat phenomenon changes depending on the electric power or torque generated by the motor, that is, the beat phenomenon increases if the electric power is large at the same speed. In other words, when the power is small, the pulsation rate is within the allowable range even if the DC voltage is the rated voltage. 7 of Non-Patent Document 1 also shows that the pulsation rate increases as the output of the converter increases when the voltage is constant.
- the absolute value unit 18b of the DC voltage command unit 16A receives the active power P having a positive or negative sign, takes the absolute value thereof, and outputs it as a dominant power value P1.
- the divider 25 divides P1 by a predetermined value (for example, maximum power) and outputs a coefficient Kp.
- the limiter 26 ensures that the coefficient Kp is 0 ⁇ Kp ⁇ 1.
- the multiplier 27 multiplies the output value of the limiter 26 and the output value of the DC voltage value setting table 19. As a result, the DC voltage command value Vc * is a value that takes active power into consideration.
- the limiter 28 becomes a small value such as 0V.
- the limiter process is performed so that the DC voltage command value Vc * is in the range from 3000V to 3600V.
- the pulsation rate is proportional to the active power output from the inverter and inversely proportional to the square of the DC voltage. Therefore, if the coefficient Kp is proportional to the square root of the active power, the active power is large. The pulsation rate is almost the same regardless of the active power.
- the DC voltage command value is increased when the active power is increased. However, if the current value, the torque command value, the torque current command value, the torque current value, etc. are increased except for the active power, the DC voltage command value is increased. Even if the voltage command value is increased, the same effect can be expected. The same applies to the following embodiments.
- the influence of pulsation caused by the converter converting AC to DC is detected as a pulsation component included in the active power of the inverter, and the amplitude of the voltage output by the inverter is determined. By correcting, an effect of suppressing torque pulsation or the like can be obtained.
- the DC voltage is set to a normal value, and when the active power is larger than the predetermined value, the DC voltage value is increased when the active power is large. There is an effect that the burden on the switching elements constituting the inverter can be reduced after being reduced. For this reason, it is possible to obtain an effect that the power conversion device can be reduced in size and cost.
- FIG. 11 is a block diagram illustrating a configuration example of the power conversion device according to the third embodiment.
- the third embodiment is different from the second embodiment only in the DC voltage command unit 16B.
- the DC voltage value setting table 19 operates by further limiting the conditions for operating the DC voltage in accordance with the calculated value of the active power and the case where the active power is a positive value. That is, the DC voltage is raised only during powering, and the DC voltage is fixed at the rated value of 3000 V during regeneration.
- the present embodiment is formed for the purpose of realizing energy saving by reducing the beat phenomenon during power regeneration compared to power running and by returning the energy to an AC power source as much as possible from the viewpoint of energy saving during regeneration. Yes.
- Other configurations are the same as those of the second embodiment, and the drawings are also denoted by the same reference numerals, and only different portions will be described here.
- FIG. 12 is a diagram showing a DC voltage command unit in the power conversion apparatus according to Embodiment 3 of the present invention.
- a limiter 29, a comparator 30, and a switching unit 31 are added.
- the comparator 30 outputs a signal of 1 when the active power P is greater than 0, that is, during power running, so that the switching unit 31 is set to A. Further, the comparator 30 outputs a signal of 0 when P is 0 or less, that is, when coasting or regenerating, so that the switching unit 31 is set to B.
- the limiter 29 connected to the contact B of the switching unit 31 performs a limiter process of 3000 V or more and 3000 V or less so that the DC voltage is 3000 V in order to fix the DC voltage to the rated value of 3000 V during regeneration.
- the signal which switches A and B setting of the switching part 31 can acquire the same effect by not only active power but torque command, power running command, or regeneration (brake) command.
- the DC voltage command unit 16B includes the comparator 30, the limiter 29, and the switching unit 31, the DC voltage is increased only during powering, and the DC voltage is set to the rated value during regeneration. Can be fixed at 3000V.
- the burden on the switching elements constituting the inverter 4 can be reduced. If the active power is small even during power running, the DC voltage remains at its normal value, and even if the active power is large, the DC voltage rise is changed according to the active power. Even if the voltage is increased, the same effect can be obtained with respect to not increasing the DC voltage during regeneration.
- FIG. FIG. 13 is a block diagram illustrating a configuration example of the power conversion device according to the fourth embodiment.
- FIG. 14 is a diagram illustrating the configuration of the pulsation detecting unit in the power conversion apparatus according to Embodiment 4 of the present invention.
- the pulsation detection part 8B and the pulsation detection part 16C differ.
- the pulsation detection unit 8B includes the three-phase / dq axis conversion unit 21, the phase calculation unit 20, the active power calculation unit 11A, and the bandpass filter 12 in the same manner as in the second embodiment.
- a correction gain calculator 32 that calculates the correction gain k as an input and a multiplier 33 that multiplies the output value of the bandpass filter 12 by the correction gain k that is the output of the correction gain calculator 32.
- This correction gain k may be changed by the angular frequency ⁇ , set by table data, or given by a function.
- the correction gain is set to the maximum before the pulsation frequency component of 120 Hz.
- this correction gain is set to zero, no correction is made, and by changing the correction gain with respect to the angular frequency ⁇ , whether or not to correct, how much to correct when correcting, There is an effect that it can be changed according to the angular frequency ⁇ .
- FIG. 15 is a diagram showing a pulsation detecting unit 16C in the power conversion apparatus according to Embodiment 4 of the present invention.
- the pulsation detector 16C includes an absolute value unit 18 that converts the absolute value of the angular frequency ⁇ into a DC voltage value setting table 19B.
- the absolute value unit 18 converts the input angular frequency ⁇ into an absolute value of the angular frequency ⁇ so as to have only a positive value in order to simplify the DC voltage value setting table 19B because the input angular frequency ⁇ is signed with a positive or negative sign.
- the horizontal axis represents the angular frequency ⁇ that is an absolute value
- the vertical axis represents the DC voltage command value that is output. As shown in FIG.
- the DC voltage value setting table 19B has a frequency that is twice the AC power supply frequency where the beat phenomenon is large (in this case, 120 Hz, but may be 100 Hz depending on the AC power supply).
- the voltage when the DC voltage is maximized in a predetermined range including (in this embodiment, a range of 105 Hz or more) is 3300 V, and the DC voltage is gradually increased in the previous range.
- the output voltage of the inverter 4, that is, the motor voltage Vm is such that Vm / ⁇ is substantially constant in a range where the frequency ⁇ of the inverter 4 is greater than 0 and less than a predetermined angular frequency ( ⁇ 1) (that is, 0 ⁇ ⁇ 1). It is controlled to become.
- the motor voltage Vm reaches the maximum value expressed by the following equation, the inverter 4 can no longer perform voltage amplitude control.
- the angular frequency when the maximum value is reached is ⁇ 1.
- ⁇ 1 is usually smaller than the angular frequency corresponding to twice the AC power supply frequency.
- the motor voltage Vm is fixed at this maximum value, and only the frequency changes.
- Vm (( ⁇ 6) / ⁇ ) ⁇ Vc (25)
- the characteristic of the maximum torque Tmax of the induction machine controlled by such a pattern of the motor voltage Vm has the following relationship in the high speed ( ⁇ > ⁇ 1) region. Tmax ⁇ (Vc / ⁇ ) 2 (26)
- Vc DC voltage
- Tmax ⁇ (Vc / ⁇ ) 2
- the DC voltage Vc can be increased in a high speed ( ⁇ > ⁇ 1) region without increasing the breakdown voltage of the switching elements constituting the inverter 4.
- An IGBT insulated gate bipolar transistor having a self-extinguishing function is used for the switching element constituting the inverter 4.
- the peak value Vp of the collector-emitter voltage waveform Vce when the IGBT element shown in FIG. 16 cuts off the current I is empirically expressed by the following equation.
- Vp Vc + I ⁇ ⁇ (L / C) (27)
- L is the inductance value of the floating inductance of the IGBT, and C is the floating capacitance of the floating capacitor of the IGBT.
- the current value that the IGBT cuts off in the actual operation state is smaller in the one-pulse mode than in the multi-pulse (asynchronous) mode.
- the IGBT cuts off the current at the peak value of the ripple.
- the maximum value Ip of the current that the IGBT cuts off in the multi-pulse (asynchronous) mode is the motor constant of the induction machine and the modulation rate of the voltage output from the inverter 4 if the fundamental value of the motor current flowing in the motor is Im. Although it varies slightly depending on the length of the wiring between the inverter 4 and the induction engine, it is empirically expressed as follows.
- the coefficient 1.5 described below is usually a value of about 1.3 to 1.5, but here, the upper limit value of 1.5 is used.
- Ip 1.5 ⁇ ⁇ 2 ⁇ Im (28)
- the motor current waveform is such that the IGBT element cuts off the current only once per cycle.
- the current Iq to be cut off at this time is the current value IQ if the fundamental wave effective value of the motor current is Im.
- Is empirically expressed as follows with respect to the fundamental effective value Im. Iq 0.7 ⁇ ⁇ 2 ⁇ Im (29)
- Ip ⁇ 2.1 ⁇ Iq (30)
- the overcharge component I ⁇ ⁇ (L / C) in the equation (27) becomes small. Therefore, even if the DC voltage Vc is increased, the peak value Vp of the collector-emitter voltage of the IGBT. Will not grow.
- the inductance value L of the stray inductance of the IGBT is about 3.0 ⁇ H, and the stray capacitance C of the stray capacitor is about 1.5 to 3.0 ⁇ F.
- ⁇ (L / C) in equation (27) becomes ⁇ (2) ⁇ 1.41.
- Vp is about 100 A
- Vp is about 3450 V, and the influence on the IGBT element can be further reduced.
- 3600V and 3300V are only examples, and are set in consideration of the characteristics of the switching elements and usage conditions.
- the influence of pulsation caused by the converter converting AC to DC is detected as the pulsation component included in the active power of the inverter, and the amplitude of the voltage output by the inverter is determined.
- an effect of suppressing torque pulsation or the like can be obtained.
- by increasing the DC voltage during a period in which the inverter outputs a frequency at which the beat phenomenon becomes large it is possible to reduce the capacitance of the capacitor required to suppress the beat phenomenon to an allowable range. For this reason, it is possible to obtain an effect that the power converter can be reduced in size and cost.
- the DC voltage Vc at a frequency operating in the 1-pulse mode loss can be reduced and a larger torque can be generated without increasing the burden on the switching element.
- the maximum value of the command value of the DC voltage Vc is set to 3300 V.
- the voltage is gradually increased from 85 Hz, for example, 3600 V from 115 Hz to 125 Hz. It may be gradually decreased at 125 Hz or higher and 3300 V at 140 Hz or higher.
- an upper limit voltage value (for example, 3300 V) within a range in which the command value of the DC voltage Vc is higher than a normal voltage and does not increase the burden on the switching element is referred to as a one-pulse mode voltage upper limit value.
- the one-pulse mode voltage upper limit value is set so that the voltage applied to the switching element does not exceed the maximum value under the assumed use conditions. If the command value of the DC voltage Vc is higher than usual at the frequency at which the inverter operates in the 1-pulse mode and is not more than the 1-pulse mode voltage upper limit value, the voltage value may fluctuate with respect to the change in frequency.
- the command value may be a normal voltage temporarily.
- an AC rotating machine induction machine
- the AC rotating machine is not limited to an induction machine.
- the present invention is not limited to the AC rotating machine, and the same effect can be expected when applied to other loads such as those controlling an electromagnetic actuator such as a linear induction motor, a linear synchronous motor, or a solenoid.
- the present invention is an inverter that drives an AC motor at a variable speed using a direct current obtained by rectifying an alternating current power supply with a converter as a power supply. It is what is done.
- the present invention can also be applied to appliances that use a single-phase power receiving device to control a motor with an inverter, such as an air conditioner, a refrigerator, and a washing machine.
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Abstract
Description
しかし、特許文献1のものでは、非特許文献1に記載されているように所定のビート現象の抑制効果を得るためには、直流電圧の脈動率を小さくできるようにコンデンサ容量の大きさが決まるという制約を受ける課題がある。すなわち、交流電源周波数の2倍の周波数でビート現象が大きくなるので、その周波数において直流電圧の脈動成分を10%以下にするようにして、直流コンデンサ容量を決めている。ビート現象が最も大きくなる特定の周波数ポイントのためにコンデンサ容量が大きくなるという課題があった。
図1は、この発明の実施の形態1に係る電力変換装置の構成例を示すブロック図である。電力変換装置は、単相交流電源1からの交流電力を直流電力に変換するコンバータ2、コンバータ2により整流された直流電力を貯えるコンデンサ3、コンデンサ3に貯えられた直流電力を任意の周波数の三相交流に変換するインバータ4を有する。インバータ4は、交流回転機である誘導機5を駆動する。コンバータ2は、商用周波数の交流電源1からPWM(Pulse width modulation:パルス幅変調)制御を行って直流電力に変換するものである。インバータ4は、低速域では可変電圧可変周波数(VVVF)制御を行い、高速域では定電圧可変周波数(CVVF)制御を行なう。
P=Vu*・iu+Vv*・iv+Vw*・iw (1) 有効電力演算部11の出力である有効電力Pには、コンバータ2が交流を直流に変換することに伴う脈動分に起因するモータ電流の脈動成分を含むことになる。なお、電圧と電流を回転直交座標での値を用いて、有効電力を計算してもよい。
T1=1/(2π・60) (2)
T2=1/(2π・180) (3)
コンバータ2の入力電流iAは正弦波であるとして、コンバータ2の入力電源電圧Vとコンバータ2の入力電流iAは、それぞれ次のように記載できる。
V=√2・E・cos(ωt+φ) (4)
iA=√2・I・cos(ωt) (5)
Pin=2・E・I・cos(ωt+φ)・cos(ωt)
=E・I・(cos(2ωt+φ)+cosφ) (6)
ここで、(6)式における定数項は、負荷に供給される電力を表し、ωの2倍の角周波数で変動する正弦波の成分はコンデンサ3に供給される脈動電力である。コンバータ2では力率を1に制御できるので、cosφ=1.0である。すると、定数項は、E・Iとなる。
(6)式における脈動電力成分をPin~とすると、次式で表されることになる。
Pin~=E・I・(cos(2ωt+φ) (7)
(10)式の第2項は、直流電圧Vcの脈動成分を表していることになる。脈動成分は電源周波数の2倍の周波数であり、その大きさはコンデンサ容量C、直流電圧Vcの平均値に反比例することが判る。なお、(E・I)は、コンバータ2に入力される電力であり、直流電圧Vcが変化しても一定に保たれる。
なお、(10)式、(12)式は、直流電圧Vcの脈動がインバータ4の出力側に影響しないという仮定の下での理論式であるが、インバータ4の出力電力が脈動する場合でも、ほぼ同様に成立する。
なお、後で詳しく説明するが、1パルスモードでインバータが動作している場合には、多パルスモードの場合と比較して、直流電圧を定格電圧よりも高くしてもスイッチング素子への影響は小さくなる。
β=(b-a)/a (A)
ここに、bはインバータ出力電流の変動幅であり、aはインバータ出力電流の出力周波数での変動幅である。
直流電圧を通常よりも高くする所定の周波数範囲の上限値は、直流電圧値が通常の値でのビート率が許容できる値である必要がある。所定の周波数範囲の下限値においても、同様である。また、直流電圧を通常よりも高くする周波数範囲において、その周波数における直流電圧値でのビート率が許容できる範囲とする必要がある。直流電圧を通常よりも高くする周波数範囲を広く取れば、ビート率を確実に許容範囲に収めることができる。なお、ビート率とは別の指標により、所定の範囲を決めてもよい。インバータが出力する有効電力の脈動成分を許容できる範囲に抑制できれば、どのように決めてもよい。
直流電圧を通常よりも高くする周波数範囲は、許容するビート率β、交流電源周波数の2倍の周波数での脈動率δの目標値、直流電圧の通常値と最大値の比などを考慮して適切に決める。この実施の形態のように、ビート率βを1.2以下、交流電源周波数の2倍の周波数での脈動率を10%、直流電圧の通常値と最大値の比が1.2の場合は、先に説明したように直流電圧を最大値にする周波数の範囲の幅を10Hzとすることで十分である。
直流電圧制御部17には、直流電圧指令部16の出力である直流電圧指令値Vc*と直流電圧検出部15で検出された直流電圧Vcとが入力される。直流電圧制御部17では、直流電圧指令値Vc*と直流電圧Vcとの差を求め、この差がゼロになるようにコンバータ2を制御する。
Rs:モータの一次抵抗値
Ls:モータの一次インダクタンス
M:モータの相互インダクタンス
Lr:モータの二次インダクタンス
Rr:モータの二次抵抗値
σ=1-M・M/Ls/Lr
ωs*=(Iq*/Id*)・(Rr/Lr) (13)
すべり角周波数指令値ωs*と角周波数ωと脈動検出部8から得た脈動量P_BEETの所定の係数Kfを乗じて得た補正量F_BEETを減算することにより、インバータ4は出力する電圧の周波数に相当するインバータ角周波数ωinvを演算する。すなわち、インバータ角周波数ωinvは、(14)式で演算する。
ωinv=ω+ωs*-F_BEET (14)
F_BEET=Kf・P_BEET (15)
インバータ角周波数ωinv、トルク電流指令値Iq*、磁束電流指令値Id*から、回転二軸上のd軸電圧指令値Vd*、q軸電圧指令値Vq*を、以下の(16)、(17)式で演算することができる。
Vd*=Rs・Id*-ωinv・σ・Ls・Iq* (16)
Vq*=Rs・Iq*+ωinv・Ls・Id* (17)
θv=θ+tan-1(Vd*/Vq*) (19)
(19)式で得られた電圧位相θvとd軸電圧指令値Vd*、q軸電圧指令値Vq*から三相電圧指令値Vu*、Vv*、Vw*は(20)式で算出する。
脈動検出部8から得た脈動成分に基づいてインバータ4が出力する電圧の周波数が補正されるため、インバータ4の出力側のモータ電流およびトルクの脈動を抑制することが可能となる。図6に、脈動検出部と直流電圧指令部の動作を説明する図を示す。図6では、Kf=1としている。インバータ4の出力側のモータ電流およびトルクの脈動と同期した脈動検出部8から得た脈動成分P_BEETが正であれば、インバータ角周波数ωinvを減少させるように調整し、電圧制御部7の出力する三相電圧指令値Vu*、Vv*、Vw*の周波数は小さくなる。逆に脈動検出部8から得た脈動成分P_BEETが負であれば、インバータ角周波数ωinvを増加させるように調整し、電圧制御部7の出力する三相電圧指令値Vu*、Vv*、Vw*の周波数は大きくなる。そのことにより、インバータ4の出力側のモータ電流およびトルクの脈動に応じて、制御を行なうことができ、インバータ4の出力側のモータ電流およびトルクの脈動を抑制することができる。
また、ビート現象が大きくなる周波数をインバータが出力する期間すなわちコンデンサの電圧が脈動する期間だけ直流電圧を大きくすることにより、ビート現象を許容できる範囲に抑えるために必要となるコンデンサ容量を低減することができる。そのため、電力変換装置を小型、低コスト化を実現できる。
以上のことは、他の実施の形態でもあてはまる。
図8は、実施の形態2に係る電力変換装置に係る電力変換装置の構成例を示すブロック図である。図9は、この発明の実施の形態2に係る電力変換装置における脈動検出部の構成を説明する図である。この実施の形態2では、実施の形態1の場合と比較して、脈動検出部8A、電圧制御部7A、直流電圧指令部16Aが異なる。実施の形態1では、三相電圧指令値と三相電流から有効電力を演算し、その有効電力から脈動成分を検出し、その脈動成分により周波数を補正していた。この実施の形態2では、脈動検出部8Aにおいてdq軸電圧指令値とdq軸電流から有効電力を演算し、その有効電力の脈動成分に応じて電圧指令値の振幅を電圧制御部7Aが補正する。また、その演算された有効電力の値に応じて直流電圧を操作し、有効電力Pが小さくビート現象が許容できる範囲内の場合は直流電圧を通常の値とするように直流電圧指令部16Aが動作する。なお、他の構成は実施の形態1と同様であり、図面も同一符号で示し、ここでは異なる部分のみ説明する。
P=Vd*・Id+Vq*・Iq (21)
(21)式の演算を行なうために、有効電力演算部11Aは、乗算器22a、22bと加算器23を有する。乗算器22aでVd*とIdを掛けて、乗算器22bでVq*とIqを掛けて、それぞれの乗算値を加算器23で足し合わせ、加算器23の出力を有効電力Pとして出力する。
なお、有効電力演算部11Aの出力である有効電力Pには、コンバータ2が交流を直流に変換することに伴う脈動分に起因するモータ電流の脈動ならびにトルク脈動成分を含むことになる。
また、減算器24は、有効電力演算部11Aの出力から帯域通過フィルタの出力P_BEETを減算し、脈動成分を含まない有効電力Pとして、減算器24の出力を直流電圧指令部16Aに出力する。
すべり角周波数指令値ωs*と角周波数ωとを加算して、インバータ4は出力する電圧の周波数に相当するインバータ角周波数ωinvを演算する。すなわち、インバータ角周波数ωinvは、下に示す(22)式で演算する。
ωinv=ω+ωs* (22)
直流電圧指令部16Aには、脈動検出部8Aの出力である脈動を除いた有効電力Pと角周波数ωが入力される。直流電圧指令部16Aの絶対値器18、直流電圧値設定テーブル19は、実施の形態1の場合と同様である。この実施の形態2の直流電圧指令部16Aは、直流電圧を上昇させる期間を実施の形態1よりも限定することに加えて、有効電力に応じて電圧を上昇させる幅を変化させることによりインバータ4を構成するスイッチング素子の負担を軽減することを目的としている。本実施の形態は、ビート現象がモータの発生する電力もしくはトルクにより変化すること、すなわち、同じ速度で電力が大きければビート現象は大きくなることに基づいている。逆にいうと、電力が小さい場合には直流電圧が定格電圧でも脈動率が許容できる範囲内にあることになる。非特許文献1の図7でも、電圧が一定の場合にコンバータの出力が大きいほど脈動率が大きくなることが示されている。
(12)式によると、脈動率はインバータが出力する有効電力に比例し直流電圧の2乗に反比例するので、係数Kpが有効電力の平方根に比例するようにしてやれば、有効電力が大きい場合に有効電力によらず脈動率がほぼ同じになる。
なお、本実施の形態では、有効電力が大きくなると直流電圧指令値を大きくなるようにしたが、有効電力以外では電流値やトルク指令値、もしくはトルク電流指令値、トルク電流値などが大きくなると直流電圧指令値を大きくなるようにしても、同様の効果が期待できる。これは、以下の実施の形態でも同様である。
図11は、実施の形態3に係る電力変換装置の構成例を示すブロック図である。この実施の形態3は、実施の形態2と直流電圧指令部16Bのみが異なることになる。この実施の形態3では、演算された有効電力の値に応じて直流電圧を操作する条件を有効電力が正の値の場合と更に限定を行なって直流電圧値設定テーブル19が動作する。すなわち、直流電圧を上昇させるのを力行時のみに限定して、回生時は直流電圧を定格値の3000Vに固定する。本実施の形態では、回生時には力行時に比較してビート現象が小さいことと回生時は省エネルギーの観点からエネルギーをできるだけ交流電源に戻したほうが省エネルギーを実現できることを目的に本実施の形態が成されている。なお、他の構成は実施の形態2と同様であり、図面も同一符号で示し、ここでは異なる部分のみ説明する。
比較器30は、有効電力Pが0より大きければ、すなわち力行時は1の信号を出力して、切り替え部31をAの設定になるようにする。また、比較器30は、Pが0以下、すなわち、惰行もしくは回生時であると0の信号を出力して、切り替え部31をBの設定になるようにする。
図13は、実施の形態4に係る電力変換装置の構成例を示すブロック図である。図14は、この発明の実施の形態4に係る電力変換装置における脈動検出部の構成を説明する図である。この実施の形態4では、実施の形態2の場合と比較して、脈動検出部8B、脈動検出部16Cが異なる。
Vm=((√6)/π)・Vc (25)
Tmax ∝ (Vc/ω)2 (26)
直流電圧Vcを一定とした時には、最大トルクTmaxは角周波数ωの2乗に反比例する。したがって、特に高速域においてトルクの減少が著しくなり、高速域で十分なトルクが得にくい。
インバータ4を構成するスイッチグ素子には、自己消弧機能を有するIGBT(insulated gate bipolar transistor)が用いられている。
図16に示すIGBT素子が電流Iを遮断した時の素子のコレクタ-エミッタ間電圧波形Vceのピーク値Vpは、経験的に以下の式で表される。
Vp=Vc+I・√(L/C) (27)
なお、LはIGBTの浮遊インダクタンスのインダクタンス値、CはIGBTの浮遊コンデンサの浮遊容量である。
Ip=1.5・√2・Im (28)
Iq=0.7・√2・Im (29)
(28)式と(29)式とにおいて、Imはパルスモードによって変化しないと仮定すると、以下が成立する。
Ip≒2.1・Iq (30)
1パルスモードへ移行すると、(27)式における過充電成分I・√(L/C)が小さくなるので、その分、直流電圧Vcを上昇させてもIGBTのコレクタ-エミッタ間電圧のピーク値Vpは大きくならない。
また、ビート現象が大きくなる周波数をインバータが出力する期間において直流電圧を大きくすることにより、ビート現象を許容できる範囲に抑えるために必要となるコンデンサ容量を低減することができる。そのため、電力変換装置を小型、低コスト化を実現できる効果を得られる。さらに、1パルスモードで動作する周波数において直流電圧Vcを高くすることで、スイッチング素子に負担を増加させることなく、損失を低減でき、より大きなトルクを出せるようになる。
3 :コンデンサ、 4 :インバータ
5 :誘導機(交流回転機)、 6a:電流検出部
6b:電流検出部、 6c:電流検出部
7 :電圧制御部、 7A:電圧制御部
8 :脈動検出部、 8A:脈動検出部
9a:乗算器、 9b:乗算器
9c:乗算器、 10 :加算器
11 :有効電力演算部、 11A:有効電力演算部
12 :帯域通過フィルタ、 13 :高域通過フィルタ
14 :低域通過フィルタ、 15 :直流電圧検出部
16 :直流電圧指令部、 16A:直流電圧指令部
16B:直流電圧指令部、 16C:直流電圧指令部
17 :直流電圧制御部、
18 :絶対値器、 18b:絶対値器
19 :直流電圧値設定テーブル、 19B:直流電圧値設定テーブル
20 :位相演算部
21 :三相dq軸変換演算部、 22a:乗算器
22b:乗算器、 23 :加算器
24 :減算器、 25 :除算器
26 :リミッタ、 27 :乗算器
28 :リミッタ、 29 :リミッタ
30 :比較器、 31 :切り替え部
32 :補正ゲイン演算部 33 :乗算器
Claims (15)
- 交流電源からの交流電力を直流電力に変換するコンバータと、
該コンバータが出力する直流電力を貯えるコンデンサと、
該コンデンサに貯えられた直流電力を交流電力に変換するインバータと、
該インバータが出力する交流電圧の指令値を求めてこの指令値を出力するように前記インバータを制御する電圧制御部と、
前記インバータが出力する交流電流を計測する電流計測器と、
前記電圧制御部が求める交流電圧の指令値と前記電流計測器が計測する交流電流とが入力されて前記インバータが出力する有効電力の脈動を検出する脈動検出部と、
前記コンデンサの電圧を計測する電圧計測器と、
前記インバータが出力する交流電圧の周波数に応じて前記コンデンサの電圧の指令値を求める直流電圧指令部と、
前記電圧計測器が計測する電圧と前記直流電圧指令部が求める指令値とが入力されて前記コンデンサの電圧が指令値になるように前記コンバータを制御する直流電圧制御部とを備え、
前記直流電圧指令部は、前記インバータが出力する交流電圧の周波数が、前記コンデンサの電圧が脈動する周波数を含む所定の範囲内である場合に、前記コンデンサの電圧の指令値を通常よりも高くし、
前記電圧制御部は、前記脈動検出部が出力する脈動成分が入力されて前記脈動成分を抑制するように前記インバータが出力する交流電圧の指令値を求めることを特徴とする電力変換装置。 - 前記所定の範囲が、前記脈動成分が許容できる範囲となるように決められることを特徴とする請求項1に記載の電力変換装置。
- 前記所定の範囲内で、前記インバータが1パルスモードで動作する周波数の範囲の少なくとも一部で、前記指令値を通常よりも高く、かつ前記インバータが有するスイッチング素子への負担を増加させない範囲の上限の電圧値以下とすることを特徴とする請求項1に記載の電力変換装置。
- 前記直流電圧指令部が、前記インバータが出力する有効電力の絶対値が所定値以下の場合に、前記コンデンサの電圧を通常の値とすることを特徴とする請求項1または請求項2に記載の電力変換装置。
- 前記直流電圧指令部が、前記インバータが出力する有効電力が負の場合に、前記コンデンサの電圧を通常の値とすることを特徴とする請求項1または請求項2に記載の電力変換装置。
- 前記直流電圧指令部が、前記インバータが出力する交流電圧の周波数から出力する前記指令値を求める直流電圧値設定テーブルを持ち、
前記直流電圧値設定テーブルにおいて、前記所定の範囲内において前記指令値を最大にする範囲を有し、この前記指令値を最大にする範囲よりも周波数が低い側の前記所定の範囲において周波数の増加に対して前記指令値が増加することを特徴とする請求項1ないし請求項3の何れかに記載の電力変換装置。 - 前記指令値を最大にする範囲よりも周波数が高い側の前記所定の範囲において周波数の増加に対して前記指令値が減少することを特徴とする請求項6に記載の電力変換装置。
- 前記脈動検出部が、前記インバータが出力する有効電力を求める有効電力演算部と、前記有効電力演算部の出力から脈動を検出する帯域通過フィルタを有するものであることを特徴とする請求項1ないし請求項3の何れかに記載の電力変換装置。
- 前記有効電力演算部が、前記電流計測器が計測する3相の交流電流と前記電圧制御部が求める交流電圧の3相の指令値のそれぞれを乗じたものの和を取って有効電力を求めるものであることを特徴とする請求項8に記載の電力変換装置。
- 前記有効電力演算部が、前記電流計測器が計測する3相の交流電流を回転直交座標系での値に変換したものと、回転直交座標系での前記電圧制御部が求める交流電圧の指令値をそれぞれ乗じたものの和を取って有効電力を求めるものであることを特徴とする請求項8に記載の電力変換装置。
- 前記帯域通過フィルタが、通過させる帯域の下限と関係する第1の時定数の第1の1次遅れフィルタと前記第1の1次遅れフィルタの入力から前記第1の1次遅れフィルタの出力を引く減算器とを有する高域通過フィルタと、通過させる帯域の上限と関係する第2の時定数の第2の1次遅れフィルタを有する高域通過フィルタを直列に接続したものであることを特徴とする請求項8に記載の電力変換装置。
- 前記脈動検出部が、補正ゲインを演算する補正ゲイン演算部、前記帯域通過フィルタの出力と前記補正ゲイン演算部が出力する前記補正ゲインを乗算する乗算器を有し、
前記乗算器の出力が前記脈動検出部の出力となることを特徴とする請求項8に記載の電力変換装置。 - 前記補正ゲイン演算部が出力する前記補正ゲインが、前記インバータが出力する交流電圧の周波数により変化することを特徴とする請求項12に記載の電力変換装置。
- 前記電圧制御部が、前記脈動成分に応じて前記インバータが出力する交流電圧の周波数の指令値を制御することを特徴とする請求項1ないし請求項3の何れかに記載の電力変換装置。
- 前記電圧制御部が、前記脈動成分に応じて前記インバータが出力する交流電圧の振幅の指令値を制御することを特徴とする請求項1ないし請求項3の何れかに記載の電力変換装置。
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CN100438320C (zh) * | 1997-10-31 | 2008-11-26 | 株式会社日立制作所 | 电源转换设备 |
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JP4645139B2 (ja) * | 2004-10-04 | 2011-03-09 | ダイキン工業株式会社 | 電力変換装置 |
CN101127490A (zh) | 2006-03-21 | 2008-02-20 | 上海恒精机电设备有限公司 | 一种大功率晶体管变频电源 |
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JP5121200B2 (ja) * | 2006-09-26 | 2013-01-16 | 株式会社東芝 | 永久磁石電動機の制御装置 |
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2008
- 2008-10-31 WO PCT/JP2008/003132 patent/WO2010049976A1/ja active Application Filing
-
2009
- 2009-05-28 AU AU2009309187A patent/AU2009309187B9/en not_active Ceased
- 2009-05-28 JP JP2009544341A patent/JP4433099B1/ja not_active Expired - Fee Related
- 2009-05-28 EP EP09823203.6A patent/EP2346151A4/en not_active Withdrawn
- 2009-05-28 CN CN2009801437198A patent/CN102197580B/zh not_active Expired - Fee Related
- 2009-05-28 US US13/123,434 patent/US8542502B2/en not_active Expired - Fee Related
- 2009-05-28 RU RU2011121873/07A patent/RU2462806C1/ru not_active IP Right Cessation
- 2009-05-28 WO PCT/JP2009/002349 patent/WO2010050086A1/ja active Application Filing
- 2009-05-28 KR KR1020117008453A patent/KR101175030B1/ko not_active IP Right Cessation
- 2009-05-28 MX MX2011004387A patent/MX2011004387A/es active IP Right Grant
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2011
- 2011-12-09 HK HK11113346.1A patent/HK1159334A1/xx not_active IP Right Cessation
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Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JP2012039753A (ja) * | 2010-08-06 | 2012-02-23 | Toshiba Corp | 車両用補助電源装置 |
US20120065806A1 (en) * | 2011-05-06 | 2012-03-15 | General Electric Company | Method for measuring energy usage in an appliance |
JP2014100065A (ja) * | 2014-03-05 | 2014-05-29 | Toshiba Corp | 車両用補助電源装置 |
Also Published As
Publication number | Publication date |
---|---|
KR101175030B1 (ko) | 2012-08-17 |
WO2010049976A1 (ja) | 2010-05-06 |
EP2346151A4 (en) | 2014-07-30 |
AU2009309187B2 (en) | 2013-06-06 |
AU2009309187A1 (en) | 2010-05-06 |
HK1159334A1 (en) | 2012-07-27 |
US8542502B2 (en) | 2013-09-24 |
US20110194318A1 (en) | 2011-08-11 |
RU2462806C1 (ru) | 2012-09-27 |
AU2009309187B9 (en) | 2013-12-19 |
KR20110053280A (ko) | 2011-05-19 |
MX2011004387A (es) | 2011-06-16 |
JPWO2010050086A1 (ja) | 2012-03-29 |
EP2346151A1 (en) | 2011-07-20 |
CN102197580B (zh) | 2013-11-20 |
JP4433099B1 (ja) | 2010-03-17 |
CN102197580A (zh) | 2011-09-21 |
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