WO2006045226A1 - Procede et equipement pour demodulation par egalisation 8psk dans des systemes edge - Google Patents

Procede et equipement pour demodulation par egalisation 8psk dans des systemes edge Download PDF

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Publication number
WO2006045226A1
WO2006045226A1 PCT/CN2004/001241 CN2004001241W WO2006045226A1 WO 2006045226 A1 WO2006045226 A1 WO 2006045226A1 CN 2004001241 W CN2004001241 W CN 2004001241W WO 2006045226 A1 WO2006045226 A1 WO 2006045226A1
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module
signal
sequence
channel parameter
metric
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PCT/CN2004/001241
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English (en)
Chinese (zh)
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Gang Xiong
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Zte Corporation
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Priority to CNB2004800436674A priority Critical patent/CN100452890C/zh
Priority to PCT/CN2004/001241 priority patent/WO2006045226A1/fr
Publication of WO2006045226A1 publication Critical patent/WO2006045226A1/fr

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L25/03178—Arrangements involving sequence estimation techniques
    • H04L25/03248—Arrangements for operating in conjunction with other apparatus
    • H04L25/03292—Arrangements for operating in conjunction with other apparatus with channel estimation circuitry
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
    • H04L25/03006—Arrangements for removing intersymbol interference
    • H04L2025/0335—Arrangements for removing intersymbol interference characterised by the type of transmission
    • H04L2025/03375—Passband transmission
    • H04L2025/03401—PSK

Definitions

  • the present invention relates to a method and apparatus for equalization demodulation in the field of mobile communications, and more particularly to a method and apparatus for 8PSK equalization demodulation for an EDGE (Enhanced Da ta tes for GSM Evoluting) system.
  • EDGE Enhanced Da ta tes for GSM Evoluting
  • the GSM system which is the second generation mobile cellular communication system, has been widely used worldwide.
  • HSCSD High Speed Circuit Switched Data
  • GPRS General Packet Radio Service
  • HSCSD and GPRS adopt a multi-slot operation mode
  • the data transmission rate has been improved to some extent, but it still uses the modulation method of GMSK (Gaussian Minimum Shift Keying), and the third generation mobile
  • GMSK Gausian Minimum Shift Keying
  • the wide-area coverage of the 384 kb it/s data rate of the letter system and the local coverage of the data rate of approximately 2 Mb it/s are still far-reaching, so it is necessary to adopt more advanced communication and signal processing techniques to further expand the GSM system.
  • ETSI European Telecommunications Standards Institute
  • ETSI European Telecommunications Standards Institute
  • the figure is a basic schematic diagram of a channel model of a mobile communication system.
  • the baseband receiver receives the data transmitted through the wireless channel port.
  • the data is first demodulated by the demodulation module for the received baseband I and Q signals, and the demodulated result is sent to the channel decoding module for channel decoding.
  • the channel decoding module For the control channel, the transmission information of the system can be obtained directly; and for the traffic channel, the source decoding is required to obtain the voice and data sent by the system.
  • the demodulation module is located at the front end of the receiver, and it can be seen that the demodulation performance is good or not.
  • the connection determines the performance of the entire mobile communication system.
  • EDGE introduces a multi-level digital modulation scheme, 8PSK modulation. Since 8PSK modulation is a linear modulation, three consecutive bits are mapped to one symbol of the I/Q coordinates, thereby providing higher bit rate and spectral efficiency, and the implementation complexity is moderate.
  • the modulation of GMSK used in the GSM system is also part of the EDGE modulation scheme.
  • the symbol rates of both modulation modes are 271kbi t/s, and the net bit rate per time slot is 22. 8kbi t/s (GMSK) and 69. 2kb i t /s (8PSI ). 8PSK modulation is used for the user's data channel, and GMSK is used for all control channels on the GPRS 200kHz carrier.
  • the channel characteristics of the wireless channel are very poor, mainly manifested by multipath fading and Doppler fading.
  • Multipath fading can cause inter-symbol interference between signals, and the receiving end must use equalization techniques to eliminate the effects of the channel.
  • Equalization compensates for amplitude and delay in the channel by an equalizer in the receiver to eliminate inter-symbol interference.
  • the demodulator must estimate the original modulated data to the greatest extent possible in the received interfered signal. In order for the demodulator to perform this work, each burst sequence contains a predetermined sequence that the receiver can recognize. That is, the training sequence is such that the receiver can estimate the signal distortion caused by the propagation.
  • Equalization techniques are generally classified into linear equalization methods, nonlinear equalization methods, and maximum likelihood sequence equalization (MLSE).
  • the most likelihood sequence equalization method is used as an optimal sequence estimation method in a channel with intersymbol interference, and is often used in an equalizer of a mobile radio channel.
  • the equalizer based on the Vi ter bi algorithm is commonly used to implement the MLSE.
  • M the total number of states of the channel
  • Z the computational complexity of the MLSE algorithm based on the Vi terbi algorithm depends on M and L. When M is large, the computational complexity is still very high even when L is small.
  • the optimal Vi terbi algorithm can generally be used for demodulation, and the dispersion length in the channel is generally taken as 6 in the system, so the computational complexity is not very high.
  • Figure 2 is in the EDGE protocol.
  • Chinese patent 01112664. 7 proposes an adaptive 8PSK modulation equalization demodulation implementation method for EDGE technology in the third generation mobile communication system.
  • the inverted signal is E-filtered and the output will be output.
  • coherent demodulation is performed to determine the demodulated symbols, and then the coherent demodulated data is used to perform N iterative path searches (N rf is the number of iterations, generally For 1 or 2), the sequence with the largest likelihood function value is selected from all possible sequences as the output sequence.
  • N rf is the number of iterations, generally For 1 or 2
  • the sequence with the largest likelihood function value is selected from all possible sequences as the output sequence.
  • the computational complexity is reduced to .
  • the invention has a small amount of calculation and a high system achievability, the performance of the algorithm for the decentralized demodulation is not fully stipulated in the EDGE protocol, and is not suitable for implementation in the actual EDGE system. Summary of the invention
  • the object of the present invention is to provide a method and apparatus for 8PSK equalization demodulation for an EDGE system by reducing the number of states and selecting a maximum likelihood sequence from all possible sequences.
  • the output sequence can greatly reduce the computational complexity and ensure the performance of the baseband demodulation system while satisfying the EDGE ⁇ specification.
  • the present invention provides a method for 8PSK equalization demodulation for an f EDGE system, comprising the following steps:
  • Step 1 using the ⁇ 3 ' 8 for the received I and Q signals;
  • Step 2 Perform correlation on the inverted signal to obtain an estimated channel parameter
  • Step 3 Determine the time advance amount and the energy and the maximum signal according to the estimated value of the channel parameter, and estimate the value of the channel;
  • Step 4 Match and filter the inverted signal according to the estimated value of the energy and the maximum channel parameter
  • Step 5 Using the estimated energy and the maximum channel parameter to estimate the singularity and matching the filtered signal, find the maximum likelihood sequence, and output the maximum likelihood sequence;
  • Step 6 Convert the output maximum likelihood sequence symbol value into a bit value.
  • Step 53 Select a maximum sub-branch metric from the calculated sub-branch metrics, save the maximum sub-branch metric as a branch metric of the state transition, and save the symbol value of the branch metric;
  • Step 54 Branches in each path The metric is added to the surviving metric of the previous path stored in the previous state of the pair to obtain the cumulative metric of the four paths;
  • Step storm 55 Select and store a path with the largest cumulative amount from the two paths entering the state as the new surviving path, and the maximum metric is used as the surviving metric of the determinate, and all other non-surviving paths are deleted at the same time;
  • Step 56 If k ⁇ the length of the sequence to be demodulated, go to step 52; otherwise, compare the surviving metrics of the respective states to obtain a maximum surviving metric, and the surviving sequence corresponding to the largest surviving metric is the maximum likelihood sequence.
  • the invention also provides an 8PSK equalization demodulation device suitable for an EDGE system, comprising: a signal inversion module, a channel estimation module, a delay synchronization module ⁇ matching filtering module, and a balanced demodulation module and a symbol conversion module, wherein
  • the signal 3 conversion module has an input end connected to the signal sampling output end of the receiver end, configured to invert the sampled 8PSK signal, and simultaneously output the inverted signal to the channel estimation module and the matched filtering module;
  • the channel estimation module is configured to correlate the input training sequence with the inverted signal to obtain an estimated value of the channel parameter, and output the estimated value of the obtained channel parameter to the delay synchronization module;
  • the delay synchronization module is configured to obtain a timing advance according to an estimated value of the input channel parameter, determine an estimated channel parameter with the largest energy, and simultaneously input the channel parameter estimated value with the largest energy to the matched filtering module.
  • equalization demodulation module is configured to obtain a timing advance according to an estimated value of the input channel parameter, determine an estimated channel parameter with the largest energy, and simultaneously input the channel parameter estimated value with the largest energy to the matched filtering module.
  • the matched filtering module is configured to match and filter the channel parameter estimation value with the largest energy output from the delay synchronization module and the inverted nickname output from the signal inversion module, and The filtered signal is output to the equalization demodulation module;
  • the equalization demodulation module is configured to search for a maximum likelihood sequence according to the input filtered signal and the channel parameter estimated value with the largest energy, and output the obtained fishing symbol value to the symbol conversion module;
  • the symbol conversion module is configured to convert the input symbol value into a bit value corresponding thereto.
  • the invention adopts the reduced state Vi terb i algorithm to perform equalization demodulation on the input baseband digital I and Q signals, and selects the maximum likelihood sequence as the output sequence from all possible sequences, under the premise of meeting the EDGE protocol specification. It can greatly reduce the complexity of i-time calculation, and solve various distortions of signals in the wireless channel in the EDGE system, such as the occurrence of zeros in the channel special 'I', especially the inter-symbol interference caused by the multipath effect. Illustration
  • 1 is a basic schematic diagram of a channel model of an existing mobile communication system
  • Figure 2 is a constellation diagram of 8PSK in the existing EDGE protocol
  • Figure 3 is a flow chart of the method of the present invention.
  • FIG. 4 is a disk diagram of a mesh transfer in the present invention.
  • Figure 5 is a schematic diagram of 8PSK subset splitting in the present invention.
  • FIG. 6 is a structural view of the apparatus of the present invention. detailed description
  • the method of the present invention is applicable to 8PSK equalization demodulation of an EDGE system.
  • the maximum likelihood sequence is selected from all possible sequences as an output sequence, which can be greatly reduced under the premise of satisfying the EDGE protocol specification.
  • the computational complexity, specifically, the flow of the method is as shown in FIG. 3, and includes the following steps:
  • Step 1 Invert the received I and Q signals by using ⁇ ⁇ / 8 ;
  • Step 2 Perform correlation on the inverted signal to obtain an estimated channel parameter
  • Step 3 Obtain time advance quantity and energy and maximum channel parameter estimation value according to the estimated value of the channel parameter, thereby performing delay synchronization; since the space signal transmission has a certain time delay, the transmission signal and the reception signal are required. Synchronizing in time, the timing advance is to achieve this synchronization, to ensure the correctness of the demodulation.
  • Step 4 matching and filtering the estimated value of the channel parameter and the inverse-synchronized signal
  • Step 5 using the estimated value of the channel parameter and the matched filtered signal, finding the maximum likelihood column, and making the maximum likelihood sequence Output as a demodulation result
  • Step 6 Convert the output maximum likelihood sequence symbol value into a bit value.
  • step 1 because of the protocol according to EDGE, the baseband modulation of 8PSK requires symbol rotation, that is, where k represents the index of the modulation symbol, and the rotation angle of each modulation is 3 ⁇ / 8 .
  • phase anti-rotation operation When demodulating 8PSK, the phase anti-rotation operation is required, and the phase anti-rotation operation is performed according to the following formula:
  • the received signal is received at the position of the jth sample point on the kth symbol, and 2 ⁇ is the real part and the imaginary part of the received signal respectively; for the inverted signal, » and 2 ) are respectively inverted signals y » The real and imaginary parts.
  • the present invention uses a look-up table method to obtain sine and cosine values. Because it is 2 weeks ( 2>k7v
  • one table stores the value of ⁇ 8 ), and the other one stores the value of 8 .
  • the real and imaginary parts in the equation (9) are obtained by querying the two, thus obtaining the respective inverted signals t).
  • an estimated value of the channel parameter is obtained by correlating the training sequence with the inverted signal.
  • each burst has 156.2 symbols, which occupies one time slot, about 5 s s, which is small compared with the channel fading period. Therefore, it can be considered that the channel time variation in a time slot has little effect.
  • the signal propagates through the air, there is a channel to influence it. If the mobile station is moving, the channel will change, but since the time slot of a time slot is very short, then the change of this channel can be considered negligible.
  • the training sequence ⁇ 26 symbols (about 96.2 ⁇ ⁇ ) is placed in the middle of the burst so that the channel parameters are considered to be constant in one time slot.
  • the sliding correlation method is used to obtain the parameters of the signal by using the orthogonal characteristics of the training sequence.
  • the estimated value of the channel parameter associated with the slipping of the signal after the training sequence can be expressed as:
  • ⁇ is the symbolic value of the training sequence
  • ) represents the estimated value of the signal at the position of the 'J' sample points on the first symbol, ) Expressed as a signal after flipping.
  • step 3 the advance of the time is found based on the estimated value of the signal obtained in the previous step, and the energy and the maximum estimated channel parameter are determined as the coefficients of the equalized, demodulated basic channel and matched filter.
  • the process of delay synchronization is the process of finding the maximum energy sum in the channel parameter estimates.
  • the formula for calculating the timing advance is:
  • ⁇ 4 argmax ⁇ n(k) ⁇ >
  • the timing advance is obtained by finding the sum of the energy of the gas, for example, the parameter estimates are a, b, c, d, e, then the energy sum of the different positions is
  • step 4 the estimated channel parameter output in step 3 is used as the input of the matched filter module, and matched and filtered with the inverted signal.
  • the coefficient of the matched filter that is, the coefficient (FIR filter) required to filter the signal, which is conjugated with the energy and the estimated value of the largest channel parameter.
  • step 5 the maximum likelihood sequence is searched for based on the channel parameter estimate of the input in step 3 and the matched filtered output signal, and the demodulated result is found.
  • the algorithm for finding the maximum likelihood sequence is a suboptimal algorithm for finding the maximum likelihood sequence.
  • the present invention mainly focuses on the complexity of the implementation of the salty demodulation equalization, and the basic principle is based on the Viterbi algorithm.
  • the algorithm for finding the maximum likelihood sequence of the sub-optimal includes the following steps:
  • the calculation formula for the sub-branch metric is:
  • Sub _ Branch _ Metric Re ⁇ i ⁇ Z k - ⁇ S ⁇ > where ⁇ is the estimated value of the symbol in the surviving path;
  • S I is an autocorrelation function of the synthesized channel
  • Step 53 Select a maximum secondary branch metric from the calculated secondary branch metric, save the maximum secondary branch metric as a branch metric of the state transition, and save the symbol value of the maximum secondary branch metric;
  • Step 54 Add the branch metric in each path to the surviving metric value of the previous path stored in the corresponding previous level state to obtain the cumulative metric value of the four paths; before or after the step 54 a state surviving symbol path history table, wherein the surviving symbol path history table is an array of length 5, and the symbol estimates stored on the surviving paths of the past 5 moments are saved ⁇
  • Step 55 Select and store a path with the largest cumulative amount from the two paths entering the state as a new surviving path, and the maximum metric is used as a surviving metric of the state, and all other non-surviving paths are deleted at the same time;
  • Step 56 If k ⁇ the long sequence of the sequence to be demodulated, go to step 52; otherwise, stop the iteration and compare the surviving metrics of each state, and the surviving sequence corresponding to the largest surviving metric is the maximum likelihood sequence.
  • FIG. 4 is a disk shape operation diagram of the mesh transfer according to the present invention.
  • the arrow indicates the branch, the state 2 / and 2.
  • +1 are the two states before the transition, and the state and /+16 are the two states after the transition.
  • the two adjacent states 2 / and 2 / +1 of the previous stage there are four branches.
  • four sub-branch metrics need to be calculated, and the largest one is selected from the sub-branch metrics.
  • each branch metric is added to the cumulative metric of the previous path stored in state 2 i or 2i+l of the previous level to obtain the accumulation of four paths Branch-UpO, Branch-Upl, BranctuDownO, and Branch-Downl. metric. (It should be noted that the branch metrics in these four paths are in the 4 sub-branch metrics: ⁇ large value.) Then compare the two current states and +16 under the corresponding two current states, each current state is left A path with a larger cumulative metric is used as the surviving path. At the same time, the value t of the current state is used as the surviving metric and the input bit corresponding to the surviving path is stored in the corresponding buffer, and the next level of calculation is prepared.
  • the symbol value in the subset 0 shown in Fig. 5 is input.
  • the value of the survivor metric is the largest value that compares the cumulative metrics in Branch-UpO and Branch_Upl.
  • the input ⁇ is the symbol value in subset 1 shown in Figure 5.
  • the value of the survivor metric is the largest value that compares the cumulative metrics in Branch-DownO and Branch-Down.
  • FIG. 5 is a schematic diagram of 8PSK subset splitting according to the present invention, dividing the 8PSK signal into a state with a small number, and according to this state, creating a disk map 0 of the mesh transfer as shown in FIG. 4.
  • 8PSK is divided into two subsets, denoted as subset 0 and subset 1, respectively.
  • Subset 0 contains the symbols 1, 3, 5, 7; and subset 1 encloses the symbols 0, 2, 4, 6.
  • the state transition in the grid diagram in the Vi teirbi: algorithm can be categorized as a transition of subset 0 and subset 1, rather than a shift of each symbol.
  • each state - "" ⁇ " ⁇ " ⁇ "*- 5 ⁇ represents each subset 0 or 1, rather than a value, but its corresponding symbol value needs to be stored in the survivor.
  • the present invention also provides an apparatus for 8PSK equalization demodulation for an EDGE system.
  • the structure of the apparatus is shown in FIG. 5.
  • the apparatus includes: a picture number inversion module 301, a channel estimation module 302, and a delay synchronization module 303.
  • the input end of the signal inversion module 301 is connected to the signal sampling output end of the receiver, and is used for inverting the sampled 8PSK signal, and simultaneously outputting the inverted signal to the channel estimation module 302 and the matched filtering mode: ⁇ 304;
  • the channel estimation module 302 is configured to correlate the input training sequence with the inverted signal. Obtaining an estimated value of the channel parameter, and outputting the estimated value of the obtained channel parameter to the delay synchronization module 303;
  • the delay synchronization module 303 is configured to obtain an advance amount of time according to the estimated value of the input channel parameter, determine the channel parameter estimation value with the largest energy, and simultaneously input the channel parameter estimation value with the largest energy to the matched filtering module 304 and the equalization.
  • the matching filtering module 304 is configured to perform matched filtering on the estimated value of the energy output from the delay synchronization module 303 and the inverted signal output from the signal inversion module 301, and output the matched filtered signal to the signal.
  • the equalization demodulation module 305 is configured to find the maximum likelihood sequence according to the input matched filtered signal and the energy maximum channel parameter estimation value, and output the obtained symbol value to the symbol conversion module 306;
  • the symbol conversion module 306 is operative to convert the input symbol values into corresponding bit values.
  • the equalization demodulation module 305 is the core of the apparatus for finding the maximum likelihood sequence, and the equalization demodulation module 305 uses the estimated channel parameter value and the output of the matched filter as the input of the equalization demodulation to find the maximum. The likelihood sequence, while outputting the result of the demodulation.
  • the value range of the DSP has a value of P.
  • the saved metrics are most likely to overflow, beyond the representation range of the DSP. Therefore, in the implementation of the DSP, it is necessary to ensure that there is no overflow during the operation, and it can adapt to a large dynamic range.
  • FIG. 5 is a schematic diagram of 8PSK subset splitting.
  • the 8PSK signal is segmented into a smaller number of states, and a mesh map is created based on this state.
  • 8PSK is divided into two subsets, denoted as subset 0 and subset 1, respectively.
  • Subset 0 contains the symbols 1, 3, 5, 7; and subset 1 contains the symbols 0, 2, 4, 6.
  • the state transition in the trellis diagram in the Vi terbi algorithm can then be seen as a transition of subset 0 and sub-1, rather than a shift of each symbol.
  • FIG. 4 is a disk diagram of the mesh transfer according to the present invention. For the two adjacent states 2 i and 2 i+l of the previous stage, there are four branches.
  • the branch metrics of the four branches and the received signal need to be calculated (please specify that the secondary branch metric is How to calculate, select the largest one from the sub-branch metric as the branch metric), and each branch metric is added to the previous metric and the cumulative metric of the previous Luoyang stored in state 2 i or 2 i+l to obtain four Path Branch—UpO, Branch—Upl, Branch—Dou and Branch—Lengl cumulative metrics. (It should be noted that the branch metrics in the four paths are the maximum of the four sub-branch metrics.) Then, in the corresponding two current states i and i+16, the current state is left tired. Only one path with a larger metric value is used as the surviving path. At the same time, the metric of the current state is stored as a surviving metric and the input bit corresponding to the surviving path is stored in the corresponding buffer, and the next level of calculation is prepared.
  • the apparatus further includes a training sequence module, and the training sequence module is configured to output, to the channel estimation module, a training sequence for correlating with the inverted signal.
  • the method of the invention comprehensively considers the performance, complexity, stability and operation speed of the equalization demodulation method, and adopts the reduced state Vi terbi algorithm to perform equalization demodulation on the input baseband digital I and Q signals to solve the EDGE system.
  • Various distortions of the medium signal in the wireless channel such as zero occurrence of channel characteristics, especially inter-symbol interference due to multipath effects.

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Abstract

Cette invention concerne un procédé et un équipement pour démodulation par égalisation 8PSK dans un système EDGE, ce procédé consistant: à inverser le signal I, Q reçu avec e-j3Πk/8; à rapporter le signal inversé pour obtenir la valeur d'évaluation du paramètre de canal; en fonction de cette valeur d'évaluation de paramètre de canal, à effectuer une synchronisation de retard et à déterminer le temps d'avance et l'énergie, ainsi que la valeur d'évaluation de paramètre de canal la plus élevée; à filtrer par appariement la valeur d'évaluation du paramètre de canal avec le signal inversé et synchronisé; en utilisant cette valeur d'évaluation du paramètre de canal et le signal filtré par appariement, à rechercher la séquence de probabilité maximum et à émettre cette séquence de probabilité maximum sous la forme du résultat de la démodulation; et à convertir cette séquence de probabilité maximum émise en valeur binaire. Cette invention concerne également un équipement pour démodulation par égalisation 8PSK dans un système EDGE. En réduisant le nombre d'états, en sélectionnant la séquence de probabilité maximum parmi toutes les séquences possibles comme séquence de sortie, à la condition de satisfaire la spécification du protocole EDGE, cette invention permet de réduire la complexité des calculs et garantit les performances de la démodulation en bande de base.
PCT/CN2004/001241 2004-10-29 2004-10-29 Procede et equipement pour demodulation par egalisation 8psk dans des systemes edge WO2006045226A1 (fr)

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CN105024962A (zh) * 2015-05-25 2015-11-04 中国电子科技集团公司第十研究所 Gmsk信号的低复杂度相干解调方法
CN114401174A (zh) * 2022-01-21 2022-04-26 中国电子科技集团公司第五十四研究所 一种基于soqpsk和psp的联合相位跟踪检测方法

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CN1389994A (zh) * 2001-06-01 2003-01-08 上海大唐移动通信设备有限公司 一种适用于edge系统的8psk数字调制方法
CN1394048A (zh) * 2001-07-04 2003-01-29 华为技术有限公司 八相移相键控调制方法及装置
CN1443011A (zh) * 2002-03-05 2003-09-17 深圳市中兴通讯股份有限公司上海第二研究所 一种用于移动通信系统的均衡解调方法

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WO2008151254A1 (fr) * 2007-06-04 2008-12-11 The Regents Of The University Of California Procédés de génération de tissu et compositions formulées de tissu
CN103001899A (zh) * 2011-09-15 2013-03-27 京信通信系统（中国）有限公司 用于gsm通信系统的自适应均衡解调方法及装置
CN105024962A (zh) * 2015-05-25 2015-11-04 中国电子科技集团公司第十研究所 Gmsk信号的低复杂度相干解调方法
CN105024962B (zh) * 2015-05-25 2018-02-23 中国电子科技集团公司第十研究所 Gmsk信号的低复杂度相干解调方法
CN114401174A (zh) * 2022-01-21 2022-04-26 中国电子科技集团公司第五十四研究所 一种基于soqpsk和psp的联合相位跟踪检测方法
CN114401174B (zh) * 2022-01-21 2023-12-29 中国电子科技集团公司第五十四研究所 一种基于soqpsk和psp的联合相位跟踪检测方法

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