Classifications

• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M3/00—Conversion of DC power input into DC power output
  • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
  • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
  • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
  • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
  • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
  • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
  • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
• • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
  • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
  • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
  • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
  • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

• the present invention relates to a DC-DC converter, and more particularly, to a DC-DC converter including a diode module capable of reducing switching loss.
• a DC-DC converter that converts an input DC voltage into a stabilized desired DC voltage by switching control of a semiconductor device has advantages such as high efficiency, easy size reduction, and easy weight reduction. At present, it is applied to the power supply of various electronic devices, the motor control based on the inverter technology, the lighting circuit of various discharge tubes, and the like, and is an essential component thereof.
• the DC-DC converter 100 has a field-effect transistor Ql as a main switching element, a flywheel diode D3, a choke coil Ll, an output capacitor C5, and a control circuit 102. Indicates a DC power supply, and resistor R1 indicates a load.
• the capacitor C1 is the junction capacitance between the drain and source of the field-effect transistor Q1.
• the DC power supply Vi has a positive terminal connected to a drain, which is one end of the field effect transistor Q1, and a negative terminal grounded.
• the source which is one end of the field effect transistor Q1 is connected to the power source of the flywheel diode D3 and one end of the choke coil L1, and the other end of the choke coil L1 is connected to one end of the output capacitor C5.
• the other end of the output capacitor C5 and the anode of the flywheel diode D3 are grounded.
• the control circuit 102 has a detection terminal connected to the load R1 side of the choke coil L1, and an output terminal connected to the gate of the field effect transistor Q1.
• Patent Document 1 discloses a wide range of input / output.
• a configuration of a resonance circuit using a junction capacitance of a switching element or a rectifying element is disclosed.
• Patent Document 1 JP 2003-189602 A
• this rectifier circuit part is a single module, it will be a circuit with at least three terminals, and only a flywheel diode that is a two-terminal element will be used.
• this rectifier circuit part is a single module, it will be a circuit with at least three terminals, and only a flywheel diode that is a two-terminal element will be used.
• a flywheel diode that is a two-terminal element
• the present invention uses a diode module that can reduce switching loss, can cope with a wide range of input / output voltage fluctuations, and can easily replace a conventional circuit with the circuit of the present invention.
• the purpose was to provide a DC-DC converter.
• a DC-DC converter includes a main switching element, a choke coil, an output capacitor, and a diode module, and performs a DC operation by turning on and off the main switching element.
• a DC-DC converter for converting a voltage of a power supply and outputting different DC voltages wherein the diode module includes a first series circuit including an auxiliary switching element and a resonance capacitor, a flywheel diode, And a second series circuit comprising a resonance coil, wherein the first and second series circuits are connected in parallel.
• the diode module includes a first diode connected in parallel to the resonance capacitor.
• the diode module includes a second diode connected between a connection point between the auxiliary switching element and the resonance capacitor and a connection point between the flywheel diode and the resonance coil. It is characterized by the following.
• one end of the main switching element is connected to one end of a DC power supply, and the other end of the main switching element is connected to the choke capacitor.
• the other end of the choke coil is connected to one end of the output capacitor, and the diode module is connected to a connection point between the main switching element and the choke coil and the other end of the DC power supply. Connected between them to perform a step-down operation.
• one end of the choke coil is connected to one end of a DC power supply, and the other end of the choke coil is connected to one end of the main switching element.
• the other end of the main switching element is connected to the other end of the DC power supply, the diode module power is connected between a connection point between the choke coil and the main switching element, and one end of the output capacitor, and the voltage is increased. The operation is performed.
• one end of the main switching element is connected to one end of a DC power supply, and the other end of the main switching element is connected to one end of the choke coil.
• the other end of the choke coil is connected to the other end of the DC power supply, and the diode module is connected between a connection point between the main switching element and the choke coil and one end of the output capacitor. It is characterized by performing buck-boost operation.
• one end of the first choke coil is connected to one end of a DC power supply, and the other end of the first choke coil is connected to the main switching element. And the other end of the main switching element is connected to the other end of the DC power supply, and the other end of the coupling capacitor is connected to one end of a second choke coil.
• the other end of the choke coil is connected to one end of the output capacitor, and the diode module is connected between the connection point between the coupling capacitor and the second choke coil and the other end of the DC power supply. And perform a step-up / step-down operation.
• one end of the first choke coil is connected to one end of a DC power supply, and the other end of the first choke coil is connected to the main switching element. And the other end of the main switching element is connected to the other end of the DC power supply, and the other end of the coupling capacitor is connected to the other end of the coupling capacitor.
• 2 is connected to one end of the choke coil, the other end of the second choke coil is connected to the other end of the DC power supply, and the diode module is connected to a connection point between the coupling capacitor and the second choke coil. Connected between one end of the output capacitor and a step-up / step-down operation.
• one end of the main switching element is connected to one end of a DC power supply, and the other end of the main switching element is connected to one end of the first choke coil.
• one end of the coupling capacitor, the other end of the first choke coil is connected to the other end of the DC power supply, the other end of the coupling capacitor is connected to one end of the second choke coil, and the second The other end of the second choke coil is connected to one end of the output capacitor, and the diode module is connected between the connection point of the coupling capacitor and the second choke coil and the other end of the DC power supply.
• a step-up / step-down operation is connected between the connection point of the coupling capacitor and the second choke coil and the other end of the DC power supply.
• the DC-DC converter according to the present invention is characterized in that a capacitor is connected in parallel with the main switching element.
• the DC-DC converter according to the present invention is characterized in that a third diode is provided between the connection point between the resonance coil and the flywheel diode and the DC power supply.
• the diode module in which the series circuit including the auxiliary switching element and the resonance capacitor and the series circuit including the flywheel diode and the resonance coil are connected in parallel The switching loss of the main and auxiliary switching elements and the recovery current of the flywheel diode are reduced, and PWM control over a wide input / output voltage range is possible. Also, since the diode module of the present invention is modularized as a two-terminal element, the flywheel diode in the conventional DC-DC converter can be easily replaced with the diode module of the present invention.
• connecting the first diode in parallel with the resonance capacitor in the diode module prevents the voltage of the resonance capacitor from being reversed, Even if the duty ratio of the main switching element is very small, the DC-DC converter can operate normally.
• the DC-CD converter according to the present invention can be easily realized.
• FIG. 1 is a circuit diagram showing a step-down DC-DC converter as a DC-DC converter according to a first embodiment of the present invention.
• FIG. 2 (a) is a circuit diagram showing one embodiment of a diode module according to the present invention
• FIG. 2 (b) is a circuit diagram showing another embodiment of the diode module according to the present invention.
• FIG. 3 is a circuit diagram of the circuit diagram of FIG. 1, which is simplified for explanation.
• FIG. 4 is a timing chart showing the operation of the DC-DC converter according to the first embodiment of the present invention.
• FIG. 5 is a current state diagram showing the operation of the DC-DC converter according to the first embodiment of the present invention.
• FIG. 5 (a) shows a period tO tl shown in the timing chart of FIG. 4, and FIG.
• FIG. 6 is a current state diagram showing an operation of the DC-DC converter according to the first embodiment of the present invention.
• FIG. 6 (a) shows a period t4 to t5 shown in the timing chart of FIG. 4, and FIG.
• the periods t5-6 and (c) indicate the current states of the periods t6-7 and (d), respectively, and the current states of the periods t7-8 similarly, respectively.
• FIG. 7 is a current state diagram showing an operation of the DC-DC converter according to the first embodiment of the present invention.
• FIG. 7 (a) shows a period t8-19 shown in the timing chart of FIG. 4, and FIG. The current state during the period t9-tlO is shown in FIG. Garden 8]
• (a) is a current state diagram when the junction capacity of the flywheel diode is considered in the first embodiment of the present invention, and
• (b) is a timing chart thereof.
• FIG. 10 is a circuit diagram showing another aspect of the connection position of the diode in the first embodiment of the present invention.
• FIG. 11 is a circuit diagram showing a step-up DC-DC converter as a second embodiment of the DC-DC converter according to the present invention.
• FIG. 12 is a circuit diagram showing a step-up / step-down DC-DC converter as a third embodiment of the DC-DC converter according to the present invention.
• FIG. 13 is a circuit diagram showing a Cuk-type DC-DC converter as a fourth embodiment of the DC-DC converter according to the present invention.
• FIG. 14 is a circuit diagram showing a DC-DC converter of the Sepic type as a fifth embodiment of the DC-DC converter according to the present invention.
• FIG. 15 is a circuit diagram showing a Zeta-type DC-DC converter as a DC-DC converter according to a sixth embodiment of the present invention.
• FIG. 16 is a circuit diagram showing a conventional step-down DC-DC converter.
• FIG. 1 is a circuit diagram showing a first embodiment of a DC-DC converter according to the present invention.
• a DC-DC converter 10 includes a main switching element Ql, a choke coil Ll, an output capacitor C5, a diode module 20, and a control circuit 12, and a voltage Vi indicates a DC power supply, and a resistor R1 indicates a load.
• the main switching element Q1 is preferably made of a field-effect transistor, and the diode D1 and the capacitor C1 connected in parallel to the main switching element Q1 have a body diode and a drain, respectively, built in the field-effect transistor. This shows the source-to-source junction capacitance.
• This DC-DC converter 10 is a step-down DC-DC converter, in which the drain, which is one end of main switching element Q1, is connected to the positive terminal of DC power supply Vi, and the other end of main switching element Q1. Is connected to one end of the choke coil L1, the other end of the choke coil L1 is connected to one end of the output capacitor C5, and the negative terminal of the DC power supply Vi and the other end of the output capacitor C5 are grounded.
• the diode module 20 is connected between a connection point of the main switching element Q1 and the choke coil L1 and a negative terminal of the DC power supply Vi.
• the control circuit 12 has a detection terminal connected to the load R1 of the choke coil L1, and an output terminal connected to the main switching element and the gate of an auxiliary switching element Q2 of the diode module 20, which will be described later.
• FIGS. 2A and 2B are circuit diagrams showing one embodiment of the diode module 20 according to the present invention.
• a diode module 20 includes a first series circuit including an auxiliary switching element Q2 and a resonance capacitor C4, and a flywheel die.
• the second series circuit including the diode D3 and the resonance coil L2 is connected in parallel.
• a first diode D5 is connected to the resonance capacitor C4 in parallel with the capacitor C4.
• the power source of the second diode D4 is connected to the connection point between the auxiliary switching element Q2 and the resonance coil L2, and the anode of the second diode D4 is connected to the connection point between the flywheel diode D3 and the resonance coil L2. It has been.
• the auxiliary switching element Q2 is preferably made of a field effect transistor, and the diode D2 connected in parallel to the auxiliary switching element Q2 is a body diode built in the field effect transistor.
• the capacitor C3 connected in parallel with the flywheel diode D3 indicates the connection capacitance of the flywheel diode D3.
• its power source and anode can be defined as shown according to the polarity of the flywheel diode D3.
• the diode module 20 also includes a first series circuit including an auxiliary switching element Q2 and a resonance capacitor C4, a flywheel diode D3, and a resonance coil L2.
• a second series circuit is configured to be connected in parallel, and a first diode D5 is connected to the resonance capacitor C4 in parallel with the capacitor C4.
• the anode of the second diode D4 is connected to the connection point between the auxiliary switching element Q2 and the resonance coil L2, and the force of the second diode D4 is connected to the connection point between the flywheel diode D3 and the resonance coil L2.
• each of the elements D3, D4, D5, and Q2 is inverted with respect to the diode module 20 shown in FIG. 2 (a). It has a connected configuration. Again, the power source and anode of diode module 20 are defined as shown, according to the polarity of flywheel diode D3.
• the flywheel diode D3 has a sufficient withstand voltage and generates noise due to ringing described later. If it is not necessary to consider the occurrence, the second diode D4 may not be necessarily used. When the second diode D4 is not provided, the connection order of the series circuit consisting of the auxiliary switching element Q2 and the resonance capacitor C4 can be reversed. The connection order of the series circuit including the coil L2 may be reversed.
• each switching element Ql, Q2 is a field effect transistor.
• a bipolar transistor or an IGBT Insulated Gate
• Another switching element such as a bipolar transistor may be used.
• the diode D1 and the capacitor Cl connected in parallel with the main switching element Q1, the diode D2 connected in parallel with the switching element Q2, and the flywheel diode D3 are connected.
• Capacitor C3 can also be constituted by corresponding external components.
• the diode module 20 has a conventional step-down converter whose power source is connected to the connection point between the main switching element Q1 and the choke coil L1, and whose anode is connected to the negative terminal of the DC power supply Vi.
• a DC-DC converter 10 according to the present invention is realized by substituting a flywheel diode (D3 shown in FIG. 16) in a type DC-DC converter.
• the control circuit 12 drives the main switching element Q1 and the auxiliary switching element Q2 by PWM control so that they are turned on alternately with a period in which both are turned off.
• the choke coil L1 operates sufficiently as a substantially constant current source Io, and the resonance capacitor C4 is sufficiently larger than the junction capacitance of the auxiliary switching element Q2. It operates as a constant voltage source that supplies a large, substantially constant voltage VC4. Further, it is assumed that the on-resistance of the main switching element Q1 and the auxiliary switching element Q2 is substantially zero, and the forward voltage of each diode is substantially zero.
• the effect of the junction capacitance C3 of the flywheel diode D3 and the operation of the first diode D5 and the second diode D4 are described.
• the flywheel diode D3 is regarded as an ideal element having no junction capacitance, and the diode module 20 is configured without the first diode D5 and the second diode D4. I shall. More than Under the premise, the circuit diagram shown in FIG. 1 can be simplified as the circuit diagram shown in FIG.
• Vi is a constant DC voltage supplied from the DC power supply
• Io is a current flowing from the constant current source.
• VQ1 is the voltage applied across the main switching element Q1
• VQ2 is the voltage applied across the auxiliary switching element Q2
• VD3 is the voltage applied across the flywheel diode D3
• VL2 is the resonance coil L2.
• IQ1 is the current flowing through the main switching element Q1
• IQ2 is the current flowing through the auxiliary switching element Q2
• ID3 is the current flowing through the flywheel diode D3.
• the direction of the arrow shown in the figure is defined as the positive direction.
• IQ1 includes the current flowing through the junction capacitance C1 and the body diode D1 of the switching element Q1
• IQ2 also includes the current flowing through the body diode D2 of the switching element Q2.
• FIG. 4 shows the operation of the DC—DC converter 10 from the stage where the main switching element Q1 is in the ON state and is in a steady operation, until the main switching element Q1 is turned off and then turned on again. This will be described in detail with reference to the timing chart shown and the current state diagrams shown in FIGS.
• the main switching element Q1 is in the on state and the auxiliary switching element Q2 is in the off state.
• the main switching element Q1 is constant from the constant voltage power supply Vi via the main switching element Q1. Current Io is flowing.
• the voltage of VQ2 is “Vi + VC4”.
• flywheel diode D3 In period t2-3, as shown in FIG. 5 (c), flywheel diode D3 conducts and current ID3 starts to flow. Further, the capacitor C1 is charged by the current “Io—ID3”. At time t3, the voltage of VQ1 reaches “Vi + VC4”, VQ2 is zero, and VL2 is —VC Reach four.
• the current IQ2 flowing through the diode D2 flows through the auxiliary switching element Q2.
• ID3 increases linearly by the action of the resonance coil L2, and IQ2 is “ID3_Io”.
• IQ2 goes to zero and ID3 reaches Io.
• the time t4 at which the auxiliary switching element Q2 is turned on may be any time between the time t3 and the time t5.However, in order to reduce the conduction loss of the auxiliary switching element Q2, the time closer to the time t3 is shorter. good.
• time t8 when the main switching element Q1 is turned on can be any time between the time t7 and the time t9, To reduce the conduction loss of the child Ql, it is better to be close to time t7.
• ID3 becomes Io at time t9 IQ1 becomes zero.
• ID3 decreases linearly as shown in Fig. 4 due to the action of the resonance coil L2, and IQ1 decreases linearly in the positive direction.
• ID3 goes to zero and IQ1 reaches Io.
• VL2 becomes zero and VD3 becomes Vi.
• the operation returns to time tO, and this cycle is repeated.
• VQ1 is zero when the main switching element Q1 is turned off (time Ijtl) and turned on (time t8). Since VQ2 is zero when the switching element Q2 is turned on (time t4) and turned off (time t6), zero voltage switching is realized in these switching elements Ql and Q2, and the switching loss is greatly reduced. . Also, since ID3 decreases slowly (t6 tlO), the recovery current of the flywheel diode D3 during the reverse recovery time can be significantly reduced.
• the DC-DC converter 10 includes a diode module 20 having a second diode D4 shown in FIGS. 2 (a) and 2 (b).
• the occurrence of such ringing can be suppressed. That is, in the diode module 20 of the present embodiment, as shown in FIG. 9A, the resonance energy flows out to the capacitor C4 via the diode D4. Therefore, as shown in the timing chart of FIG. 9 (c), the voltage VD3 of the flywheel diode D3 is “Vi + VC4 ”and is clamped to that value. After time t1l, charging and discharging of the junction capacitance C3 does not occur as shown in FIG. 9 (b).
• a third diode (also denoted by reference numeral D4) may be provided, in which case the voltage V D3 of the flywheel diode D3 is clamped to Vi.
• the DC-DC converter 10 including the diode module 20 without the first diode D5 consider obtaining a very low output voltage using a low duty ratio close to 0%, for example. .
• the period t7 tlO (Fig. 6 (d), Fig. 7 (a), Fig. 7 (b)) in the timing chart of Fig. 4 becomes very short, and sufficient energy is supplied to the resonance coil L2. Since accumulation is not possible, the capacitor C1 cannot be charged to the voltage of “Vi + VC4” during the period tl-t3 (FIGS. 5 (b) and 5 (c)). As a result, the capacitor C4 for resonance cannot be sufficiently charged during the period t3—15 (FIGS.
• the DC-DC converter 10 has the diode module 20 including the first diode D5 connected in parallel with the resonance capacitor C4, whereby the voltage of the resonance capacitor C4 is increased. This prevents VC4 from going in the opposite direction. As a result, the DC-DC converter 10 can operate normally even at an extremely low duty ratio close to 0%. When the DC-DC converter 10 is not used at such a low duty ratio, the diode D5 may not be used.
• a DC-DC converter according to the present invention is realized in a step-down circuit configuration, but the present invention is not limited to such a circuit configuration.
• the circuit configuration of The same operation and effect can be obtained by changing the flywheel diode that is used to the diode modules 20 and 20 shown in FIGS. 2A and 2B.
• a DC-DC converter according to the present invention is realized by incorporating a diode module 20 into a circuit configuration of a boost type, a buck-boost type, a Cuk type, a Sepic type, and a Zeta type.
• the details of the operation related to the diode module 20 are the same as the operation of the first embodiment described above with reference to FIGS. Then, a configuration unique to each embodiment will be described.
• FIG. 11 is a circuit diagram showing a DC-DC converter according to a second embodiment of the present invention.
• a DC-DC converter 30 is a step-up DC-DC converter, in which one end of a choke coil L1 is connected to a positive terminal, which is one end of a DC power supply Vi, and the other end of the choke coil L1 is mainly connected.
• the source which is the other end of the main switching element Q1, is connected to the negative terminal, which is the other end of the DC power supply Vi.
• the diode module 20 has its anode connected to the connection point of the choke coil L1 and the main switching element Q1, and its power source connected to one end of the output capacitor C5.
• FIG. 12 is a circuit diagram showing a third embodiment of the DC-DC converter according to the present invention.
• a DC-DC converter 40 is a step-up / step-down DC-DC converter.
• the drain, which is one end of the main switching element Q1 is connected to the positive terminal, which is one end of the DC power supply Vi, and the The source at the other end is connected to one end of the choke coil L1, and the other end of the choke coil L1 is connected to the negative terminal at the other end of the DC power supply Vi.
• the diode module 20 has its power source connected to the connection point between the main switching element Q1 and the choke coil L1, and its anode connected to one end of the output capacitor C5.
• FIG. 13 is a circuit diagram showing a DC-DC converter according to a fourth embodiment of the present invention.
• a DC-DC converter 50 is a Cuk-type DC-DC converter that performs a buck-boost operation.
• one end of the first choke coil L1 is connected to the positive terminal, which is one end of the DC power supply Vi, and the first choke coil L1 is connected to the first choke coil L1.
• the other end of LI is connected to the drain which is one end of the main switching element Ql and one end of the coupling capacitor C6, the source which is the other end of the main switching element Q1 is connected to the negative terminal which is the other end of the DC power supply Vi,
• the other end of the coupling capacitor C6 is connected to one end of the second choke coil L3, and the other end of the second choke coil L3 is connected to one end of the output capacitor C5.
• the diode module 20 has its power source connected to the connection point between the coupling capacitor C6 and the second choke coil L3, and its anode connected to the negative terminal of the DC power supply Vi.
• FIG. 14 is a circuit diagram showing a fifth embodiment of the DC-DC converter according to the present invention.
• a DC-DC converter 60 is a Sepic-type DC-DC converter that performs a step-up / step-down operation.
• one end of the first choke coil L1 is connected to the positive terminal, which is one end of the DC power supply Vi, and the other end of the first choke coil L1 is one end of the main switching element Q1.
• the other end of the main switching element Q1 is connected to the other end of the DC power supply Vi, and the other end of the coupling capacitor C6 is connected to one end of the second choke coil L3.
• the other end of the second choke coil L3 is connected to the negative terminal, which is the other end of the DC power supply Vi.
• the diode module 20 has an anode connected to a connection point between the coupling capacitor C6 and the second choke coil L3, and a power source connected to one end of the output capacitor C5.
• FIG. 15 is a circuit diagram showing a sixth embodiment of the DC-DC converter according to the present invention.
• a DC-DC converter 70 is a Zeta-type DC-DC converter that performs a buck-boost operation.
• the drain which is one end of the main switching element Q1
• the source which is the other end of the main switching element Q1
• the first choke coil L1 is connected to the negative terminal, which is the other end of the DC power supply
• the other end of the coupling capacitor C6 is connected to the second choke coil L3.
• the other end of the second choke coil L3 is connected to one end of the output capacitor C5.
• the diode module 20 has its power source connected to the connection point between the coupling capacitor C6 and the second choke coil L3, and its anode connected to the negative terminal of the DC power supply Vi. Connected c

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• 2004
  • 2004-04-30 JP JP2004135916A patent/JP4534223B2/ja not_active Expired - Fee Related
• 2005
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