EP3482454B1 - Phasengesteuertes antennenelement - Google Patents

Phasengesteuertes antennenelement Download PDF

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Publication number
EP3482454B1
EP3482454B1 EP17735448.7A EP17735448A EP3482454B1 EP 3482454 B1 EP3482454 B1 EP 3482454B1 EP 17735448 A EP17735448 A EP 17735448A EP 3482454 B1 EP3482454 B1 EP 3482454B1
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EP
European Patent Office
Prior art keywords
phase
antenna element
waveguide radiator
element according
waveguide
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Active
Application number
EP17735448.7A
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German (de)
English (en)
French (fr)
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EP3482454A1 (de
Inventor
Jörg Oppenländer
Alexander Mössinger
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Lisa Draexlmaier GmbH
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Lisa Draexlmaier GmbH
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
    • H01Q3/32—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by mechanical means
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/18—Phase-shifters
    • H01P1/182—Waveguide phase-shifters
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/42—Housings not intimately mechanically associated with radiating elements, e.g. radome
    • H01Q1/425—Housings not intimately mechanically associated with radiating elements, e.g. radome comprising a metallic grid
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/02—Waveguide horns
    • H01Q13/0241—Waveguide horns radiating a circularly polarised wave
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/02—Waveguide horns
    • H01Q13/025—Multimode horn antennas; Horns using higher mode of propagation
    • H01Q13/0258—Orthomode horns
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/20—Non-resonant leaky-waveguide or transmission-line antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/28—Non-resonant leaky-waveguide or transmission-line antennas; Equivalent structures causing radiation along the transmission path of a guided wave comprising elements constituting electric discontinuities and spaced in direction of wave propagation, e.g. dielectric elements or conductive elements forming artificial dielectric
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/24—Polarising devices; Polarisation filters 
    • H01Q15/242—Polarisation converters
    • H01Q15/244—Polarisation converters converting a linear polarised wave into a circular polarised wave
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H01Q21/0075—Stripline fed arrays
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/061—Two dimensional planar arrays
    • H01Q21/064—Two dimensional planar arrays using horn or slot aerials

Definitions

  • the invention relates to a phase-controlled antenna element for phase-controlled group antennas, in particular for the GHz frequency range.
  • a phase-controlled antenna element is intended to set, control and monitor the phase position of an electromagnetic wave emitted and / or received by the antenna element in a simple manner.
  • the antenna directional diagram of stationary antenna groups can be spatially changed with the aid of variable, controllable phase actuators ("phase shifters").
  • phase shifters variable, controllable phase actuators
  • the main beam can be swiveled in different directions.
  • the phase control elements change the relative phase position of the signals that are received or sent by various individual members of the group antennas. If the relative phase position of the signals of the individual antennas is adjusted accordingly with the aid of the phase control elements, the main beam of the antenna diagram of the group antenna points in the desired direction.
  • phase actuators are mostly composed of non-linear solids ("solid state phase shifters”), mostly ferrites, microswitches (MEMS technology, binary switches), or liquid crystals (“liquid crystals”). All these However, technologies have the disadvantage that they often lead to a considerable loss of signal, since part of the high-frequency power is dissipated in the phase control elements. In particular in the case of applications in the GHz range, the antenna efficiency of the group antennas is greatly reduced as a result.
  • phase control elements must always be accommodated in the feed networks of the group antennas. This leads to an undesirable increase in the dimensions of the feed networks and thus of the group antennas themselves.
  • the group antennas are typically very heavy.
  • Phased array antennas using conventional phase actuators are very expensive. This prevents their use in particular for civil applications above 10 GHz.
  • a further problem is the exact control of the antenna pattern of the group antennas. Such a control is only possible if the amplitude relations and the phase relations of all signals which are sent or received by the antenna elements of the group antenna are accurate at every point in time (ie for every state) are known.
  • phase control elements allows the reliable instantaneous determination of the phase position of the signal after the phase control element. For this it would be necessary to be able to reliably determine the state of the phase control element at any time. However, this is practically impossible with solid-state, MEMS or liquid-crystal phase shifters.
  • Solid-state phase shifters also typically contain non-linear components, which makes determining the amplitude relationships very difficult or even impossible.
  • the attenuation values and the wave impedance of such phase shifters are typically dependent on the value of the phase rotation.
  • Phase shifters based on microswitches typically work in binary mode. With binary phase shifters, the phase position of the individual signals can only be set granularly in certain steps. A highly precise alignment of the antenna diagram is not possible in principle.
  • a phase-controlled antenna array which includes electronically controllable lenses and MEMS phase shifters.
  • the DE9200386U1 shows an antenna structure based on the Yagi principle, in which parasitic elements made of circular, centrally perforated disks are pushed onto a support tube between sleeve-shaped spacers.
  • the WO 02/084797 A1 a phased array antenna with a plurality of circularly polarized radiator elements, the array antenna comprising movement means which is used for the independent and angular rotation of at least a part of the radiator elements.
  • the phase-controlled antenna element consists of a waveguide radiator (1) with signal decoupling or coupling (7), into which a rotatable phase control element (2) is inserted, and a drive unit (6).
  • the phase control element comprises a holder (3), at least two polarizers (4) which are attached to the holder (3), and a connecting element (5).
  • Each of the at least two polarizers (4) can convert a circularly polarized signal into a linearly polarized signal.
  • the phase control element (2) is rotatably mounted in the waveguide radiator (1) and with the help of the connecting element (5) with the Drive unit (6) connected in such a way that the drive unit (6) can rotate the phase control element (2) around the axis (10) of the waveguide radiator (1), as shown in FIG Fig. 1 is illustrated like a sketch.
  • FIG. 2 The principle of operation of the invention is shown in Fig. 2 shown.
  • a wave (19a) incident in the waveguide radiator (1) with circular polarization and phase position ⁇ is transformed by the first polarizer (4a) into a wave with linear polarization (19b).
  • This wave of linear polarization is reconverted by the second polarizer (4b) into a wave with circular polarization (19c).
  • the phase control element (2) is now rotated by an angle ⁇ in the waveguide radiator (1) with the aid of the drive unit (6) and the connecting element (5), the polarization vector (19b) of the linear wave rotates between the two polarizers (4a) and ( 4b) in a plane perpendicular to the axis (10) (direction of propagation of the electromagnetic wave). Since the polarizer (4a) also rotates, the circular wave (19c) generated by the second polarizer (4b) now has a phase position of ⁇ + 2 ⁇ The circular wave (19c) with phase position ⁇ + 2 ⁇ can then can be decoupled from the waveguide radiator (1) with the aid of the signal decoupling or coupling (7).
  • phase control of the antenna element Due to the design of the phase control of the antenna element, the dependence of the phase angle difference between the outgoing (19c) and incoming (19a) circular wave on the rotation of the phase control element (2) is strictly linear, continuous and strictly 2 ⁇ periodic. In addition, any phase rotation or phase shift can be set continuously by the drive unit (6).
  • phase control element (2) Since the phase control element (2) is, from an electrodynamic point of view, a purely passive component which does not contain any non-linear components, its function is completely reciprocal. This means that a shaft which runs from bottom to top through the phase control element (2) is rotated in its phase in the same way as a shaft which runs from top to bottom through the phase control element (2).
  • phase position of a signal sent or received by the waveguide radiator (1) can thus be set as desired. Simultaneous transmission and reception is also possible.
  • the wave impedance of the waveguide radiator (1) is completely independent of the relative phase position of the incoming and outgoing wave.
  • phase control also works with practically no loss, since with an appropriate design the losses induced by the polarizers (4a, b) and the dielectric holder (3) are very small.
  • the total losses are less than 0.2 dB, which corresponds to an efficiency of more than 95%.
  • Conventional phase shifters have typically losses of several dB at these frequencies.
  • the phase-controlled antenna element according to the invention is therefore hardly different from a corresponding antenna element without phase control, as is e.g. is already used in antenna fields, distinguishable.
  • antenna fields of this type are implemented with phase-controlled antenna elements according to the invention, the RF properties, in particular antenna gain and antenna efficiency, of the antenna fields advantageously change only insignificantly, despite the additional phase control.
  • a further advantage of the device according to the invention is therefore that the phase control function and the antenna function are integrated in a single component and are nevertheless completely independent of one another.
  • the waveguide radiator (1) is preferably designed such that it contains at least one cylindrical waveguide piece (section). This ensures that a cylindrically symmetrical electromagnetic oscillation mode (mode) of circular polarization can develop in its interior, which can be transformed into a mode of linear polarization by the polarizers (4).
  • mode cylindrically symmetrical electromagnetic oscillation mode
  • the waveguide termination can, for example, be conical or stepped on one side.
  • the aperture of the waveguide radiator can also be designed, for example, conical, square or rectangular.
  • the waveguide radiator (1) As a horn radiator.
  • the dimensional design of the waveguide radiator (1) for a specific operating frequency band is carried out using the known methods of antenna technology.
  • An axis of rotation (10) for the phase control element (2) is preferably in the axis of symmetry of the cylindrical waveguide section, which the waveguide radiator (1) preferably contains. It can thus be ensured that the mode conversion by the polarizers (4) takes place in an optimal manner.
  • the at least two polarizers (4a) and (4b) are preferably mounted in the holder (3) perpendicular to the axis of rotation (10) and parallel to one another. The linear mode between the polarizers can then develop undisturbed.
  • the phase position of the wave (19a) emitted and / or received by the hollow conductor radiator (1) can be instantaneous at any time, i.e. can be exactly determined immediately, without further calculation.
  • phase-controlled antenna element can be implemented very inexpensively. Reproduction of the phased antenna elements in large numbers, e.g. for use in larger group antennas is easily possible.
  • drive units (6) for example, both inexpensive electric motors or micro-electric motors, as well as piezomotors, or simple actuators that are constructed from electroactive materials can be used.
  • the connecting element (5) is preferably designed as an axle and is preferably made of a non-metallic, dielectric material such as plastic. This has the advantage that cylindrical cavity modes are not, or only very slightly, disturbed when the axis is attached symmetrically in the waveguide radiator (1).
  • the drive unit (6) controls the phase control element (2) in a contactless manner, e.g. via a rotating magnetic field, rotates.
  • a magnetic rotator can be attached above the termination of the waveguide radiator, which then acts together with the rotating magnetic field as a connecting element (5), if e.g. Parts of the polarizer are made of magnetic materials.
  • the polarizers (4a) and (4b) can e.g. consist of simple, flat meander polarizers which are applied to a conventional carrier material. These polarizers can be produced by known thin-film etching processes or by additive processes ("circuit printing").
  • the at least two polarizers (4a) and (4b) preferably have a shape symmetrical to the axis (10) so that they can be easily accommodated in the cylindrically symmetrical waveguide section of the waveguide radiator (1).
  • the in Fig. 3 The polarizer (4a, b) shown is designed as a meander polarizer.
  • multilayer meander polarizers ie structures that are aligned parallel to one another and separated from one another by only fractions of the wavelength, are advantageous, since they can have large frequency bandwidths and thus enable broadband operation.
  • Embodiments are conceivable in which the signal polarization is not converted by plane polarizers but by structures spatially distributed in the holder (e.g. septum polarizers).
  • structures spatially distributed in the holder e.g. septum polarizers.
  • holder (3) e.g. closed-cell foams with low density, which are known to have very low HF losses, but also plastic materials such as
  • Polytetrafluoroethylene (Teflon) or polyimides can be used. Because of the small size of the phase control element in the range of one wavelength, especially at frequencies above 10 GHz, the HF losses remain very small here too with appropriate impedance matching to the corresponding electromagnetic mode in the waveguide radiator (1).
  • phase control element (2) at a specific operating frequency is similar to the dimensional design of the waveguide radiator (1) at a specific operating frequency, the phase control element (2) can typically easily be attached inside the waveguide radiator (1) will.
  • its minimum diameter is typically in the range of one wavelength of the operating frequency.
  • the expansion of the waveguide radiator (1) in the direction of the incident waves is typically a few wavelengths of the operating frequency.
  • the dimensions of the phase control element are always in the range of the dimensions of the waveguide radiator (1).
  • the dimensions of the phase control element (2) are typically in the range smaller than one wavelength, i.e. approx. 1cm x 1cm. If the holder (3) is designed as a dielectric filling body and the relative permittivity is selected to be correspondingly large, then much smaller shapes can also be realized. The ohmic losses then increase slightly, but are still only in the percentage range.
  • the phase control element (2) can be made so small that it is in the waveguide radiator (1) by selecting the dielectric constant for the material of the holder (3). Takes place.
  • FIG Fig. 4 One embodiment of the phased antenna element is shown in FIG Fig. 4 shown schematically.
  • the waveguide radiator (1) is designed as a cylindrical horn radiator and the signal decoupling or coupling (7) is implemented using microstrip technology on an HF substrate (71).
  • the microstrip line (7) used to couple or couple the circular mode is designed here in the form of a loop. This has the advantage that the cylindrically symmetrical waveguide mode in the waveguide radiator (1) can be excited or decoupled directly and practically without losses.
  • the waveguide radiator (1) is at least partially cut out at the position of the coupling (7) so that the signal coupling or coupling (7) with its substrate (71) can be inserted and aligned in the waveguide radiator (1).
  • vias Conductive through-contacts
  • a recess (73) is provided in the substrate (71) through which the axis (5), which establishes the connection between the drive unit (6) and the phase control element (2), can be guided.
  • the holder (3) of the polarizers (4) is also designed as a dielectric filler (9) which completely fills the cross section of the waveguide radiator (1).
  • Such embodiments of the holder can be advantageous, since the impedance matching of the modes in the waveguide radiator (1) can be facilitated and undesired modes can be suppressed.
  • the materials used for the dielectric filling body are in particular plastic materials with low surface energy, such as e.g. Polytetrafluoroethylene (Teflon) or polyimide, which, when rotated in the waveguide radiator (1), generate very little to negligible friction.
  • plastic materials with low surface energy such as e.g. Polytetrafluoroethylene (Teflon) or polyimide, which, when rotated in the waveguide radiator (1), generate very little to negligible friction.
  • the signal decoupling or coupling (7) is designed in two parts as two orthogonal, pin-like microstrip lines (7a) and (7b), which are located on two separate substrates lying one above the other.
  • Such embodiments can be advantageous if two signals are more orthogonal with the phase-controlled antenna element Polarization should be received and / or sent at the same time. Phase imbalances can also be compensated if the signals are processed in an orthogonal system.
  • dielectric filling bodies (9a) and (9b) are provided, which ensure that the volume of air remaining in the waveguide radiator (1) is completely filled with dielectric.
  • the filling bodies (9a) and (9b) are fixedly mounted in the waveguide radiator (1) and do not rotate with the phase control element.
  • they typically have a recess for the axis (10), analogous to the substrates of the microwave lines (7a) and (7b).
  • the waveguide radiator (1) is filled homogeneously with dielectric and the mode distribution in its interior is advantageously homogeneous.
  • the waveguide radiator (1) it can also be advantageous to choose different dielectric constants for the various dielectric filling bodies 9, 9a, 9b. E.g. when the waveguide radiator (1) tapers downwards, it can be advantageous to use a higher dielectric constant for the filler body (9b).
  • FIG. 6 A further development of the invention for the direct reception or transmission of signals with linear polarization by the phase-controlled antenna element is in Fig. 6 shown.
  • the advantageous further development consists in that in the waveguide radiator (1) in front of the phase control element (2) there is at least one further polarizer (41) which can transform signals with linear polarization into signals with circular polarization, and after the phase control element (2) and before at least one further polarizer (42) is attached to the coupling-out (7), which polarizer can transform signals of circular polarization into signals of linear polarization.
  • the phase control element (2) also consists of the holder (3) and the polarizers (4a) and (4b) and has a drive unit (6) which connects to the phase control element (2) or the holder ( 3) is connected in such a way that the phase control element (2) or the holder (3) in the waveguide radiator (1) can be rotated about the axis (10).
  • the phase control element (2) can easily perform its function according to the invention.
  • the second polarizer (42) which is attached after the phase control element (2) and before the decoupling (7), transforms the signal of circular polarization generated by the phase control element (2) and its phase position determined back into a signal of linear polarization, which can be directly decoupled by a decoupling (7) designed accordingly for linear modes.
  • the coupling (7) excites a linear mode in the waveguide radiator (1), which is transformed into a circular mode by the second polarizer (42).
  • This circular mode is one of the phase control element (2) Angle of rotation of the phase control element (2) around the axis (10) dependent phase position.
  • the circularly polarized signal with the set phase position, which leaves the phase control element (2), is transformed by the first polarizer (41) into a signal with linear polarization and the imposed phase position and emitted by the waveguide radiator (1).
  • FIG. 6 An embodiment of the in Fig. 6 further development shown is in Fig. 7 shown schematically.
  • the signal decoupling or coupling (7) is analogous to the embodiment of FIG Fig. 5 designed in two parts as a pin-shaped, orthogonal microstrip line (7a) and (7b) on separate substrates.
  • the additional polarizers (41) and (42) are each embedded in a dielectric filler body (9c) or (9d) and are typically fixedly mounted in the waveguide radiator (1).
  • the area between the coupling-out and coupling-out (7a) and (7b) is filled with a dielectric filling body (9a), the waveguide termination below the coupling-out or coupling-in (7b) is filled with a dielectric filling body (9b).
  • This structure has the advantage that the entire interior of the waveguide radiator (1) is filled with a dielectric, typically of the same type, so that mode discontinuities cannot occur.
  • the coupling-out and coupling-in (7a) and (7b) can also be designed in one piece for a linear mode for a corresponding application (analogous to the exemplary embodiment in FIG Fig. 4 ).
  • the first additional polarizer (41) rotatable and to equip it with an independent drive so that the polarizer (41) in the waveguide radiator (1) independently of the phase control element (2) the axis (10) can be rotated.
  • Such an arrangement is particularly advantageous when, in mobile arrangements, the movement of the carrier causes a rotation of the polarization vector of the incident wave relative to the array antenna fixedly mounted on the carrier.
  • FIG. 8 A corresponding embodiment is shown in Fig. 8 shown schematically.
  • the polarizer (41) is rotatably mounted in the waveguide radiator (1) and connected to its own drive (12) with the aid of a connector (13) so that this drive (12) can rotate the polarizer (41) about the axis (10) .
  • FIG Fig. 8 The independent rotation of the polarizer (41) from the rotation of the phase control element (2) is shown in FIG Fig. 8 realized in such a way that the axis (5) which connects the phase control element (2) to its drive (6) is designed as a hollow axis.
  • the connector (13), which connects the polarizer (41) to its drive (12), is located in this hollow axis.
  • the second additional polarizer (42) is firmly attached in the antenna radiator (1), since its alignment determines the alignment of the linear mode which is coupled out and coupled in by the coupling out and coupling (7).
  • the fixed alignment of the polarizer (42) is therefore based on the position of the coupling-out or coupling-in (7).
  • the coupling out or coupling (7) is in the embodiment of Fig. 8 designed in one piece as a pin-like microstrip line.
  • This embodiment is advantageous if a linear mode is to be coupled out or coupled into the waveguide radiator (1).
  • the second additional polarizer (42) can also be dispensed with, since the circularly polarized signal generated by the phase control element (2) basically contains all the information of the incident wave.
  • a 90 ° hybrid coupler for example, can then be used, into which the signal divided into signals (7a) and (7b) is fed.

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EP17735448.7A 2016-07-08 2017-06-27 Phasengesteuertes antennenelement Active EP3482454B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102016112582.2A DE102016112582A1 (de) 2016-07-08 2016-07-08 Phasengesteuertes Antennenelement
PCT/EP2017/065881 WO2018007209A1 (de) 2016-07-08 2017-06-27 Phasengesteuertes antennenelement

Publications (2)

Publication Number Publication Date
EP3482454A1 EP3482454A1 (de) 2019-05-15
EP3482454B1 true EP3482454B1 (de) 2020-09-30

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US (1) US10868350B2 (he)
EP (1) EP3482454B1 (he)
CN (1) CN109417228B (he)
DE (1) DE102016112582A1 (he)
ES (1) ES2836259T3 (he)
IL (1) IL264095B2 (he)
WO (1) WO2018007209A1 (he)

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CN114122736B (zh) * 2022-01-26 2022-05-24 华南理工大学 一种全向覆盖的宽带圆极化多波束天线阵列
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US11949489B1 (en) 2022-10-17 2024-04-02 Isco International, Llc Method and system for improving multiple-input-multiple-output (MIMO) beam isolation via alternating polarization
US11985692B2 (en) 2022-10-17 2024-05-14 Isco International, Llc Method and system for antenna integrated radio (AIR) downlink and uplink beam polarization adaptation
US11956058B1 (en) 2022-10-17 2024-04-09 Isco International, Llc Method and system for mobile device signal to interference plus noise ratio (SINR) improvement via polarization adjusting/optimization
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CN117498136B (zh) * 2024-01-02 2024-03-15 北京镭宝光电技术有限公司 光参量振荡器

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US20200119422A1 (en) 2020-04-16
ES2836259T3 (es) 2021-06-24
IL264095B (he) 2022-12-01
WO2018007209A1 (de) 2018-01-11
US10868350B2 (en) 2020-12-15
CN109417228A (zh) 2019-03-01
EP3482454A1 (de) 2019-05-15
IL264095A (he) 2019-01-31
CN109417228B (zh) 2021-02-02
DE102016112582A1 (de) 2018-01-11

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