EP1754284A1 - Structure a guides d'ondes - Google Patents

Structure a guides d'ondes

Info

Publication number
EP1754284A1
EP1754284A1 EP05716908A EP05716908A EP1754284A1 EP 1754284 A1 EP1754284 A1 EP 1754284A1 EP 05716908 A EP05716908 A EP 05716908A EP 05716908 A EP05716908 A EP 05716908A EP 1754284 A1 EP1754284 A1 EP 1754284A1
Authority
EP
European Patent Office
Prior art keywords
parallel plate
waveguide structure
conductive layer
line
plate line
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP05716908A
Other languages
German (de)
English (en)
Inventor
Joerg Schoebel
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Robert Bosch GmbH
Original Assignee
Robert Bosch GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Robert Bosch GmbH filed Critical Robert Bosch GmbH
Publication of EP1754284A1 publication Critical patent/EP1754284A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/27—Adaptation for use in or on movable bodies
    • H01Q1/32—Adaptation for use in or on road or rail vehicles
    • H01Q1/3208—Adaptation for use in or on road or rail vehicles characterised by the application wherein the antenna is used
    • H01Q1/3233—Adaptation for use in or on road or rail vehicles characterised by the application wherein the antenna is used particular used as part of a sensor or in a security system, e.g. for automotive radar, navigation systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H01Q21/0031—Parallel-plate fed arrays; Lens-fed arrays
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q25/00—Antennas or antenna systems providing at least two radiating patterns
    • H01Q25/007—Antennas or antenna systems providing at least two radiating patterns using two or more primary active elements in the focal region of a focusing device
    • H01Q25/008—Antennas or antenna systems providing at least two radiating patterns using two or more primary active elements in the focal region of a focusing device lens fed multibeam arrays

Definitions

  • the invention relates to a waveguide structure for generating a phase gradient between the input signals of an arrangement of antenna elements.
  • the white conductor structure is implemented on a dielectric microwave substrate which is provided on both sides with at least one conductive layer. At least one of the two conductive layers is structured and forms the signal side of the waveguide structure. while the other conductive layer serves as the ground.
  • the waveguide structure comprises at least one parallel plate line with beam lobes for signal feed or for signal acquisition.
  • phase gradient ⁇ between the input signals of adjacent antenna elements 1 namely causes their output signals to advance or lag, so that the resulting phase front of the Wave of the antenna output signal is pivoted at an angle (azimuth).
  • a large number of civil and military applications in the radar and communication field for microwave antennas with electronically pivotable or switchable beam lobe are known.
  • An example here is the use in automotive radar systems for adaptive cruise control (ACC), which are typically based on the principle of multi-lobe monopulse radar work. In this case, several beam lobes are formed via one or more antennas in the azimuth plane, each of which overlaps in pairs in partial areas.
  • ACC adaptive cruise control
  • future applications in the automotive sector are in the area of "low-speed following" and "stop-and-go” operation, reversing and parking aids, blind spot monitoring, detection of collisions with measures
  • the antenna elements are coupled to the outputs of such a lens structure and, depending on the selected input, thus generate a beam lobe with a beam deflection which results from the phase gradient.
  • the Rotman lens has good focusing properties and can be flexibly designed for any phase gradient at the antenna gates.
  • lens structures are realized in connection with a planar antenna with several fixed beam lobes in planar microstrip technology.
  • the elements of the lens are used as planar elements of a microstrip circuit on a microwave substrate, e.g. Ceramic, glass or filled plastics.
  • FIG. 1 The basic structure of a planar Rotman lens is shown in Fig. 1.
  • Parallel plate line 1 is fed on one side via beam gates ("beam ports") 2, which are connected via microstrip lines 3 and possibly via a switch for selecting a beam lobe to a transmission or reception circuit (not shown here) Wave propagation to the antenna ports ("Antenna Ports") 4 instead.
  • Beam ports beam gates
  • the microstrip lines 5 between the antenna gates 4 and the link elements 6 are designed in the form of compensating lines, the length of which varies from the center of the parallel plate line 1 to the outside.
  • the contour of the parallel plate line 1 and the lengths of the compensating lines 5 determine the respective signal path length. They are designed so that there is a phase gradient of zero on the antenna elements 6 for a centrally arranged beam lobe gate, while the maximum predetermined phase gradient results for the outermost beam lobe gate.
  • the lens structure described above has a number of shortcomings which make it difficult to use in radar sensors.
  • the losses of the lens, in particular due to the compensation lines are relatively high.
  • the area requirement for parallel plate lines and compensating lines is also relatively large. As a rule, there are also relatively high overexposure losses on the sides of the lens structure or the parallel plate line.
  • Rotman lens the beam gates are quite far from the antenna. This makes the sensor relatively long in the direction of elevation, which is unfavorable for installation in a motor vehicle.
  • planar waveguide structure of the type mentioned is proposed, the space requirement of which is relatively small and which also enables relatively low-loss beam deflection.
  • the parallel plate line has a curved reflector contour so that it acts as a signal reflector.
  • a defined beam deflection can be brought about not only by means of a lens structure but also with the aid of a reflective structure.
  • a suitable reflector structure can also be implemented in the form of a planar waveguide structure on a microwave substrate, namely as a parallel plate line with a curved reflector contour.
  • the parallel plate line is with several beam gates
  • Signal feed or for Signalabgr-ff equipped which are arranged so that the signals through reflection on the curved reflector contour of the parallel plate line from the beam gates to the coupled antenna elements or from the antenna elements to the beam gates.
  • a phase gradient is generated between the output signals of the parallel plate line depends on the respective beam club gate.
  • a planar group antenna connected to the outputs of the parallel plate line can thus emit several beam lobes with different deflection angles.
  • the conductive layers of the parallel plate line terminate on the signal and on the ground plane along a curved line that the
  • the curved reflector contour of the parallel plate line can also be realized in the form of correspondingly arranged, conductive bushings between the conductive layers on the signal side and on the ground side, the distance between these Durcli currencies and the diameter of these Durcli guides should be small compared to the line wavelength. It proves to be particularly advantageous if the curvature of the reflector contour is approximately parabolic. At this point, however, it should be pointed out that the focusing properties of the waveguide aperture according to the invention can still be improved if there is a deviation from a parabolic contour. With the aid of numerical (-) optimization, a reflector contour can be determined, by means of which the phase deviations in the focal points are uniformly minimized.
  • microstrip lines are formed in the conductive layer and are coupled to the beam lobe gates of the parallel plate line via planar feed horns (line taper). It has been shown that the bundling or overexposure can be determined by the size of the food horns, which contributes to reducing the losses. In addition, overexposure only occurs to a lesser extent due to the shape of the reflector structure.
  • the signals applied to the beam lobe gates can be guided to the rear of the microwave substrate via radiation coupling or lead-throughs, so-called HF vias. If a multi-layer substrate is used, RF electronics can then be arranged here, which has proven to be advantageous for certain applications.
  • the parallel plate line of the waveguide structure according to the invention can be continued on the antenna side and can be provided there with slots which act as antenna elements of a group antenna. In this case, the radiation is relatively low loss.
  • WeUe-Üdterstaiktur according to the invention is another embodiment of the WeUe-Üdterstaiktur according to the invention.
  • Parallel plate line antenna gates designed for coupling the antenna elements. This coupling is advantageously also realized by planar feed horns (line taper) and microstrip lines.
  • dummy ports are formed in the conductive layer on the contour of the parallel plate line. Dummy ports in the area between the beam gates serve to decouple the individual beam gates from one another. The arrangement of dummy ports in the area between the beam gates and the reflector contour prevents unwanted reflections. These dummy ports are also advantageously implemented in the form of planar feed domes, each of which is closed with little reflection or leads to a line with little reflection.
  • the waveguide structure according to the invention with a parallel plate line, on which beam lobe gates and possibly antenna gates and dummy ports are formed, can therefore be realized together with all the necessary connecting lines in the form of a completely planar -V microstrip structure on a microwave substrate.
  • FIG. 2 shows a top view of an inventive waveguide structure with two different beam paths (FIGS. 2a and 2b),
  • FIG. 3 illustrates the focusing on a planar parabolic reflector by way of example on three beam paths
  • FIG. 4 shows a perspective view of a first waveguide structure according to the invention
  • Fig. 5 shows a perspective view of a second invention
  • the guide structure 10 shown in FIGS. 2a : * and 2b serves to generate a phase gradient between the input signals of an arrangement of antenna elements 16.
  • the waveguide structure 10 is realized in microstrip technology, as in the
  • a single-layer microwave substrate made of ceramic, glass or a filled plastic is used, which is metallized on both sides.
  • the metallized underside forms the mass of the white conductor structure 10 and can also be structured.
  • the parallel plate line 11 has a curved reflector contour 20 so that it acts as a signal reflector.
  • the curvature of the reflector contour 20 is approximately parabolic.
  • Microstrip lines 13 are formed in the conductive layer on the signal side and are coupled to the beam gates 12 of the parallel plate line 11 via gradually widened line sections 17. These gradually widened line sections 17 are referred to as "tapers" or as food horns, because the wave propagation from the end of the microstrip lines continued in this way into a parallel plate line is comparable to the radiation of a horn antenna into the room B. exponential, linear or Klopfenstein.
  • the parallel plate line 11 in the exemplary embodiment shown here also has antenna gates 14 which are likewise coupled to the antenna elements 16 via line taper 18 and microstrip lines 15.
  • Dummy ports 23 and 24 are formed. They are each implemented in the form of a line taper that is closed with little reflection or leads to a line with little reflection.
  • the line termination can be implemented, for example, as a discrete resistor with a ground leadthrough or short-circuit stub or by attaching absorber material to a line.
  • the dummy ports 23 are between each
  • Beam lobe gates 12 are arranged and serve on the one hand to decouple the beam lobe gates 12 from one another and on the other hand to improve the spread of the planar KugelweUen emanating from the food horns 17, by preventing reflection or refraction of the wee at a melee channels located next to the food horn 17. Between the arrangement of the beam lobe gates 12 and the reflector contour
  • the dummy ports 24 are positioned in order to prevent unwanted reflections.
  • FIG. 2a shows a white front 8 which occurs perpendicular to the front face of the anime, ie with a deflection angle of 0 °.
  • the white front 9 shown in FIG. 2b strikes the front face of the antenna with a deflection angle not equal to 0 °. Accordingly, the two illustrated white fronts 8 and 9 are bundled by the parallel plate line 11 with the reflector contour 20 at different beam lobe gates 12a and 12b.
  • the perpendicular to the Antenna interference strikes front 8 is bundled on the centrally arranged beam lobe gate 12a, while the front 9, which strikes the antenna end face with a deflection angle not equal to 0 °, is bundled on the outer beam gate 12b.
  • FIG 3 shows the parallel plate line 11 shown in FIGS. 2a and 2b with the curved reflector contour 20 and, by way of example, three beam paths in this parallel plate line, as they occur when three plane waves are received with different deflection angles to the front face of the ante.
  • these plane waves correspond to input signals on the antenna gates 14, with a
  • Phase gradient between adjacent antenna gates 14 exists. If the antenna gates are guided on antenna elements, these signals form beam lobes, which each have different deflection angles to the antenna normal.
  • the signals are reflected on the curved reflector contour 20 and run in the
  • Receiving case three focal points 31, 32 and 33 together.
  • Focal point 32 for the beam perpendicular to the front face of the anime results in two focal spots 31 and 33 for the waves not incident perpendicularly.
  • the focal spots 31 and 33 are sufficient wine so that they can be picked up by a planar food horn.
  • the resulting phase errors are tolerable.
  • the food horns are placed so that their phase centers are close to the locations of minimal phase deviation, which can be determined by suitable averaging or by numerical optimization.
  • the orientation of the food horns is chosen so that, in the case of transmission, as small a portion of the radiation as possible is lost due to overexposure at the edges and so that the radiation maximum occurs approximately in the middle of the antenna gates. Numerical optimization can also be carried out for this purpose.
  • the antenna gates only have to illuminate a relatively narrow area of the reflector contour. They can therefore be designed to be relatively large, because radiation from the antenna gate only reaches the associated beam gate gate from the area of the reflector in front of the respective antenna gate.
  • the beam lobe gates can be made quite small, since they are intended to illuminate the entire reflector contour.
  • FIGS. 4 and 5 show two waveguide structures 40 and 50 according to the invention, each of which is implemented on a microwave substrate in the form of a parallel plate line with M-type strip lines, which has already been explained in connection with FIG. 2.
  • the curved reflector contour of the parallel plate line 11 is realized in that the metallizations on the signal plane and on the ground plane end at curved lines 21 running parallel to one another. Therefore not only the metalization on the signal side of the microwave substrate has to be correspondingly structured, but also the metalization on the ground side.
  • Metal channels which consist of a non-metalized substrate surrounded by air, form a symmetrical dielectric waveguide. This leads a TMO wave without a lower cut-off frequency.
  • the TM-WeUen are preferentially excited by the TEM-WeUe of the ParaUelplatte ein because of their field course. Because of the small thickness of the substrate, there are usually no higher TM values.
  • the curved reflector contour of the parallel plate line 11 is reactivated in that metallic passages 22, so-called “vias”, are formed along a curved line between the metal levels of the parallel plate line 11. If the diameter and spacing of the passages 22 are small compared to the wavelength, the electromagnetic wave is practically totally reflected.

Abstract

L'invention concerne une structure planaire à guides d'ondes pour générer un gradient de phase entre les signaux d'entrée d'un réseau d'éléments d'antenne, cette structure présentant un encombrement relativement faible et permettant une déflexion de faisceau avec des pertes relativement faibles. Cette structure à guides d'ondes (10) est réalisée sur un substrat diélectrique à micro-ondes pourvu d'au moins une couche conductrice sur chaque face. Au moins une de ces deux couches conductrices est structurée et forme le côté signal de la structure à guides d'ondes (10), l'autre couche conductrice servant de masse. Ladite structure à guides d'ondes (10) comprend au moins une ligne à plaques parallèles (11) comprenant des portes à faisceau (12) pour l'injection ou le prélèvement de signaux. Selon l'invention, cette ligne à plaques parallèles (11) présente un contour de réflecteur courbé (20) de façon à agir comme réflecteur de signal.
EP05716908A 2004-04-07 2005-03-04 Structure a guides d'ondes Withdrawn EP1754284A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102004016982A DE102004016982A1 (de) 2004-04-07 2004-04-07 Wellenleiterstruktur
PCT/EP2005/050966 WO2005099042A1 (fr) 2004-04-07 2005-03-04 Structure a guides d'ondes

Publications (1)

Publication Number Publication Date
EP1754284A1 true EP1754284A1 (fr) 2007-02-21

Family

ID=34961453

Family Applications (1)

Application Number Title Priority Date Filing Date
EP05716908A Withdrawn EP1754284A1 (fr) 2004-04-07 2005-03-04 Structure a guides d'ondes

Country Status (6)

Country Link
US (1) US7518566B2 (fr)
EP (1) EP1754284A1 (fr)
JP (1) JP4243611B2 (fr)
CN (1) CN1943077A (fr)
DE (1) DE102004016982A1 (fr)
WO (1) WO2005099042A1 (fr)

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US8604989B1 (en) * 2006-11-22 2013-12-10 Randall B. Olsen Steerable antenna
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US20080303739A1 (en) * 2007-06-07 2008-12-11 Thomas Edward Sharon Integrated multi-beam antenna receiving system with improved signal distribution
WO2010068954A1 (fr) * 2008-12-12 2010-06-17 Wavebender, Inc. Antenne à cavité de guide d’onde intégrée et réflecteur d’antenne
FR2986377B1 (fr) * 2012-01-27 2014-03-28 Thales Sa Formateur multi-faisceaux a deux dimensions, antenne comportant un tel formateur multi-faisceaux et systeme de telecommunication par satellite comportant une telle antenne
JP2013201686A (ja) * 2012-03-26 2013-10-03 Furukawa Electric Co Ltd:The ロットマンレンズ
US9612317B2 (en) * 2014-08-17 2017-04-04 Google Inc. Beam forming network for feeding short wall slotted waveguide arrays
US9711860B2 (en) * 2015-08-13 2017-07-18 Sony Corporation Wideband antennas including a substrate integrated waveguide
CN105428822B (zh) * 2015-11-24 2019-03-15 大连楼兰科技股份有限公司 车载防撞雷达一发多收siw透镜天线
CN106257748A (zh) * 2016-08-31 2016-12-28 广东通宇通讯股份有限公司 一种多波束系统
JP6723133B2 (ja) * 2016-10-04 2020-07-15 日立オートモティブシステムズ株式会社 アンテナ、センサ及び車載システム
US10285082B2 (en) * 2016-11-17 2019-05-07 Rohde & Schwarz Gmbh & Co. Kg Testing device and method for testing a device under test with respect to its beamforming behavior
US11329393B2 (en) * 2016-12-07 2022-05-10 Fujikura Ltd. Antenna device
WO2019000179A1 (fr) 2017-06-26 2019-01-03 华为技术有限公司 Appareil d'alimentation électrique
CN109193180B (zh) * 2018-08-30 2020-11-27 电子科技大学 用于近场二维聚焦的高效率基片集成波导漏波缝隙阵天线
US11545757B2 (en) * 2018-12-19 2023-01-03 Huawek Technologies Canada Co., Ltd. Dual end-fed broadside leaky-wave antenna
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Also Published As

Publication number Publication date
JP2006525687A (ja) 2006-11-09
JP4243611B2 (ja) 2009-03-25
WO2005099042A1 (fr) 2005-10-20
US20070212008A1 (en) 2007-09-13
CN1943077A (zh) 2007-04-04
DE102004016982A1 (de) 2005-10-27
US7518566B2 (en) 2009-04-14

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