EP1314241A1 - Generatrice a courant continu avec dispositif de limitation de courant regulable - Google Patents

Generatrice a courant continu avec dispositif de limitation de courant regulable

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Publication number
EP1314241A1
EP1314241A1 EP01965166A EP01965166A EP1314241A1 EP 1314241 A1 EP1314241 A1 EP 1314241A1 EP 01965166 A EP01965166 A EP 01965166A EP 01965166 A EP01965166 A EP 01965166A EP 1314241 A1 EP1314241 A1 EP 1314241A1
Authority
EP
European Patent Office
Prior art keywords
current
signal
speed
value
machine according
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP01965166A
Other languages
German (de)
English (en)
Inventor
Alexander Hahn
Hermann Rappenecker
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Ebm Papst St Georgen GmbH and Co KG
Original Assignee
Papst Motoren GmbH and Co KG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Papst Motoren GmbH and Co KG filed Critical Papst Motoren GmbH and Co KG
Publication of EP1314241A1 publication Critical patent/EP1314241A1/fr
Withdrawn legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/28—Arrangements for controlling current
    • F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F04—POSITIVE - DISPLACEMENT MACHINES FOR LIQUIDS; PUMPS FOR LIQUIDS OR ELASTIC FLUIDS
    • F04D—NON-POSITIVE-DISPLACEMENT PUMPS
    • F04D27/00—Control, e.g. regulation, of pumps, pumping installations or pumping systems specially adapted for elastic fluids
    • F04D27/004—Control, e.g. regulation, of pumps, pumping installations or pumping systems specially adapted for elastic fluids by varying driving speed

Definitions

  • the invention relates to an electronically commutated DC machine with a rotor and a stator.
  • Such electronically commutated direct current machines are known in various embodiments. It has been shown that they are suitable for a variety of drive tasks, especially if their price is affordable.
  • the current limiting arrangement can be set by means of a current setpoint signal, such a DC machine is extremely versatile. For example, you can control the speed in the usual way by designing the timing signal as the output signal of a speed controller and using this timing signal to control the speed of the DC machine, the current setpoint signal is usually set to a fixed high value, which is at the upper limit of the the DC machine of permissible current lies. In such a case, the current setpoint signal causes a current limitation when the engine is started, and the value for this current limitation can be set according to needs, e.g. according to the power of a power supply.
  • the speed can also be controlled in such a way that a current setpoint signal for the current limiting arrangement is generated as the output signal of a speed controller and the speed is regulated with this current setpoint signal, the clock preset signal being set such that the current limiting arrangement is constantly active. This results in a speed control of very high control quality.
  • the current setpoint signal can also be set to a constant value of the desired level and at the same time the clock signal can be set so that the current limiting arrangement is constantly active.
  • One of these applications is the drive of a radial or diagonal fan, which shows completely surprising properties in connection with such a constant current control.
  • the invention also relates to the use of such a DC machine for driving a fan, which is preferably designed as a diagonal or radial fan.
  • a DC machine for driving a fan, which is preferably designed as a diagonal or radial fan.
  • FIG. 1 is an overview circuit diagram of a preferred embodiment of an arrangement according to the invention with a DC machine
  • FIG. 2 shows a full-bridge circuit 78, as can preferably be used in the arrangement according to FIG. 1,
  • FIG. 3 is a table which shows the output signals of the rotor position sensors 111, 112, 113 and, as a function thereof, the control of the full-bridge circuit 78 of FIG. 2,
  • FIG. 5 shows schematic diagrams of the voltages, currents and powers occurring in FIG. 4 in the so-called mutual clocking
  • FIG. 6 shows a current limiting arrangement for limiting the drive current i_2 in the arrangement of FIG. 1 to an externally predetermined, variable value, 7 diagrams to explain the mode of operation of FIG. 6,
  • FIG. 8 shows a current limiting arrangement for limiting the braking current i_2 'in the arrangement of FIG. 1 to an externally predetermined, variable value
  • FIG. 9 shows diagrams for explaining the mode of operation of FIG. 8,
  • Fig. 10 is an illustration which is a highly schematic combined
  • FIG. 11 is an overview circuit diagram to explain a preferred embodiment of an arrangement according to the invention.
  • FIGS. 1 to 11 are illustrations for an exemplary explanation of a PWM generator according to the prior art, as it can be used advantageously in the DC machine according to FIGS. 1 to 11,
  • FIG. 12 shows diagrams for the explanation of FIG. 12,
  • FIG. 14 shows an individual illustration to explain the actuation of a bridge branch in the arrangement according to FIGS. 1 to 11,
  • 16 is a flowchart which shows an overview of various possibilities of how the arrangement according to the preceding figures can be operated as a motor or as a brake,
  • FIG. 18 shows a physical model for explaining the processes in the DC machine 32, 19 forms of the stator current as they occur in a speed control by means of the current setting (FIG. 19B) or in a speed control by means of the voltage setting (FIG. 19A),
  • 25 is a routine for monitoring the voltage on the DC machine 32
  • 26 is a diagram showing a curve of the voltage on the motor, which triggers certain processes in the routine of FIG. 25,
  • 31 shows a routine which shows how the correct one is selected from a plurality of control routines on the basis of the MODE signal
  • 32 shows a routine which shows how different routines are controlled depending on the MODE signal
  • FIG. 38 shows the schematic structure of a radio station for mobile radio, which is provided with a radial fan,
  • 41 is a representation of a ventilation duct 676, in which air is conveyed by a total of six identical radial fans, and the air flows present when all fans are regulated to the same speed,
  • 43 shows a representation analogous to FIG. 41, but with the six radial fans being operated with the same constant torque
  • 44 shows a flowchart of a first test routine which is used to test a motor, for example the motor of a fan, during operation
  • 45 is a flowchart of a second test routine used to test an engine, e.g. to test the motor of a fan during operation,
  • 47 is a diagram for explaining a preferred embodiment of the invention.
  • FIG. 1 shows a highly schematic overview of an overall representation of a preferred exemplary embodiment of an arrangement according to the invention.
  • a three-phase electronically commutated direct current machine (ECM) 32 is shown on the right as an example.
  • This has a permanent magnetic rotor 110, shown here as four-pole, which controls three Hall generators 111, 112, 113, which generate Hall signals HS1, HS2 and HS3 during operation, which are shown in FIG. 15.
  • 15 shows the phase relationship of these signals relative to one another.
  • the DC machine 32 has a stator 114 with three winding phases (phases) 115, 116, 117, which are shown here by way of example in a delta connection and whose connections are designated L1, L2 and L3.
  • connections are connected to the output of a power output stage 78, the structure of which is shown by way of example in FIG. 2. This is connected via a connection 76 to a positive operating voltage + U_B and via a node 88 and a measuring resistor 87 to ground GND.
  • the pulse-shaped total current in the supply line to the motor 32 at the node 88 is detected by means of the measuring resistor 87, so that the potential at the point 88 changes depending on the current through the stator winding 114.
  • the current when the DC machine 32 is driving is designated i_2, and the current when the DC machine 32 is braking is designated i_2 '.
  • Both are pulse-shaped direct currents, as shown for example in FIG. 13B, and their pulse duty factor toN T (FIG. 13B) is designated PWM2, cf. the following equation (9).
  • the signal (at node 88) for the driving current i_2 is fed to a current limiting stage 131 and the signal for the braking current i_2 'is fed to a current limiting stage 161.
  • Preferred exemplary embodiments of these current limiting stages are explained in detail below in FIGS. 6 and 8.
  • the term "motor" is often used for the ECM 32 below.
  • a current limiting stage 161 for the braking current i_2 ' is, of course, only required if braking is to take place. If that's not the case, you don't need it. The same applies in reverse for the current limiting stage 131 if the direct current machine 32 is to be used only as a brake.
  • a variable current limit value PWM + (for the driving current) can be supplied from a controller 24 to the current limiting stage 131, for example in order to regulate the speed n or the driving torque T + of the motor 32.
  • the current limiting stage 131 is designed by its hardware in such a way that a permissible current i_2 in the motor 32 cannot be exceeded even if the value PWMJ + assumes its maximum value.
  • the current i_2 must not exceed e.g. 5 A.
  • the current limiter 131 is designed in such a way that the current i_2 cannot become greater than 5 A even at maximum PWMJ +.
  • the motor 32 according to this example thus constantly receives a pulse-shaped during operation
  • a pulse-shaped direct current i_2 with the required pulse duty factor PWM2 is generated by either PWM1 itself generating the correct value of PWM2, or by modifying a value of PWM1 which does not correspond to the desired operating values by means of the current limiting stage 131 or the current limiting stage 161.
  • the controller 24 can supply the current limiting stage 161 with a (variable) current limiting value PWMJ- for the braking current i_2 '. This is then always kept in the permissible range by the hardware of the current limiter 161.
  • the PWMJ + value determines the upper limit for the driving current
  • the value PWMJ- determines the upper limit for the braking current in the DC machine 32.
  • the signal PWM1 is modified by the current limiting stage 131 or 161 to a (permissible) signal PWM2. This also applies if the speed of the motor 32 is regulated by generating the current setpoint PWMJ + as the output signal of a speed controller, cf. S432 in Fig. 28 and the description there.
  • the signals HS1, HS2, HS3 are fed to the controller 24 and represent a measure of the current speed n of the motor 32. These signals are also fed to a commutation controller (control logic) 49, which commutates the currents via driver stages 50, 52, 54 controls in the windings 115, 116, 117.
  • the commutation controller 49 generates signals IN1, EN1, IN2, EN2, IN3, EN3, which are fed to the driver stages 50, 52, 54, to which the signal PWM2 is also fed.
  • 14 shows an example of the structure of driver stage 50, which is identical in structure to driver stages 52 and 54.
  • 5A shows an example of the signal PWM2, which is used for PWM control of the driver stages 50, 52, 54.
  • This signal has a period T (corresponding to a frequency of 20 kHz, for example) and a duty cycle toN.
  • the ratio toN / T is called the duty cycle of the signal PWM2, cf. equation (9).
  • This duty cycle depends on a) the current through the resistor 87 b) the signal PWM1 c) the signal PWMJ + d) the signal PWMJ-
  • the voltage at the winding arrangement 114 is predetermined by the signal PWM2 - by appropriate control of the driver stages 50, 52, 54 - which is approximately equal to U_B * PWM2 according to equation (1).
  • the interaction of the factors mentioned can be specified on the controller 24.
  • One of several operating modes can be specified for this at an MODE input, cf. Fig. 16.
  • controller 24 At input n_s, controller 24 is given a desired speed ("target speed 1 ).
  • the controller 24 is given an upper limit for the driving motor current i_2.
  • an upper limit value for the braking current i_2 ' is given to it, which occurs when the DC machine 32 brakes a load.
  • the controller 24 is given a driving torque which the motor generates in a larger speed range in the corresponding operating mode. This is possible because the current of a DC machine is essentially proportional to the torque generated.
  • the characteristic curve 796 of FIG. 36 shows - for a radial fan 370 according to FIG. 33 - the absorbed current I over the volume flow V / t when operating with an essentially constant torque. It can be seen that this current I, and thus the torque generated, are constant over a fairly large range. The advantages of such a fan are explained with reference to FIGS. 38 to 43.
  • the controller 24 At the input T- the controller 24 is given a braking torque which the DC machine - as an electric brake - generates in a larger speed range.
  • digital data can be entered into the controller 24 via a bus 18 and stored there in a non-volatile memory 20. These can be, for example, the values for l_max +, l_max-, T +, T-, n_s and MODE, or other values with which the arrangement is to be programmed.
  • digital data can be transmitted from the controller 24 to the outside via the bus 18, for example speed n, alarm signal etc.
  • controller 24 and commutation controller 49 are preferably implemented by software in the same microcontroller 23. These functions are shown separately in FIG. 1 for reasons of clarity.
  • the signals PWM1, PWMJ + and PWMJ- are obtained at its output in digital form, namely as PWM signals.
  • These signals are preferably processed in the current limiters 131, 161 in analog form, because in this way an extremely rapid execution of the control process is possible, which could only be achieved digitally with great effort.
  • the resulting signal according to FIG. 11 is then converted again in an A / D converter 182 into a digital signal PWM2, which controls the voltage at the stator arrangement 114 and thus the current through it according to equation (1).
  • FIG. 1 The advantages of an arrangement according to FIG. 1 are seen primarily in the following aspects:
  • the speed can be regulated via the current limiter 131, that is to say by changing the signal PWMJ +.
  • the current in the motor 32 becomes substantially constant, and the steepness of the rise and fall of the current is large.
  • the motor 32 operates with very low fluctuations (ripple) in its torque and excellent efficiency.
  • the current limit 131 is therefore constantly active and limits the current in the motor 32 to a variable value (within predefined limits), which is specified by the speed controller 24 as the signal PWMJ +.
  • the motor 32 can be operated with constant driving torque T +. 16, S512, by setting PWM1 to a high value, e.g. would correspond to 9,300 rpm, so that the positive current limiter 131 is constantly active and that the current limiter 131 is given a value PWMJ + which corresponds to the desired driving torque T +.
  • PWMJ + is set to a constant value.
  • the motor 32 then operates with constant driving torque.
  • this operating mode is very advantageous because with it, a radial or diagonal fan automatically increases its speed with increasing back pressure, as shown by curve 790 in FIG. 35. This is a very valuable feature, especially for radial fans, because the amount of air delivered drops less with increasing back pressure than with other types of fans, so it is less affected by the back pressure.
  • the DC machine 32 can also be operated with a constant braking torque T- if braking operation is provided.
  • the current limiter 161 is given a value PWMJ-, which corresponds to the desired braking torque T-, so that a pulsed braking current i_2 'flows, which is the desired torque T- determined. This is possible because the braking torque T- is largely proportional to the braking current in the DC machine 32.
  • the speed can be regulated in the "normal" manner by changing the signal PWM1, the motor current being limited to a permissible value via the current limiter 131 (and possibly 161). This is shown in FIG. 16 at S504, and in detail in FIG. 27.
  • the advantage that the motor current is particularly constant is lost, and a current profile is obtained as shown in FIG. 19A and in which the fluctuations of the driving torque and the engine noise are larger.
  • a DC machine 32 can be used at the start of a device as a brake with constant torque T- and after the device has started up as a drive motor, either at regulated speed (FIG. 16, S504 or S520), or with constant driving torque (FIG. 16 , S512).
  • the DC machine 32 is brought to a desired speed n_s by a speed control via voltage or current control and is thus adapted to the speed of a conveyor belt to be braked. Then the DC machine 32 is coupled to the conveyor belt and the MODE mode is switched to constant braking torque in order to brake the belt.
  • a speed control via voltage or current control
  • the MODE mode is switched to constant braking torque in order to brake the belt.
  • the invention is therefore suitable for a variety of drive tasks, a particularly preferred area of application being the drive of a radial or diagonal fan with an essentially constant torque T +, as explained below with reference to FIGS. 33 to 43.
  • FIG. 2 again shows the three-phase electronically commutated direct current machine (ECM) 32 with its winding connections L1, L2 and L3, furthermore an output stage 78 designed as a full bridge with three bridge branches in which semiconductor switches 80 to 85 are arranged.
  • ECM direct current machine
  • the invention is equally suitable for other DC machines, for example for ECMs with only one phase, with two phases, or with more than three phases, or for collector machines.
  • An AC voltage from an AC voltage source 70 is rectified in a rectifier 72 and fed to a DC link 73, 74.
  • a capacitor 75 smoothes the DC voltage U_B at the intermediate circuit 73, 74, which is fed to the individual bridge branches of the full bridge 78.
  • the voltage UJ3 can be measured at a connection 76.
  • N-channel MOSFETs are used as circuit breakers both for the upper circuit breakers 80, 82 and 84 and for the lower circuit breakers 81, 83 and 85.
  • Free-wheeling diodes 90, 91, 92, 93, 94 and 95 are connected antiparallel to the circuit breakers 80 to 85.
  • the freewheeling diodes 90 to 95 are usually integrated in the associated N-channel MOSFETs.
  • the DC voltage U_B at the intermediate circuit 73, 74 is also supplied to consumers 77, e.g. electronic components of the DC machine 32.
  • the respective winding connection L1, L2 or L3 can be connected to the positive line 73 via the upper circuit breakers 80, 82 and 84, and the respective winding connection L1, L2 or L3 can be connected via the lower circuit breaker 81, 83 and 85 and a measuring resistor 87 to be connected to the negative line 74.
  • the DC machine 32 has a central control unit 34. This controls the upper and lower circuit breakers 80 to 85.
  • the measuring resistor 87 serves to measure the current i_2 flowing through the lower bridge transistors 81, 83 and 85 on the basis of the voltage between the point 88 and ground GND and to supply a current limiting arrangement in the central control unit 34.
  • this current can flow in both directions: in the direction shown when the DC machine 32 draws electrical power, and in the opposite direction when the DC machine operates as a generator and outputs power which then flows into the capacitor 75.
  • the current i_2 in the feed line to the motor 32, as measured at the measuring resistor 87 is a pulsed direct current, usually with a frequency of about 20 kHz.
  • the current through the phases 115, 116, 117 of the motor 32 - because of the freewheeling diodes 90 to 95, the regulation, and because of the preferred "mutual clocking", as will be described below - takes the form of relatively low-frequency current pulses of variable amplitude, as shown in Figs. 19A and 19B.
  • the current I in the region of the pulse roof Z is practically constant.
  • the electronics of the motor 32 thus measure the pulse-shaped current i_2 in the feed line to the motor 32 and thus cause pulses in the motor 32 with an essentially constant amplitude, as shown by way of example in FIG. 19B.
  • the rotor position sensors 111, 112 and 113 are arranged at an angular distance of 120 ° el. From each other around the rotor 110 and serve to determine its position.
  • the rotor position sensor 111 is arranged at 0 ° el. (0 ° mech.)
  • the rotor position sensor 112 at 120 ° el. (60 ° mech.)
  • the rotor position sensor 113 at 240 ° el. (120 ° mech.), Or in equivalent positions.
  • the rotor position sensor 111 supplies a Hall signal HS1, the rotor position sensor 112 a Hall signal HS2 and the rotor position sensor 113 a Hall signal HS3, cf. 3 and 15.
  • the Hall signals HS1, HS2, HS3 are fed to the central control device 34, which determines the position of the rotor 110 and its speed n from this.
  • FIG. 3 shows a table which shows the current supply to the upper circuit breakers 80, 82 and 84 (column 704) and the lower circuit breakers 81, 83 and 85 (column 702) as a function of the Hall signals HS1, HS2 and HS3 (column 700) for indicates a direction of rotation of the DC machine.
  • the angular range of the electrical angle phi_el specified, e.g. 0 ° el. to 60 ° el.
  • Fig. 4 The case of Fig. 4 is described below that e.g. the MOSFETs 80 and 81 are turned on alternately, which is referred to as "mutual clocking".
  • a “1” in one of the lower circuit breakers 81, 83, 85 means that the latter is clocked by a PWM signal, that is to say is switched off and on with a specific duty cycle.
  • a "1" for a lower power switch means that this is clocked by a PWM signal (FIG. 5C) and that the associated upper power switch is triggered by the inverted PWM signal (FIG. 5B) also clocked, that is, switched off and on. More about simple and mutual clocking is shown in FIG. 4.
  • EN1, EN2, EN3 and IN1, IN2, IN3 determine the activation of a driver module 200 (FIG. 14), which generates a mutual clocking therefrom.
  • PWM signal PWM2 see description of FIG.
  • FIG. 4 shows an equivalent circuit diagram with the circuit parts active for the rotor position in the range from 0 ° ... 60 ° el.
  • the same parts as in Figs. 1 and 2 are given the same reference numerals and will not be described again.
  • the circuit breakers 80, 81, 82 are shown symbolically in the form of switches.
  • winding strand 116 connected between L1 and L2 (to which the series strings 115 and 117 are connected in parallel, as can be seen in FIGS. 1 and 2) is represented as inductor 120, winding resistor 121 and voltage source 122 for those when the rotor 110 is rotated into winding 116 induced voltage UJ, which according to
  • UJ n * k_e ... (3) is proportional to the speed n of the motor and a motor constant k_e.
  • the winding current flowing through the winding 116 is designated i_3, the intermediate circuit direct current i_1 is the smoothed current from the intermediate circuit 73, 74, and i_2 is the pulse-shaped current of the output stage.
  • the upper circuit breaker 82 is closed with a rotor position in the range 0 ° ... 60 ° el.
  • Power can be supplied to the stator winding 114 in various ways:
  • the lower circuit breaker 81 is closed and opened by a PWM signal 228 (pulse width modulated signal); the upper circuit breaker 80 remains open.
  • the engine speed is controlled by the so-called duty cycle toN / T (FIG. 13) of a PWM signal 228 (FIG. 4).
  • the winding current i_3 flows from the positive line 73 via the circuit breaker 82, the winding resistor 121 and the inductance 120 to the circuit breaker 81.
  • the winding current i_3 is increased by the voltage at the intermediate circuit 73, 74, and the motor is driven.
  • current i_2 is equal to current i_3. Therefore, when the switch 81 is closed, the winding current i_3 can be determined and also regulated by measuring the current i_2.
  • the winding current i_3 does not immediately drop to 0, but the inductance 120 tends to maintain the current i_3. Since the diode 91 is not conductive for the current i_3, the winding current i_3 flows via the freewheeling diode 90 and via the closed switch 82.
  • an approximately constant winding current i_3 depends on the pulse duty factor of the PWM signal 228, and the drive current i_2 corresponds to the winding current i__3 when the switch 81 is closed ,
  • the arithmetic mean value of the pulse-shaped current i_2 corresponds to the intermediate circuit direct current i_1.
  • the power switch 81 is switched on and off by the PWM signal 228 as in the simple clocking.
  • the circuit breaker 80 is additionally opened by a PWM signal 227 when the circuit breaker 81 is closed, and vice versa.
  • the PWM signal 227 thus essentially corresponds to the inverted PWM signal 228. Further details are given in FIG. 5.
  • the mutual clocking ensures that the free-wheeling diode 90 is bridged by the conductive MOSFET 80, on which a major part of the power loss arises during the simple clocking. This takes advantage of the fact that the current in MOSFETs can flow in both directions.
  • alternating clocking enables a winding current i_3 in both directions, i.e. motor and generator. With simple clocking, the winding current i_3 can flow through the diode 90 only in a direction driving the direct current machine 32.
  • a winding current i_3 in the opposite direction causes the DC machine 32 to brake.
  • a negative, that is, braking, current is designated i_2 'in FIG. 1. Since the current i_2 or i_2 ', as long as it flows, is the same size as i_3, this current can be used to regulate i_3 to a desired value.
  • 5A to 5F show diagrams of the voltages, currents and powers occurring in FIG. 4 with a mutual clocking.
  • FIG. 5A shows a PWM signal PWM2 180, which has a frequency of 20 KHz, for example and is described in more detail in FIGS. 12 and 13, and with which the signals 227 for actuating the circuit breaker 80 (FIG. 4) and 228 for actuating the circuit breaker 81 (FIG. 4) are generated by the driver module 200 (FIG. 14) become.
  • Signals 227 and 228 are substantially mirror images of one another, ie, when signal 227 is high, signal 228 is low, and when signal 227 is low, signal 228 is high.
  • These signals 227, 228 are separated from one another by dead times ⁇ t (for example 1 ⁇ s), during which the two transistors 80, 81 are non-conductive. During these dead times, a current i_90 (FIG. 5D) flows through the diode 90.
  • 5B schematically shows the current i_80, which is a function of the PWM signal
  • the maximum current i_max has e.g. the value 4 A.
  • 5C schematically shows the current i_81, which is a function of the PWM signal
  • the maximum current i_max has e.g. the value 5 A.
  • 5D shows the current i_90, which flows through the diode 90 in each dead time ⁇ t.
  • the maximum current i_max has e.g. the value 5 A.
  • the dead time ⁇ t must be observed, since if the transistor 80 and the transistor 81 were to become conductive at the same time, a short circuit would occur which would destroy the full bridge.
  • the winding current i_3 (see FIG. 4) therefore flows alternately via the lower switch 81 and the upper switch 80 during the mutual clocking. During the switchover, it flows through the freewheeling diode 90 during a short dead time ⁇ t.
  • 5E shows the resulting power loss P80 from transistor 80 and P90 from diode 90.
  • the maximum power loss P80_max of transistor 80 is, for example, 1 W
  • the maximum power loss P90_max of diode 90 is, for example, 6 W.
  • the alternating clocking thus becomes the power loss during the time that the transistor 81 is open, reduced from the dead time from 6 W to 1 W, since during the time T_80 (FIG. 5E) the transistor 80 with its low internal resistance (eg 60 m ⁇ ) bridges the diode 90.
  • 5F shows the power loss P81 of the transistor 81.
  • the maximum power loss P81_max of the transistor 81 is, for example, 1 W.
  • the measuring resistor 87 (see FIG. 1) is provided in the DC link.
  • the drive current i_2 or the braking current i_2 ' is measured on it.
  • 6 and 8 is based on a comparison between a first signal (for example the signal at input 138 of comparator 137, which can be influenced by the signal PWMJ +), which is preferably in the form of a smoothed analog value, and a second signal , which is in the form of pulses (eg the signal at input 140 of comparator 137, which is derived from drive current i_2).
  • a first signal for example the signal at input 138 of comparator 137, which can be influenced by the signal PWMJ +
  • a second signal which is in the form of pulses
  • the first signal is also preferably derived from a pulse-shaped signal (PWMJ +) if a digital controller is used.
  • PWMJ + pulse-shaped signal
  • a pulse-shaped signal is used as the second signal which is derived from the motor current pulses i_2 and i_2 '.
  • the level of the motor current pulses i_2 or i_2 ' corresponds to the level of the winding current i_3 (cf. description of FIG. 4). It would also be possible to smooth the current pulses i_2 or i_2 'before the comparison and to supply them as an analog second signal. However, due to the smoothing, part of the information regarding the level of the winding current i_3 is lost.
  • the signal PWM2 which determines the switching on and off of the clocked output stage and thus the current i_2 or i_2 ', is determined by the potential at one point 156 (Fig. 6 and 8) controlled, and this potential is determined, among other things, by an analog control value SWA1.
  • the current limiting arrangement changes the potential present at point 156 if the current i_2 or i_2 'becomes too large. This change is extremely rapid, which is why it can also be used for control tasks according to the invention.
  • FIG. 6 shows the current limiting arrangement 131 for the pulse-shaped drive current i_2 flowing through the measuring resistor 87. It is only effective when the current i_2 has the direction shown (motor 32 drives) and is therefore referred to as a "positive" current limitation. Their function is to immediately reduce the pulse duty factor of the PWM2 signal when the current i_2 becomes greater than a value which is predetermined by the pulse duty factor of the PWMJ + signal, and thereby to limit the current i_2 to the set value.
  • the node 154 is connected via a high-resistance resistor 152 to a node 156, which is connected to the input of an analog PWM converter 182 (see FIGS. 12 and 13), at the output of which a PWM signal PWM2 is obtained which 1 and 11, the driver stages 50, 52, 54 is supplied and the level of the drive or braking current in the stator winding 114 is determined.
  • an analog PWM converter 182 see FIGS. 12 and 13
  • the node 156 is connected to a node 146 via a resistor 150.
  • Resistor 150 has a lower resistance than resistor 152, cf. the table below.
  • a small capacitor 148 is between point 146 and GND. 6 and 7A show, the current pulses i_2 of the motor current cause positive voltage pulses u_2 at the negative input 140 of the comparator 137, while at the positive input 138 there is an analog potential PHI1, the level of which is determined by the (variable) pulse duty factor PWMJ +.
  • the minus input 140 of the comparator 137 is connected via a resistor 130 to the node 88 at the measuring resistor 87.
  • the filter capacitor 132 is therefore not used for averaging the motor current i_2, but for filtering spikes at the beginning of each pulse; therefore this capacitor is very small.
  • the measuring resistor 87 is designed here in such a way that a voltage drop of approximately 200 mV occurs across it at the maximum permissible current i_2.
  • An input 304 of the current limiter 131 is supplied by the controller 24 with the PWM signal PWMJ +, which alternates between a positive potential of +5 V and ground potential GND. Between this input 304 and a node 311 there is a resistor 310, and between the node 311 and ground GND there is a capacitor 312. Depending on the duty cycle of the signal PWMJ +, a DC voltage is thus established at the node 311, which e.g. the duty cycle is 100% +5 V and decreases as the duty cycle decreases.
  • the maximum voltage u_2 at the measuring resistor 87 is approximately 0.2 V here, a voltage of +5 V at the plus input 138 of the comparator 137 would be too high. Therefore there is a resistor 314 between the node 311 and the plus input 138, and a resistor 136 between the plus input 138 and ground.
  • the resistors 311, 314, 136 form a voltage divider which determines the potential PHI1 at the plus input 138. PHI1 is thus determined by the pulse duty factor of the signal PWMJ +, and the voltage divider 311, 314, 136 is so chosen so that the maximum current i_2 that is permissible for the motor 32, for example 5 A.
  • FIGS. 7A and 7B explain the mode of operation of FIG. 6. If, in FIG. 7A, a pulse u_2 rises between times t10 and t11 beyond a value which is predetermined by the instantaneous potential PHI1 at plus input 138, the comparator switches 137 between times t10 and t11. Its previously high-impedance output 142 is internally connected to ground GND, so that between t10 and t11 a discharge current flows from capacitor 148 to ground GND via resistor 144 and the potential at point 146 consequently decreases. This also reduces the potential u_156 at point 156, cf.
  • PWM2 determines the amplitude of the pulses i_2. This amplitude therefore decreases and is limited to the value specified by PWM J +.
  • the value PHI1 is reduced in this example by slowly reducing the pulse duty factor PWMJ +. Therefore, between t12 and t13, the amplitude u_2 is greater than PHI1, so that the output 142 is switched to ground and consequently the potential u_156 at the node 156 decreases, as shown in FIG. 7B. The same happens between times t15 and t16, times t17 and t18, and times t19 and t19A.
  • the potential u_156 follows the setpoint PHI1 with a slight delay, which in turn is predetermined by the (variable) value PWMJ +, and since u_156 determines the voltage on the stator winding 114 and thus the amplitude of the motor current i_2, the motor current drops i_2 accordingly and is consequently determined by the signal PWMJ +.
  • the signals could be in such an arrangement PWMJ + and PWM1 can also be specified as analog signals, but digital signals have the great advantage that they can be calculated, generated and changed very quickly with digital precision in one (or more) microprocessors.
  • resistor 150 is significantly smaller than resistor 152, the potential of point 146 has priority over the potential SWA1 of point 154, so that if current i_2 is too high, potential u_156 at point 156 is immediately reduced, even if PWM1 is high ,
  • the maximum permissible current i_2 can be set very conveniently within the adjustment range of the current limiting arrangement 131, e.g. from 0 ... 5 A if the maximum permissible current i_2 is 5 A.
  • the current limiting arrangement 131 can be used to regulate the speed of the motor 32 by changing the value PWMJ +.
  • PWM1 is constantly set to a high value, e.g. to 100%.
  • PWM1 is set to a speed-dependent value, e.g. to 0% at speed 0, to 50% at 10,000 rpm, and in between to linearly variable intermediate values.
  • the current limiting arrangement 131 can also be used to regulate the current in the driving motor 32 to a constant value, in which case PWM1 is also set to 100%.
  • PWMJ + is set to a constant value, and the motor 32 then delivers a constant drive torque in a larger speed range, cf. curve 796 in FIG. 36.
  • the arrangement 131 can also serve in the usual way to limit the motor current i_2 to a maximum permissible value, for example 5 A, in which case PWMJ + is set to its maximum value and the speed n is regulated by changing the signal PWM1.
  • the motor 32 is used only for driving and not for braking, the current limiting arrangement 161 (FIG. 8) can be omitted.
  • the motor can be operated with one-sided clocking, as described above. Alternatively, alternate clocking can also be used in this case, which has particular advantages in terms of efficiency.
  • FIG. 8 shows the "negative" current limiting arrangement 161. Its function is to increase the pulse duty factor of the signal PWM2 when the braking current i_2 'is higher than a value which is predetermined by the pulse duty factor of the signal PWMJ-.
  • the same reference numerals are used for parts that are the same or have the same effect as in FIG. 6. For this, reference is made to FIG. 6.
  • the maximum braking current in this example was 5 A, the minimum 0 A.
  • the arrangement 161 of FIG. 8 contains a comparator 167, the output 172 of which is connected to the anode of a diode 176, the cathode of which is connected to the point 146. Furthermore, the output 172 is connected to the regulated voltage + Vcc (here: +5 V) via a resistor 174. Vcc is also connected via a resistor 162 to the minus input 170 of the comparator 167, which is connected via a resistor 160 to the node 88 and via a small capacitor 163 to ground GND.
  • Vcc is also connected via a resistor 162 to the minus input 170 of the comparator 167, which is connected via a resistor 160 to the node 88 and via a small capacitor 163 to ground GND.
  • the plus input 168 of the comparator 167 is connected to ground via a resistor 166 and directly to a node 324, which is connected to ground via a capacitor 322 and to an input 308 via a resistor 320, to which the signal PWMJ- is fed.
  • capacitor 322 serves as a low pass filter.
  • the analog control value SWA1 at point 154 is fed to point 156 via high-resistance resistor 152.
  • the current u of the stator winding 114 and thus also the current through the measuring resistor 87 are determined by the potential u_156 at point 156. Is this stream negative, this is called a braking current i_2 '. If this braking current rises above a value which is determined by the pulse duty factor of PWMJ-, the current limiter 161 immediately pulls the potential at point 156 upwards and thereby increases PWM2 so much that the braking current i_2 'maximally that by PWMJ - can assume the specified value.
  • the signal PWMJ- is fed from the controller 24 to the input 308.
  • the amplitude of the PWMJ- pulses is +5 V.
  • the voltage divider formed by resistors 160 (e.g. 1 k ⁇ ) and 162 (e.g. 22 k ⁇ ) at negative input 170 of comparator 167 has the following potentials: With an amplitude of the braking current of 0 A:
  • FIG. 9A shows typical potential profiles u_2 "at the minus input 170 when a braking current i_2 'is flowing.
  • a braking current i_2 ' is flowing.
  • this potential drops with a braking current pulse a value that is lower, the higher the amplitude of the braking current pulse.
  • the potential PHI2 at the plus input 168 of the comparator 167 is determined by the pulse duty factor of the signal PWMJ-, its amplitude (here: + 5 V), and the voltage divider ratio of the resistors 320 (e.g. 22 k ⁇ ) and 166 (e.g. 10 k ⁇ ).
  • the potential PHI2 increases from 0 V to + 0.22 V. 9A shows a potential PHI2 of approximately 0.1 V, which would correspond to a target braking current of approximately 2.6 A in this example.
  • the input 170 becomes more negative than the input 168, and the output 172 becomes high-resistance. This is e.g. 9A between t20 and t21, likewise between t22 and t23.
  • Output 172 is then also connected to ground GND during these time intervals, and diode 176 blocks, so that the potential u_156 decreases because a current flows from point 156 to point 154.
  • the (small) capacitor 148 prevents abrupt voltage changes at point 146.
  • Resistor 174 is smaller than resistor 152, so that current limiter 161, which charges capacitor 148, takes precedence over value SWA1 at point 154.
  • the small capacitor 163 prevents short spikes from influencing the comparator 167.
  • the level of the permissible braking current i_2 ' is therefore directly influenced by the pulse duty factor of the PWMJ- signal, and the brake current cannot exceed the value which is predetermined by this pulse duty factor. 6 and 8, they can be used very well for control tasks, as will be described below.
  • the encoder for PWM1 has the function of a digitally controllable voltage source and could of course also be replaced by another controllable voltage source or a switchable voltage source.
  • the maximum speed njmax is fixed to a value to the left of the motor curve 790 ', i.e. Between this value and the motor curve 790 'there is an area 795 which is not used because operation in this area would normally lead to an overload of the motor 32.
  • the motor 32 only operates in a range 797, which is defined by T_max and njmax.
  • the torque-speed characteristic curve 792 consequently has the profile according to FIG. 47, i.e. the motor practically achieves its full torque T_max up to the specified speed n nax because the falling branch 796 (indicated by dash-dotted lines) of the torque-speed characteristic is not used.
  • 19A and 19B show this difference with great clarity.
  • This difference in FIG. 19B enables a higher torque T and thus a higher output to be obtained from a given motor 32.
  • An additional advantage is that the torque fluctuates very little.
  • FIG. 10 shows a combination of "positive" current limit 131 (FIG. 6) and “negative” current limit 161 (FIG. 8), which together influence the potential at point 156 such that motor current i_2 is less than a value determined by PWMJ + and the braking current i_2 'is less than a value determined by PWMJ.
  • the potential at point 88 is supplied to both the positive current limit 131 and the negative current limit 161.
  • the outputs of the current limiters 131 and 161 are both connected to the capacitor 148.
  • the small capacitor 148 which is important for the potential at point 156, is charged to the potential SWA1 at point 154 via the resistors 152 and 150. If the current limiters 131 or 161 are not active, the potential at point 156 is therefore only determined by the signal PWM1 from RGL 24.
  • the capacitor 148 (for example 100 pF) is charged or discharged, as already described.
  • the hardware current limit has priority over signal SWA1 because resistor 144 (FIG. 6) for discharging capacitor 148 and pull-up resistor 174 (FIG. 8) for charging capacitor 148 have a lot are smaller than resistor 152.
  • the capacitor 148 is recharged to the potential of point 154.
  • resistor 150 is significantly smaller than the resistor
  • the frequencies of all signals PWM1, PWM2, PWMJ +, PWMJ- were in this embodiment in the order of 20 kHz.
  • the pulse duty factor PWM1 when braking is preferably speed-dependent, e.g. 0% when the engine is at a standstill, 50% at 10,000 rpm, increasing linearly in between.
  • FIG. 11 shows an overview of a preferred exemplary embodiment of an electronically commutated motor 32 according to the invention.
  • ⁇ C 23 eg PIC 16C72A from Microchip, optionally with additional components.
  • the three rotor position sensors 111, 112 and 113 are connected in series and connected to +12 V via a resistor 64 and to ground (GND) via a resistor 65.
  • the signals of the rotor position sensors 111, 112 and 113 are processed in signal conditioners 61, 62 and 63 and fed to the ⁇ C 23 as Hall signals HS1, HS2 and HS3, which are shown schematically in FIG. 15.
  • Three potentiometers 43, 45, 47 are each connected between the voltage + Vcc and ground (GND).
  • the potentials that can be set by means of the potentiometers 43, 45 and 47 are fed to three analog inputs 44, 46 and 48 of the ⁇ C 23.
  • the ⁇ C 23 has an A / D converter 30.
  • Two control channels IN_A and IN_B of the ⁇ C 23 can be connected to a potential +5 V via a switch 41 or 42.
  • the bus 18 (FIG. 1) is connected to the ⁇ C 23 and the EEPROM 20 (non-volatile memory) is connected to the ⁇ C 23 via a bus 19.
  • the operating voltage + UJ3 of the motor 32 is tapped at point 76 (FIG. 1) and fed to the input 68 of the ⁇ C 23 via two resistors 66 and 67 connected as voltage dividers.
  • the ⁇ C 23 is connected to the driver stage 50 via the outputs EN1, IN1, to the driver stage 52 via the outputs EN2, IN2, and to the driver stage 54 via the outputs EN3, IN3.
  • the driver stages 50, 52 and 54 are in turn connected to the final stage 78 (FIG. 2).
  • a PWM generator 182 (FIGS. 12, 13) generates a signal PWM2 180, which is fed to the driver stages 50, 52 and 54. Its output 180 is connected to +5 V via a resistor 184 and to ground (GND) via a zener diode 186. The latter limits the amplitude of signal PWM2 180, and resistor 184 serves as a pull-up resistor for the open collector output of PWM generator 182.
  • the ⁇ C 23 has the controller RGL 24 and three PWM generators 25, 27 and 29 which can be controlled by this.
  • the PWM generator 25 has an output PWM1 157, which is connected to the point 156 via the RC element formed by the resistor 158 and the capacitor 159 and the resistor 152.
  • the PWM generator 27 has an output PWMJ- which is connected via line 308 to the negative current limiter 161 (FIG. 8).
  • the PWM generator 29 has an output PWMJ + which is connected via line 304 to the positive current limiter 131 (FIG. 6).
  • the point 88 on the measuring resistor 87 is connected to the positive current limit 131 and the negative current limit 161.
  • the positive current limiter 131 and the negative current limiter 161 are connected to the point 156 via the capacitor 148 connected to ground (GND) and the resistor 150, as explained in detail in FIGS. 6, 8 and 10.
  • the driver stages 50, 52 and 54 control the bridge branches in the final stage 78, via which the stator windings 114 are energized (FIG. 2).
  • the driver stages 50, 52 and 54 are controlled on the one hand by the ⁇ C 23 via the lines EN1, IN1, EN2, IN2, EN3 and IN3 and on the other hand via the signal PWM2 180.
  • the signals EN1, IN1, EN2, etc. control which of the stator windings 114 are energized (cf. description of FIGS. 2 and 3).
  • the signal PWM2 180 controls how large is the current that flows through the motor windings (cf. description of FIG. 4).
  • the ⁇ C 23 receives three rotor position signals HS1, HS2 and HS3 via the rotor position sensors 111, 112 and 113, from which it can determine the position of the rotor 110 and thus the necessary commutation via the outputs EN1, IN1, EN2 etc.
  • the ⁇ C 23 has the controller RGL 24, which controls the signal PWM1 via the PWM generator 25, the signal PWMJ- via the PWM generator 27 and the signal PWM J + via the PWM generator 29.
  • the signal PWM1 is converted (transformed) via the low pass formed from the resistor 158 and the capacitor 159 into an analog, smoothed signal SWA1 and fed via the resistor 152 to the point 156, which is connected to the PWM generator 182.
  • the potential at point 156 therefore determines the duty cycle of signal PWM2, which controls the current through stator windings 114.
  • a larger duty cycle of the signal PWM1 increases the duty cycle PWM2 and thus the current ij2 through the stator windings.
  • the signal PWM1 is thus “transformed” into a PWM signal PWM2 via the low pass 152, 158, 159 and the PWM generator 182. This "transformation” is influenced by the two current limits 131, 161 if they are active.
  • the PWMJ + signal controls the threshold above which the positive current limit 131 becomes active
  • the PWMJ- signal controls the threshold above which the negative current limit 161 becomes active.
  • the potential u_156 is reduced until the motor current i 2 is again below the threshold value.
  • the potential u_156 is raised until the braking current i 2' is again below the threshold value.
  • Both the positive current limit 131 and the negative current limit 161 at point 156 take precedence over the analog signal SWA1 controlled by PWM1 (cf. FIGS. 6, 8, 10).
  • the controller RGL 24 of the ⁇ C 23 has several options for controlling the motor 32:
  • PWM1 is variable; PWMJ + is set to 100%, for example, and PWMJ- is set to 0%, for example.
  • Analogue manipulated variables can be fed to the ⁇ C 23 via the three potentiometers 43, 45 and 47.
  • the potentials at the inputs 44, 46 and 48 can be digitized via the A / D converter 30 and used as manipulated variable, e.g. for a speed setpoint n_s.
  • the two inputs IN_A and INJ3 of the ⁇ C 23 can be set to HIGH (switch closed) or LOW (switch open) via switches 41 and 42 in order to e.g. to set an operating mode MODE of the ⁇ C 23.
  • the ⁇ C 23 can be connected to other devices, e.g. a PC or a control device, e.g. Exchange control commands and data in both directions, or write data to or read from the EEPROM 20.
  • the EEPROM 20 non-volatile memory
  • the EEPROM 20 is connected to the ⁇ C 23 via the bus 19, and the ⁇ C 23 can e.g. Read operating parameters from EEPROM 20 or write to EEPROM 20.
  • the operating voltage + UJ3 of the motor 32 is tapped at point 76 (FIG. 1) and fed to the ⁇ C 23 via the two resistors 66 and 67, which act as voltage dividers.
  • the potential at point 68 is digitized by the A / D converter 30.
  • the resistors 66, 67 transform the operating voltage + UJ3 into a range suitable for the A / D converter 30.
  • the ⁇ C 23 thus has the current operating voltage + UJ3 available, e.g. to to implement voltage monitoring, cf. 25 and 26.
  • FIG. 12 shows an example of a known circuit for the PWM generator 182. Parts which are the same or have the same effect as in the previous figures are identified by the same reference numerals as there and are usually not described again.
  • the manipulated variable u_156 is in the form of the potential at point 156 (FIG. 11).
  • the minus input of the comparator 188 there is a triangular signal 198 generated by a triangular oscillator (sawtooth oscillator) 183 (FIGS. 12 and 13).
  • the triangular oscillator 183 has a comparator 190.
  • a positive feedback resistor 192 leads from the output P3 of the comparator 190 to its positive input.
  • a negative feedback resistor 191 leads from the output P3 of the comparator 190 to the negative input P1 of the comparator 190.
  • a capacitor 195 lies between the negative input of the comparator 190 and ground.
  • the output P3 of the comparator 190 is also connected to + Vcc via a resistor 193.
  • the positive input P2 of the comparator 190 is connected to + Vcc or ground via two resistors 194 and 196.
  • the output of the comparator 188 is high-impedance and the pull-up resistor 184 pulls the line PWM2 180 to HIGH. If the voltage of the triangular signal 198 is higher than that of the signal u_156, the output of the comparator 188 is low-resistance and the signal PWM2 180 is LOW. If an inverted PWM signal is required, the plus input and the minus input on the comparator 188 are interchanged.
  • FIG. 13A shows the triangular signal 198 and the manipulated variable u_156 at point 156
  • FIG. 13B shows the PWM signal PWM2 180 resulting from FIG. 13A.
  • the triangular signal 198 of the triangular generator 183 is shown idealized. In reality it does not have a perfect triangular shape, but this does not change the mode of operation of the PWM generator 182 from FIG. 12.
  • the triangular signal 198 has an offset 199 from the voltage 0 V.
  • the manipulated variable u_156 therefore only causes a duty cycle TV> 0 if it is above the offset 199.
  • the duty cycle TV of the signal PWM2 (FIG. 5A, FIG. 13) is defined as TV can be between 0% and 100%. If the engine speed is too high, for example, u_156 is reduced and TV is reduced, cf. Fig. 13. This is called pulse width modulation (PWM).
  • PWM pulse width modulation
  • the pulse duty factors are designated PWM1 and PWM2 for better understanding.
  • driver stage 50 for the winding connection L1.
  • the other two driver stages 52 and 54 are constructed identically.
  • the driver stage 50 switches the upper circuit breaker 80 and the lower circuit breaker 81 based on the signals EN1, IN1 and in connection with the signal PWM2 180.
  • a driver module 200 of the L6384 type from SGS-Thomson is used in this exemplary embodiment.
  • the driver module 200 has a dead time generator 202, a release logic 204, a logic 206, a diode 208, an upper driver 210, a lower driver 212 and the connections 221 to 228.
  • the ⁇ C 23, or possibly a simpler logic circuit, is connected to the connections EN1 and IN1, cf. Fig. 11.
  • a transistor 250 switches on and becomes low-resistance.
  • a resistor 252 which, as explained below, determines a dead time of the driver module 200, is thereby bridged, and the input 223 thereby becomes low-resistance.
  • the upper driver 210 and the lower driver 212 and thus also the bridge arm with the circuit breakers 80, 81 are switched off.
  • the signal IN1 has no influence on the driver module 200.
  • the ⁇ C 23 receives control over the driver module 200 via the transistor 250 and thus also via the winding connection L1.
  • transistor 250 is blocked and has a high resistance.
  • a constant current from driver module 200 flows to ground via resistor 252 (eg 150 k ⁇ ).
  • a voltage drops across resistor 252, which is present at input 223. If this voltage is above, for example, 0.5 V, the driver module 200 is activated. If, on the other hand, the transistor 250 is conductive, this voltage drops to practically zero and the driver module 200 is deactivated.
  • the voltage at input 223 is also used to set the dead time.
  • the ⁇ C 23 is reset, all inputs and outputs of the ⁇ C 23 are high-impedance, including IN1 and EN1. In this case, transistor 250 is switched on via resistors 242 and 244, and driver module 200 is thereby switched off. This brings additional security.
  • a circuit without transistor 250 and resistors 242, 244 and 248 would also be theoretically possible.
  • the signal EN1 would have to be set to TRISTATE to switch on the driver module 200 and to LOW to switch off.
  • the ⁇ C 23 is reset, however, the inputs and outputs of the ⁇ C 23 become high-resistance, as stated above, and the driver module 200 and thus the respective bridge branch would be switched on, which could lead to uncontrolled switching states and is therefore not desired.
  • dead time generator 202 Each time the signal at input 221 of driver module 200 changes, dead time generator 202 generates a dead time during which both drivers 210 and 212 are switched off, so that there is no short circuit in the individual bridge branches.
  • the dead time can be set via the size of the resistor 252 and is e.g. 1 ⁇ s.
  • the ⁇ C 23 switches on the upper driver 210 of the driver module 200.
  • the ⁇ C 23 switches on the lower driver 212 of the driver module 200.
  • the signal of the output IN1 has priority over PWM2, i.e. this has no influence here either.
  • the signal IN1 is only set to zero when "pumping" via the ⁇ C 23, i.e. the driver module 200 can be controlled so that the bridge transistors 80, 81 serve as a charge pump. This is described below.
  • the ⁇ C 23 can determine whether the signal PWM2 should have priority for the control of the input 221 of the driver module 200. If PWM2 has priority, the ⁇ C 23 IN1 sets to TRISTATE. However, the ⁇ C 23 has priority if it sets IN1 to HIGH or LOW.
  • the signal PWM2 is only introduced so shortly before the driver module 200 and the ⁇ C 23 nevertheless remains in control of the driver module.
  • the signals IN1, EN1, etc. from the control logic are output first, and only then is the PWM2 signal introduced.
  • a capacitor 230 and the diode 208 integrated in the driver module 200 represent a BOOTSTRAP circuit.
  • the BOOTSTRAP circuit is necessary if 80 N-channel MOSFETs are used for the upper power switch, because they require a drive voltage which is above the voltage to be switched - here + UJ3 - lies.
  • the circuit breaker 81 If the circuit breaker 81 is closed, the winding connection L1 is grounded and the capacitor 230 is charged to +12 V via the diode 208, cf. Fig. 14.
  • the circuit breaker 81 is turned off and the circuit breaker 80 switched on, the upper driver has a voltage at input 228 which is 12 V above the voltage of winding connection L1.
  • Upper driver 210 can thus turn on upper circuit breaker 80 as long as capacitor 230 is charged.
  • the capacitor 230 must therefore be charged at regular intervals, which is referred to as "pumping". This principle is known to the person skilled in the art as a charge pump. Pumping is monitored and controlled by the ⁇ C 23, cf. S616 in Fig. 20.
  • Two resistors 232 and 234 limit the maximum driver current for transistors 80, 81, and a capacitor 236 supplies a briefly high current required for driver module 200.
  • FCT_PUMP 1
  • a routine PUMP S616 (FIG. 24) is called by a function manager 601 (FIG. 20).
  • all outputs EN1, IN1, EN2, IN2, EN3, IN3 of the ⁇ C 23 (FIG. 11) are set to LOW for a time of approximately 15 to 20 ⁇ s.
  • the lower circuit breakers 81, 83 and 85 (FIG. 2) are switched on, the upper circuit breakers 80, 82, 84 are switched off, and thus all driver stages 50, 52 and 54 (FIG. 11) are pumped.
  • the driver stages are reactivated in accordance with the stored Hall signals HS1, HS2 and HS3, as described in FIGS. 2 and 3.
  • the Hall signal HS 265 changes from HIGH whenever the Hall signals HS1, HS2 or HS3 change to LOW or LOW to HIGH, so that the Hall signal HS 265 changes every 60 ° el. (30 ° mech.). These changes in the Hall signal HS 265 are called Hall changes 267.
  • the speed n of the rotor 110 can be determined from the Hall time t_HALL (FIG. 15D) between two Hall changes 267.
  • the motor 32 as shown in FIGS. 1 and 11, can be operated in different operating modes. 16 shows an overview of four possible operating modes.
  • the first distinction with S500 is the choice between a voltage position (U position or U_CTRL) and a current position (I position or LCTRL).
  • the speed control via current position in S518 is carried out - as shown in S520 - by setting PWM1 to a value Ujmax, Ujmax preferably being as large, e.g. 100% that the positive current limitation is always active.
  • the control value PWMJ + for the positive current limitation is now controlled by a control value of the regulator RGL 24, and the speed n of the motor 32 is regulated thereby.
  • the allowable braking current Ijmax- is determined according to the data of the motor 32.
  • the positive torque setting (S510) which drives the motor 32 is carried out by setting the signal PWM1 to a value Ujmax according to S512, which is preferably as large, e.g. 100% that the positive current limitation is always active.
  • the control value PWM J + is then set to a value l (T +) belonging to the positive torque T +, e.g. a duty cycle that corresponds to 2.3 A.
  • the control value PWMJ- is set to the value Ijmax-, which corresponds to the maximum permitted braking current i_2 ', e.g. to 0%.
  • the negative torque setting (S514) that brakes the motor 32 becomes carried out by setting the signal PWM1 to a value U jmin according to S516, which is preferably so small that the negative current limitation is always active.
  • the control value PWMJ- is set to a value l (T-) belonging to the negative torque T-.
  • the control value PWM J + is set to the value I _max +, which corresponds to the maximum permissible drive current i_2.
  • the torque generated by the electric motor 32 is essentially proportional to the current i_2 during the time during which the respective lower circuit breaker 81, 83 or 85 is closed.
  • the positive torque setting (S510 in FIG. 16) takes place in an area 290.
  • the motor 32 drives with an adjustable positive torque T +.
  • the negative torque setting (S514 in Fig. 16) takes place in an area 292.
  • the motor 32 brakes with an adjustable negative torque T-.
  • the torque setting offers the possibility of setting a desired torque T of the motor 32 in both directions, that is to say driving or braking. If no braking torque is required, the relevant part can be omitted.
  • a voltage U which causes a winding current I 308 (the current I at point 308) through the stator winding 303, the latter lying between points 302 and 308. It can be viewed as a parallel connection of an inductor L 304 and a resistor R 306.
  • the stator winding 303 creates a time delay between the changing voltage U 300 and the resulting winding current I 308.
  • the current I 308 through the stator winding 303 causes a specific magnetic flux density and thus a torque T 312 on the permanent magnetic rotor (110 in FIG. 1) via the device constant K_T of the winding 303 or the motor 32.
  • the torque T 312 influences the angular frequency ⁇ 318 of the rotor as a function of the moment of inertia J 314 of the rotor 110 (FIG. 1) and the load LOAD 316 applied.
  • the angular frequency ⁇ 318 finally gives the speed n 328 in rpm via a conversion factor 60 / (2 ⁇ ).
  • the speed control n_CTRL via the U position U_CTRL changes the voltage U via the point 330 to the manipulated value calculated by the regulator RGL 24 (FIG. 11) so as to influence the speed n of the rotor 110.
  • the U position has a long controlled system (pT1 element), which leads to poor control, particularly in the case of rapidly changing loads LOAD.
  • the speed control n_CTRL via I position LCTRL (S518 in FIG. 16) or the torque position T CTRL via I position (S510 or S514 in FIG. 16) controls the winding current I 308.
  • the winding current 308 is measured at point 332 , and the voltage U 300 is set via point 330 such that the speed control via I position (S518 in FIG. 16) or the torque position T OTRL via I position (S510 or S514 in FIG. 16) predetermined winding current I 308 flows through the stator winding 303.
  • FIG. 19A shows the current I 334 through one of the winding connections L1, L2 or L3 (FIG. 1) in the speed control n_CTRL via U position (S502 in FIG. 16), in which the voltage U 300 (Fig. 18) is constant over a short period of time.
  • the time delay due to the stator winding 303 results in a slow increase in current I at location 335 of FIG. 19A. Commutation takes place at point 336, ie another stator winding 303 is energized, and current I 334 rises briefly due to the lower back EMF 324 (FIG. 18).
  • 19B shows the current I 337 through one of the winding connections L1, L2 or L3 (FIG. 1) with the speed control via the I position (S518 in FIG. 16) or the torque position T OTRL via the I position (S510 or S514 in Fig. 16).
  • Current I 337 is largely constant between the start of energization at 338 and the subsequent commutation at location 339, and when commutation at location 339, current I 337 does not have a significant increase as at 336 in FIG. 19A, but becomes practical kept constant.
  • the motor is energized via another of the winding connections L1, L2, L3, e.g. via the winding connection L2, which is not shown.
  • the current profile at the I-position LCTRL is therefore almost constant. This reduces the ripple of the torque generated by the motor and thereby the noise and improves the EMC (electro-magnetic compatibility). Therefore, because of its better EMC, less large capacitors and less circuitry are required to power such a motor. Furthermore, power supplies and cables are less stressed because there are no current peaks, or smaller power supplies can be used.
  • the current I set by the speed control is reached more quickly than in FIG. 19A, and this allows a quick reaction to changes in load. With speed control via I-position LCTRL, this increases the control quality.
  • Speed control via voltage control U_CTRL cannot react so quickly to load changes, since in voltage control U_CTRL the current I and thus the torque T rise or fall more slowly due to the pT1 delay element.
  • the physical limits of the motor 32 are not changed by the I position. For example, the current I 337 will increase more gently in the region 338 at high power since the voltage U cannot be chosen to be as high as desired. In FIG. 19, the motor 32 is therefore operated in an area below its natural characteristic, as is explained in FIG. 47.
  • the main program begins below the interrupt routines. After the motor 32 is switched on, an internal reset is triggered in the ⁇ C 23. The ⁇ C 23 is initialized in S600.
  • the function manager FCT_MAN regulates the sequence of the individual subroutines or routines.
  • routines are processed, which are time-critical and must be executed every time.
  • An example of this is a communication function COMM S604, which carries out the data transmission between the ⁇ C 23 and the EEPROM 20 (FIG. 11) or the bus (data line) 18.
  • S606 stands for any other time-critical function.
  • Functions S612, S616, S620, S624 and S628 come after S606. There is a request bit for each of these functions, which begins with the letters "FCT_".
  • the function XY S612 includes, for example, a request bit FCT_XY.
  • the function manager provides optimal use of the resources of the ⁇ C 23.
  • Fig. 21 shows an embodiment for the routine Hall interrupt S631, which is executed for each Hall interrupt 630 (Fig. 20) triggered by the occurrence of a Hall change (e.g. 267 in Fig. 15D) of the signal HS (HALL).
  • the interrupt could of course also be triggered by an optical or mechanical sensor, and it can therefore also be referred to as a "sensor-controlled interrupt”.
  • the routine Hall interrupt S631 detects the time tJ ⁇ ND of the Hall change, calculates the Hall time LHALL and the speed n from this. The commutation is then carried out and the controller S624 is called.
  • Step S340 stands for actions which may be carried out in the routine Hall interrupt S631.
  • the time of the current Hall change 267 (FIG. 15D) is stored in the variable tj ⁇ ND.
  • the time is taken from the ring counter LTIMER1.
  • the time LHALL is then calculated from the difference between the time tJ ⁇ ND of the current Hall change and the time tj ⁇ ND OLD of the previous Hall change.
  • the value tj ⁇ ND - for the calculation of the next LHALL - is saved in tj ⁇ NDjOLD.
  • the speed n is calculated from the quotient of the speed calculation constant n_CONST and the reverberation time tjHALL. Compare the description of FIG. 15 and equation (10).
  • the commutation of the COMMUT of the output stage 78 takes place in S348 by means of the driver stages 50, 52, 54, cf. Fig. 22.
  • FIG. 22 shows the subroutine COMMUT S348, which carries out the commutation of the final stage 78 (FIGS. 1 and 2) according to the commutation table of FIG. 3 with the aid of the driver stages 50, 52, 54 (FIG. 11).
  • the COMMUT S348 subroutine is called in routine Hall interrupt S631.
  • the subroutine COMMUT S348 is e.g. only after a time dependent on the speed n of the motor 32 has elapsed after the Hall change 267. In many cases, however, such a premature commutation ("early ignition”) is not necessary.
  • the signals IN1, IN2, IN3 are set to 1 in S332. Although this has no effect when driver modules 200 are deactivated, the state of the signals IN1, IN2, IN3 which remains stored is, however, defined for subsequent processes. - Thereupon jumps to the end S334.
  • the setpoints EN1_S, EN2_S, EN3_S for the signals EN1 to EN3 corresponding to the combination HL OOMB of the Hall signals HS1, HS2, HS3 from the table in FIG. 3 are loaded.
  • the setpoints IN1_S, IN2_S, IN3_S for the signals IN1 to IN3 are loaded in S308 in accordance with the combination HL_COMB of the Hall signals HS1, HS2, HS3 from the table in FIG. 3.
  • the table for the IN values is designated TIN1, TIN2, TIN3.
  • driver stages 52 and 54 were activated and the driver stage 50 was deactivated. After commutation, e.g. driver stage 54 is deactivated and driver stages 50 and 52 are activated.
  • Steps S310 to S320 serve to switch off the driver stage that was activated before commutation and should be deactivated after commutation, driver stage 54 in the example above.
  • a driver stage that should be activated before and after commutation is not switched off in between , thereby avoiding losses in the motor 32.
  • the fields in columns EN1, EN2, EN3 are provided with a frame 740, in which the respective driver module is activated during two successive angular ranges.
  • EN1 is set to 1 in S312, and the driver component of the bridge arm of the winding connection L1 is deactivated. If EN1 was deactivated before the commutation, a new deactivation has no effect.
  • the signals IN1, IN2 and IN3 are set to the setpoints IN1_S, IN2_S and IN3_S.
  • the signals EN1, EN2 and EN3 are set to the setpoints EN1_S, EN2_S and EN3_S. Since the driver blocks, which should be deactivated after commutation, have already been deactivated in S310 to S320, S324 switches the driver block on, which was previously switched off. The other driver module, which is switched on both before the commutation and after the commutation, was not switched off in S310 to S320 in order to avoid power losses in the motor 32 which would occur if the power were interrupted.
  • the subroutine COMMUT is ended in S324.
  • a second commutation table for the other direction of rotation analogous to FIG. 3 must be provided.
  • the setpoint EN1 _S is then in S306 e.g. determined by a function TEN1 (HL_COMB, DIR), where DIR stands for the desired direction of rotation.
  • HL_COMB a function TEN1
  • DIR stands for the desired direction of rotation.
  • operation in one direction of rotation is required. Operation with a commutation table for the reverse direction is possible without any problems for the person skilled in the art and is therefore not described further since this is not necessary for understanding the invention and the description is in any case very long.
  • FIG. 23 shows the routine TIMER ⁇ interrupt S639 (cf. FIG. 20), which is executed each time an interrupt 638 occurs, which is triggered by the timer TIMER0 integrated in the ⁇ C 23.
  • the timer TIMER0 is e.g. 1 byte (256 bit) in size, and with a processor frequency of 10 MHz and a prescale of 8, it reaches all
  • a counter subtimer T1 begins in S354.
  • Subtimer means that the steps S356, S358 and S362 explained in the following trigger the actual action in S360 only after a certain number of TIMERO interrupts. This has the advantage that the TIMER0 timer can also be used for other purposes that have to be called up more frequently.
  • the time T1_TIME must go to the respective engine can be adjusted.
  • the counter subtimer CNT_P begins in S362.
  • the counter CNT_P is decremented by 1 in S364.
  • FIG. 24 shows the routine PUMP S616, which is called by the routine TIMERO interrupt S639 when it is necessary to pump.
  • the current commutation state COMMUT STATE is saved in S367.
  • all outputs EN1, EN2, EN3, IN1, IN2, IN3 are set to 0, as a result of which the lower circuit breakers 81, 83 and 85 are closed, so that pumping takes place.
  • the time PUMP_TIME required for pumping is waited in S374.
  • the COMMUT STATE state of the commutation stored in S367 is then restored in S376. This can also be done by using the setpoints EN1 _S, EN2_S, EN3_S, IN1 _S, IN2_S and IN3_S.
  • the subroutine ÜBT S620 which is used to monitor the operating voltage + UJ3, which can be measured in FIG. 11 at connection 68 of the ⁇ C 23. If + UJ3 lies outside a permitted range, the full bridge circuit 78 is influenced accordingly, so that the components connected to the intermediate circuit 73, 74, for example the power transistors 80 to 85, the freewheeling diodes 90 to 95, the capacitor 75, the motor 32 and the components 77 (Fig. 2) cannot be destroyed.
  • the subroutine ÜBT is requested in the interrupt routine TIMERO interrupt S639 (S360 in FIG. 23).
  • 26 shows an example of a time profile of the digitized variable UJ3, which corresponds to the analog variable + U j3 (operating voltage of the motor 32).
  • the value Uj3 can become too small because e.g. the battery is discharged in an electric vehicle. Then the operating voltage drops below a lower limit value Uj IN DFF, and the motor 32 must be switched off automatically. If this voltage then rises above a higher lower limit value U_MIN_ON, the motor 32 can be switched on again. This gives a lower switching hysteresis.
  • variable U_B When braking, the variable U_B can become too large because the motor 32 supplies energy to the capacitor 75 (FIG. 2) as a generator, so that U_B increases because this energy cannot be consumed by the consumers 77. An excessive rise in the voltage U_B must be prevented, since otherwise the components 77 could be destroyed.
  • an increase in the size Uj3 is shown, which is caused by a braking operation of the motor 32.
  • an upper threshold value UjVlAX OFF is exceeded and all transistors 80 to 85 of motor 32 are blocked.
  • the value U_B drops at 344 and reaches the lower value at 346 Threshold value U_MAX_ON, at which the commutation of transistors 80 to 85 is switched on again normally, so that at 348 U j3 rises again.
  • the transistors 80 to 85 are blocked again, so that the value U_B drops again, and at 352 the threshold value UjVlAX DN is reached again, where the commutation of the motor 32 is switched on again. Since in this example the braking process has now ended because the motor reaches its target speed n _s, U _B drops further to a "normal" value 354, which is in the "safe range” 356.
  • a "prohibited area” with an operating voltage Uj3 that is too low is designated by 360, and a prohibited area with an operating voltage UJ3 that is too high is designated by 362.
  • the program according to FIG. 25 serves to implement the processes just described.
  • steps S382, S384 it is checked whether the size Uj3 lies outside the permitted range between U_MIN_OFF and UjVlAXjOFF. If this is the case, the system jumps to S386, otherwise to S390.
  • the motor 32 can supply energy to the capacitor 75 (FIG. 2) as a generator when braking, i.e. when it exceeds the desired speed n_s specified by the speed controller, without the voltage UJ3 at this capacitor being able to assume impermissible values ,
  • the output stage 78 is commutated as a function of the Hall signals HS1, HS2, HS3 if there are no faults.
  • the COMMUT subroutine which is also generally used for commutation, takes the value of UjOFF into account when commutating. If UjOFF has the value 1, all signals EN1, EN2, EN3 (FIG. 11) remain at HIGH, cf. S302 in Fig. 22, i.e. all driver modules 200 (FIG. 14) remain deactivated.
  • variable FCTJJBT is reset to 0 and the function manager FCTjVIAN S602 (FIG. 20) is jumped to.
  • FIG. 27 shows the routine RGL_U S624_1, which carries out a speed control n_CTRL via voltage setting UjOTRL, cf. S502 in Fig. 16, i.e.
  • the speed n is regulated by changing the voltage on the motor 32.
  • the routine RGLJJ is requested by the interrupt routine HALL interrupt S631 (FIG. 21) after the calculation of the speed n, there S350.
  • routine RGLJJ carries out PI control for calculating the manipulated variable RGL_VAL.
  • the control value RGL AL is checked for admissibility and fed to the PWM generator 25 (FIG. 11) for generating the signal PWM1.
  • control difference RGLJDIFF is calculated as the difference between the desired speed n_s and the current speed n.
  • the proportional component RGL_PROP is calculated by multiplying the control difference RGLJDIFF by the proportional factor RGL_P.
  • the new integral component RGLJNT is calculated by adding the old integral component RGLJNT to the result of multiplying the control difference RGLJDIFF by the integral factor RGLJ, and the manipulated variable RGL_VAL results from the sum of the proportional component RGL_PROP and the integral component RGLJNT.
  • steps S404 to S410 it is checked whether the manipulated variable RGL_VAL is in a permissible range.
  • RGL_VAL is greater than the maximum permissible value RGLjMAX, it is set to RGLJvlAX in S410.
  • the value PWM1 is set to the - possibly limited - manipulated value RGL / AL, and the values PWMJ + or PWMJ- are set to the maximum permissible values I _max + or Ijmax- for the maximum current i_2 or i 2 '.
  • the speed n is regulated to the desired value n_s via the voltage setting.
  • the positive hardware current limit 131 (FIG. 6) limits the current i_2 to l_max +, and the negative hardware current limit 161 (FIG. 8) limits the current i_2 'to Ijmax-.
  • routine RGL_U is ended by setting FCT_RGL to 0, and a jump is made to FCTJvlAN S602 (FIG. 20).
  • a PI controller instead of a PI controller, another controller, e.g. a PID controller can be used, as is known to those skilled in the art.
  • a PID controller e.g. a PID controller
  • the routine RGLJ is requested by the interrupt routine HALL interrupt S631 (FIG. 21) after the calculation of the speed n, there S350.
  • the routine RGLJ (FIG. 28) executes a PI control for calculating the manipulated variable RGLJ / AL, which is checked for admissibility and fed to the PWM generator 29 (FIG. 11), which controls the positive current limitation 131.
  • Steps S420 to S430 correspond to analog steps S400 to S410 of routine RGLJJ S624_1.
  • the control difference RGLJDIFF is calculated in S420, the PI controller calculates the manipulated variable RGLJ / AL in S422, and a range check of the manipulated variable RGLJ / AL takes place in S424 to S430.
  • the limitation of RGLJ / AL to RGLjVlAX seems important, because it limits the maximum motor current i 2.
  • the value PWM1 is set to a value Ujmax that is so large that the positive current limitation is always active, e.g. to 100% so that the motor current is always in the form of current pulses.
  • the value PWM J + is set to the control value RGLJ / AL - possibly limited by S424 to S 430.
  • the speed n is thus regulated to the desired value n_s via the current position.
  • the value PWMJ- is set to the maximum permissible value Ijmax- for the maximum current i_2 'and the current speed.
  • the negative hardware current limit 161 limits the current i 2 '.
  • the value RGLjVlAX of the range check in S428 and S430 must be selected so that the current i_2 cannot become greater than the permissible maximum current ljmax +.
  • a PI controller instead of a PI controller, another controller, such as a PID controller can be used, as is known to those skilled in the art.
  • Positive torque setting via current position Fig. 29 shows the routine RGL_T + S624 3, which a positive torque setting TJ TRL pos. Carried out via current position LCTRL, cf. S510 in Fig. 16, i.e. the desired torque T + is set by regulating the current L2 to a predetermined value.
  • the RGL S624 3 routine is requested by the HALL interrupt S631 interrupt routine (FIG. 21) after the speed n has been calculated, there S350. Since no speed control takes place in this case, a call independent of the calculation of the speed n would also be possible.
  • the routine RGL_T + sets the signal PWM1 in S440 to a value Ujmax at which the positive current limitation 131 is constantly active, that is to say usually to 100%.
  • the signal PWMJ + is set to a value l (T +), which corresponds to the desired positive torque T +, and PWMJ- is set to a value I jmax-, which corresponds to the maximum permissible braking current i_2 ', cf. S512 in Fig. 16.
  • the request bit FCT_RGL is reset to 0 because the routine RGL_T + has been processed.
  • the function manager 601 then returns to the start FCTj AN S602 (Fig. 20) jumped.
  • FIG. 30 shows the routine RGL_T-S624_4, which carries out a negative torque setting TJ TRL neg. Via current position LCTRL, cf. S514 in Fig. 16, i.e. the desired braking torque T- is set by regulating the current _2 'to a predetermined value.
  • the routine RGL_T- is e.g. requested by the interrupt routine HALL interrupt S631 (FIG. 21) after the calculation of the speed n, there S350. Since no speed control takes place in this operating mode, a call independent of the calculation of the speed n would also be possible.
  • the routine RGL_T- sets the signal PWM1 to a value U jmin in S450 at which the negative current limit 161 is constantly active.
  • the signal PWMJ- is set to the value l (T-), which corresponds to the desired negative torque T- corresponds, and PWMJ + is set to the value ljmax + corresponding to the maximum permissible drive current i_2, for example to 100%, cf. S516 in Fig. 16.
  • the request bit FCT_RGL is reset to 0 because the routine RGL_T- has been processed.
  • the braking torque is kept at a constant value over a wide speed range.
  • Figure 31 shows the RGL S624 routine. This enables selection of which of the routines RGLJJ S624_1 (FIG. 27), RGLJ S624_2 (FIG. 28), RGL_T + S624_3 (FIG. 29) and RGL_T-S624_4 (FIG. 30) for the controller RGL 24 (FIG. 11) should be used. Alternatively, only one or two of these routines can be provided in an engine. For example, A fan usually does not need a braking routine.
  • the routine RGL S624 is e.g. requested by the interrupt routine HALL interrupt S631 (FIG. 21) after the calculation of the speed n, there S350.
  • the variable MODE specifies the operating mode in which the motor 32 is operated.
  • the MODE variable is set in the MODE S628 routine (Fig. 20).
  • An exemplary embodiment of the MODE S628 routine is given in FIG. 32.
  • This routine sets the operating mode of the motor 32 depending on the input lines IN_A, IN_B, 44, 46 and 48 of the ⁇ C 23 (FIG. 11). It is requested and executed by the routine TIMERO interrupt S639 (FIG. 23) in S360 Function Manager 601 (Fig. 20) called in S626.
  • Current limitation 131 is active l (T +) value for PWM J +, which effects the torque T + l (T-) value for PWM J-, which causes the torque T-
  • Routine MODE S628 uses inputs IN_A and INj3 (Fig. 11), which e.g. can be set from outside the motor 32 or transmitted via the bus 18, which mode MODE should be used.
  • the parameters for the controller RGL S624 (FIG. 31) are set by digitizing the analog value at the input x via the A / D converter 30 (FIG. 11) using a function AD [x].
  • the value x is one of the inputs 44, 46 or 48 of the ⁇ C 23, and its analog value is determined by the potentiometers 43, 45 and 47, respectively.
  • the selected operating mode MODE is set to RGLJJ, so that the routine RGLJJ S624_1 (FIG. 27) is called by the routine RGL S624 (FIG. 31), which controls the speed nJ TRL via the voltage setting U_CTRL performs.
  • the speed specification n_s is set to the digitized value AD [44]
  • the value ljmax + for the maximum permissible drive current L2 is set to the value AD [46]
  • the value Ijmax- for the maximum set braking current L2 ' is set to the value AD [48] set. This will jump to FCTjMAN S602.
  • AD [44] means, for example, the value at input 44 in FIG. 11.
  • the operating parameters which in this exemplary embodiment were entered via the inputs IN_A, INJ3, 44, 46 and 48, can also be entered via the bus 18 or the EEPROM 20, e.g. by exchanging the EEPROM or a ROM.
  • parameters of the motor 32 can also be included.
  • the motor 32 can execute the operating mode RGLJ for a speed control nj TRL via current control LCTRL in response to a signal IN_A in order to achieve a desired speed n_s.
  • the mode S628 is then switched to the operating mode RGL_T-, for example, and the DC machine 32 operates with a constant braking torque, that is to say as a generator.
  • the initial drive of the DC machine 32 to a speed n_s may be necessary, for example, because otherwise the relative speed between the DC machine is too high 32 and an object to be braked would arise.
  • FIG. 33 shows a radial fan 370 with a housing 771, which has an air inlet 772 and an air outlet 774.
  • a motor 32 drives a radial fan wheel 776 to transport air from the air inlet 772 to the air outlet 774.
  • An operating voltage + UJ3 is supplied to the motor 32 via two lines 778.
  • the electrical and electronic components of motor 32 are preferably located in housing 771.
  • FIG. 34 shows characteristic curves of the radial fan 370 of FIG. 33, in which the pressure increase ⁇ p is plotted against the volume flow V / t.
  • the radial fan with speed control n_CTRL was operated via voltage control UJ TRL, whereby it was regulated on curve 780 at 3800 rpm and on curve 782 at 4000 rpm.
  • the radial fan was operated with positive torque control, in which the motor current I was set to a constant value so that the fan wheel 776 is driven with a substantially constant torque over a wide speed range.
  • the characteristic curve 784 of the radial fan which is operated with a positive constant torque, is much better than the curves 780 and 782, since a sufficient volume flow is still generated even with large pressure differences ⁇ p, or in other words: A fan with the characteristic curve 784 can be used generate a sufficiently high volume flow at a significantly higher back pressure. A radial fan with characteristic curve 784 therefore has more fields of application. (The steeper the curve 784 is, the cheaper it is to operate such a fan.)
  • the curve 780 (3800 rpm) corresponds to the curves 786, 792 and 798.
  • the curve 782 (4000 rpm) corresponds to the curves 788 and 794 and 794, respectively .800.
  • Curve 784 (constant torque) corresponds to curves 790, 796 and 802.
  • curve 790 for radial fan 370
  • the speed increases towards a lower volume flow V / t.
  • radial fan 370 operates with a constant torque T +.
  • the current I at curve 796 is constant over a wide range, but decreases slightly towards smaller volume flows. This is probably due to problems with the power supply that was used in the present measurement. In curves 792 and 794, the current I increases with increasing volume flow V / t.
  • a radial fan 370 with positive torque control e.g. In all floors of a high-rise building, where there are very different pressures in the ventilation shaft depending on the floor, ventilation is used, whereas a radial fan 370 with speed control n_CTRL via voltage control UJ TRL could only be used on specified floors, i.e. a greater variety of types of axial fans or radial fans not according to the invention can be replaced by a single type or fewer types of a radial fan according to the invention, which is operated with an essentially constant torque T +.
  • FIG. 38 schematically shows a mobile radio station 650. At the bottom, this has a filter 652 for the cooling air flowing in at 654 and flowing out at 656. There is a radial fan 370 at the top, e.g. of the type shown in FIG. 33. This fan receives its current via a regulator 658. Its current connection is designated as 778 in FIG. 33.
  • the components of the station 650 to be cooled, not shown, are located in a room 660.
  • controller 658 current controller that regulates to a constant current
  • controller 658 is a speed controller that regulates fan 370 to a constant speed of 4000 rpm
  • an operating point 664 results on curve 782 corresponding to a volume flow of 103 m3 / h, i.e. With the new filter 652, the operating points 662 and 664 hardly differ.
  • the fan 370 will be designed in such a case that the amount of cooling air is still 100% when the filter 652 is more dirty.
  • a significant advantage is that if the controller 658 regulates the radial fan 370 to constant current, a single fan is usually sufficient in FIG. 38, whereas if the controller 658 regulates the fan 370 to a constant speed of e.g. 4000 rpm regulates, for safety reasons usually two parallel fans 370 must be used so that the cooling of the components 660 is ensured even when the filter 652 is dirty.
  • the fan 370 with current control (curve 784) can maintain cooling even with a pressure drop ⁇ p of 900 Pa. This is the operating point 668, at which there is still a volume flow of 44 m 3 / h, because according to FIG. 35 the speed n of the fan 370 has risen to 5150 rpm.
  • the increase in speed n with increasing contamination of filter 652 can be used to automatically generate a warning signal when filter 652 is more contaminated.
  • a speed monitoring element 672 is used for this purpose, for example a corresponding routine in the program, which generates a signal ALARM when a speed n 0 (for example 4500 rpm) is exceeded, which is transmitted by telemetry to a central station, so that the filter 652 is activated at the next Routine maintenance is exchanged. If the filter 652 is not replaced, the ALARM signal remains and you have control in the central station whether the maintenance work has been done properly or Not.
  • FIG. 41 shows a ventilation duct 676, the outlet of which is designated 678 and to which six radial fans 370A to 370F of the type shown in FIG. 33 are connected, all of which are regulated to a constant speed of 4000 rpm.
  • 40 shows the associated fan characteristic curve 782, ie at a back pressure of 0 Pa, such a fan delivers about 144 ms of air per hour, and at a back pressure of 400 Pa about 88 m 3 / h.
  • the six fans 370A to 370F which feed into the channel 676, generate e.g. a pressure of about 100 Pa on the right fan 370F, which increases to the left up to 600 Pa (for fan 370A). This results in the flow rates according to the following table:
  • the fan 370F in FIG. 43 conveys an air quantity of 130 m3 per hour and that the fan 370A conveys an air quantity of 76 ms per hour.
  • Such a fan has a very wide range of uses, e.g. for ventilation in high-rise buildings or on long air ducts.
  • Such a radial fan can also be used at even higher back pressures, the drive motor of which is regulated to constant torque.
  • test routine TEST1 S802 for testing an engine for bearing damage and for generating an alarm signal if there is bearing damage.
  • the test routine TEST1 can also be used to test a fan for a clogged filter and to generate an alarm signal if a clogged filter is present.
  • the second variant becomes after the first variant described.
  • Step S800 is preferably carried out in function manager 601 in FIG. 20 between steps S622 and S626.
  • a corresponding test command that sets the value FCT_TEST1 to 1 can be generated at regular intervals, e.g. every 24 hours, or it can be fed to motor 32 via data bus 18, for example. The engine is then tested during operation. This is usually possible with a fan.
  • n_TEST1 1000 rpm
  • step S806 the motor is switched to the RGLJ operating mode (FIG. 28) and the desired speed n_TEST1 is specified, for a fan e.g. 1000 rpm.
  • the motor is regulated to this speed by setting the current via the value PWMJ +.
  • the current in the motor 32 at the speed n_TEST1 is thus obtained directly; this corresponds to the value PWMJ +.
  • the test routine has now started and the variable INJ ⁇ ST1 is set to 1 in S810. Then there is a jump to the start of the function manager FCTjMAN S602.
  • the values PWMJ + and PWM_TEST1 are compared in S814.
  • the COMPARE function is used to check whether the value PWM J +, which corresponds to a specific current in the motor 32, is greater than a predetermined value PWM_TEST1, which is e.g. corresponds to a current of 60 mA.
  • PWM_TEST1 which is e.g. corresponds to a current of 60 mA.
  • the latter means that there is bearing damage, and in this case the program goes to step S816, where an alarm signal is generated (SET ALARM1).
  • the program then goes to step S818, where the old operating mode MODE and the old target speed n_s are restored.
  • the test routine TEST1 can therefore be implemented very easily because, in the speed control according to FIG. 28, the speed is regulated by the motor being given a current value as the setpoint PWMJ +, so that the current in the motor 32 is automatically known and easy in this operating mode can be tested without the need for a special current measurement.
  • the current setpoint PWMJ + corresponds to the actual current through the motor 32, and this setpoint is present in the controller 24 in digital form, so it can be compared with the specified value PWM_TEST1 without any problems.
  • the routine can also be used to test for a clogged filter.
  • the speed n_TEST1 is set to a high value, for example 5000 rpm. at high speeds, the action of a defective bearing is negligible compared to the action of the air and, if applicable, a clogged filter. If the filter is clogged, the fan has less to work and the motor current drops at the same speed compared to a fan with a clean filter.
  • the comparison function COMPARE in S814 therefore reversely tests whether the value PWMJ + is less than the limit value PWM_TEST1. If so, an alarm is triggered in S816 with SET ALARM1.
  • Step S820 shows a test routine TEST2 S822 for testing an engine 32 for bearing damage.
  • the function manager bit FCT_TEST2 is used to check whether the routine TEST2 has been requested (cf. FIG. 20).
  • Step S820 is preferably carried out in function manager 601 in FIG. 20 between steps S622 and S626.
  • the test routine TEST2 S820 is based on a so-called leak test.
  • the motor is first set to a constant speed n_TEST2j3EG, e.g. to 1000 rpm. Then the motor is switched off at a time LMEAS2, and the time LTIMER1-LMEAS2 is measured by means of timer TIMER1 until the motor 32 has reached the speed n_TEST2j ⁇ ND (e.g. 50 rpm).
  • the motor needs a time of 10 seconds, for example, you know that the bearings are in order. If, on the other hand, the engine stops 3 seconds after being switched off, it is assumed that there is bearing damage and generates an alarm signal.
  • the stated time values are only examples and the run-down times depend on various parameters and are usually determined by tests. They can be entered via the data bus 18 become.
  • step S826 If no, the previous operating mode MODE and the previous target speed n_s are stored in step S826.
  • the test routine is now started and the variable INJ ⁇ ST1 is set to 1 in S830. Then there is a jump to the start of the function manager FCTjMAN S602.
  • the speed n_TEST2j3EG is reached in S834, the operating mode MODE is switched to OFF in S836, whereby the motor 32 is de-energized. This can e.g. happen by setting all three values EN1, EN2, EN3 to 1 (see description of FIG. 3).
  • the time at which engine 32 was turned off is stored in LMEAS2.
  • the value IN_TEST2 is set to 2 in S838 because the phase-out phase has now begun.
  • test routine S820 according to FIG. 45 is therefore based on a time measurement, while the test routine S800 according to FIG. 44 is based on a current measurement.
  • Reducing the speed before a measurement is particularly useful for fans in order to largely rule out an influence of the value ⁇ p, e.g. the influence of a dirty air filter.
  • both routines TEST1 and TEST2 can be completely parameterized, configured and adapted to the respective motor via the EEPROM 20 and the bus 18.
  • the direct current machine uses a current limiting arrangement and receives a pulsed direct current continuously at its feed line because the current limiting arrangement is always active.
  • the desired value for example speed, power, drive torque or braking torque, is regulated by changing the current setpoint for the response of the current limiting arrangement, which in the case of such a DC machine acts as if this current setpoint was specified or "impressed" on it.
  • the pulse duty factor of the supplied pulsed direct current is changed in order to maintain this current setpoint in the direct current machine.
  • the DC machine is preferably dimensioned such that its winding has a resistance that would be too low for the machine to be operated directly at the intended operating voltage, that is, it requires operation with current limitation.
  • this aspect is explained using numerical values.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Mechanical Engineering (AREA)
  • General Engineering & Computer Science (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)

Abstract

L'invention concerne une génératrice à courant continu à commutation électronique, équipée d'un rotor et d'un stator, comprenant un dispositif d'enroulement du stator qui peut être alimenté en courant à partir d'une source de courant continu (73, 74) par l'intermédiaire d'un circuit en pont intégral (78). Un dispositif de commutation (49, 50, 52, 54) sert à commuter des commutateurs à semiconducteur (80 à 85) et, en fonction au moins de la position du rotor (110), à mettre en circuit l'un des commutateurs à semiconducteur, au niveau d'une première branche de pont, et à mettre alternativement en et hors circuit, en fonction d'un signal de synchronisation (PWM2), un commutateur à semiconducteur, au niveau d'une deuxième branche de pont, correspondant au commutateur à semiconducteur en circuit au niveau de la première branche de pont. Par ailleurs, un dispositif est conçu pour générer un signal de synchronisation de référence (PWM1) qui influe, par son intensité, sur le rapport cyclique d'impulsions pour la mise en et hors circuit alternée du commutateur à semiconducteur associé à la première branche de pont. En outre, un dispositif de limitation de courant (131, 161), pouvant être commandé par un signal de valeur de consigne de courant (PWM_I+ ; PWM_I-), permet, lorsqu'une valeur de courant définie par le signal de valeur de consigne de courant est atteinte dans la génératrice à courant continu, de modifier le signal de synchronisation de référence de sorte que le courant circulant dans la génératrice à courant continu ne dépasse pas une valeur de courant limite prédéterminée par le signal de valeur de consigne de courant.
EP01965166A 2000-08-30 2001-08-02 Generatrice a courant continu avec dispositif de limitation de courant regulable Withdrawn EP1314241A1 (fr)

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DE10042362 2000-08-30
DE10042362 2000-08-30
PCT/EP2001/008987 WO2002019510A1 (fr) 2000-08-30 2001-08-02 Generatrice a courant continu avec dispositif de limitation de courant regulable

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US (1) US6825632B2 (fr)
EP (1) EP1314241A1 (fr)
AU (1) AU2001285867A1 (fr)
CA (1) CA2421053C (fr)
DE (1) DE10141124A1 (fr)
WO (1) WO2002019510A1 (fr)

Families Citing this family (41)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE50111285D1 (de) * 2000-08-30 2006-11-30 Ebm Papst St Georgen Gmbh & Co Verfahren zum regeln des stromes in einer gleichstrommaschine für einen lüfter
EP1427095B1 (fr) * 2002-12-02 2007-04-18 ebm-papst St. Georgen GmbH & Co. KG Moteur électrique à commutation électronique
US20040232864A1 (en) * 2003-05-23 2004-11-25 Hideki Sunaga Apparatus for controlling motor
DE102004050999A1 (de) * 2003-10-30 2005-06-02 Luk Lamellen Und Kupplungsbau Beteiligungs Kg EC-Motor und Verfahren zum Betreiben eines solchen
FR2867323B1 (fr) * 2004-03-05 2006-10-20 Valeo Climatisation Systeme de commande de vitesse d'un moteur de groupe moto-ventilateur, notamment pour une installation de chauffage et/ou de climatisation de vehicule automobile
FR2890374B1 (fr) * 2005-09-02 2009-05-01 Messier Bugatti Sa Procede de gestion d'un actionneur de frein electromecanique notamment pour aeronef
US20070205731A1 (en) * 2006-03-01 2007-09-06 Regal-Beloit Corporation Methods and systems for dynamically braking an electronically commutated motor
JP4100442B2 (ja) * 2006-09-29 2008-06-11 ダイキン工業株式会社 モータ駆動制御装置ならびにモータの駆動制御システム
GB0709200D0 (en) * 2007-05-12 2007-06-20 Trw Ltd Current measuring apparatus for use with electric motors
JP4301341B2 (ja) * 2007-11-16 2009-07-22 ダイキン工業株式会社 モータ電流算出装置ならびに空気調和装置
US8368331B2 (en) 2008-08-29 2013-02-05 Rbc Manufacturing Corporation Methods and apparatus for monitoring average current and input power in an electronically commutated motor
US8425200B2 (en) 2009-04-21 2013-04-23 Xylem IP Holdings LLC. Pump controller
DE102010047761A1 (de) * 2010-10-08 2012-04-12 Andreas Stihl Ag & Co. Kg Arbeitsgerät mit einem elektrischen Antriebsmotor
DE102012014559A1 (de) 2011-08-06 2013-02-07 Ebm-Papst St. Georgen Gmbh & Co. Kg Lüfter
DE102012203663A1 (de) * 2011-12-14 2013-06-20 Brose Fahrzeugteile GmbH & Co. Kommanditgesellschaft, Würzburg Steuervorrichtung für einen Kühlerlüfter, Kühlerlüfteranordnung und Verfahren
US8905063B2 (en) 2011-12-15 2014-12-09 Honeywell International Inc. Gas valve with fuel rate monitor
US8947242B2 (en) 2011-12-15 2015-02-03 Honeywell International Inc. Gas valve with valve leakage test
US9074770B2 (en) 2011-12-15 2015-07-07 Honeywell International Inc. Gas valve with electronic valve proving system
US8839815B2 (en) 2011-12-15 2014-09-23 Honeywell International Inc. Gas valve with electronic cycle counter
US9995486B2 (en) 2011-12-15 2018-06-12 Honeywell International Inc. Gas valve with high/low gas pressure detection
US9557059B2 (en) 2011-12-15 2017-01-31 Honeywell International Inc Gas valve with communication link
US9846440B2 (en) 2011-12-15 2017-12-19 Honeywell International Inc. Valve controller configured to estimate fuel comsumption
US9851103B2 (en) 2011-12-15 2017-12-26 Honeywell International Inc. Gas valve with overpressure diagnostics
US8899264B2 (en) 2011-12-15 2014-12-02 Honeywell International Inc. Gas valve with electronic proof of closure system
US9835265B2 (en) 2011-12-15 2017-12-05 Honeywell International Inc. Valve with actuator diagnostics
EP2620202B1 (fr) * 2012-01-30 2014-10-29 ABB Oy Procédé et appareil de surveillance de condition de filtre à air
US10422531B2 (en) 2012-09-15 2019-09-24 Honeywell International Inc. System and approach for controlling a combustion chamber
US9234661B2 (en) 2012-09-15 2016-01-12 Honeywell International Inc. Burner control system
JP6173773B2 (ja) * 2013-05-24 2017-08-02 株式会社東芝 可変速制御装置及び運転方法
EP2868970B1 (fr) 2013-10-29 2020-04-22 Honeywell Technologies Sarl Dispositif de régulation
US10024439B2 (en) 2013-12-16 2018-07-17 Honeywell International Inc. Valve over-travel mechanism
US9841122B2 (en) 2014-09-09 2017-12-12 Honeywell International Inc. Gas valve with electronic valve proving system
US9645584B2 (en) 2014-09-17 2017-05-09 Honeywell International Inc. Gas valve with electronic health monitoring
US10503181B2 (en) 2016-01-13 2019-12-10 Honeywell International Inc. Pressure regulator
US10564062B2 (en) 2016-10-19 2020-02-18 Honeywell International Inc. Human-machine interface for gas valve
JP6563434B2 (ja) * 2017-02-24 2019-08-21 ミネベアミツミ株式会社 モータ駆動制御装置及びモータ駆動制御方法
DE102017204046A1 (de) * 2017-03-10 2018-09-13 Maico Elektroapparate-Fabrik Gmbh Verfahren zum Betreiben eines Lüftungsgeräts sowie entsprechendes Lüftungsgerät
US11073281B2 (en) 2017-12-29 2021-07-27 Honeywell International Inc. Closed-loop programming and control of a combustion appliance
US10697815B2 (en) 2018-06-09 2020-06-30 Honeywell International Inc. System and methods for mitigating condensation in a sensor module
CN109185210A (zh) * 2018-10-26 2019-01-11 盛科网络（苏州）有限公司 一种热插拔风扇模块在位后延时上电的方法及装置
US11689124B2 (en) 2021-01-12 2023-06-27 Snap-On Incorporated Controlling brushless motor commutation

Family Cites Families (31)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4654566A (en) * 1974-06-24 1987-03-31 General Electric Company Control system, method of operating an electronically commutated motor, and laundering apparatus
JPS5240188A (en) * 1975-09-26 1977-03-28 Toshiba Corp Device for detecting damages of bearings
DE3024613A1 (de) * 1980-06-30 1982-01-28 Papst-Motoren GmbH & Co KG, 7742 St. Georgen Gleichstromluefter mit regelung
US4933614A (en) * 1986-04-02 1990-06-12 Alps Electric Co., Ltd. Motor drive control circuit
GB2195037B (en) * 1986-07-15 1990-06-06 Martindale Protection Limited Electric motor drive
DE3643221A1 (de) * 1986-12-18 1988-06-30 Braun Ag Gleichstromsteller
SU1654964A1 (ru) 1989-02-01 1991-06-07 Всесоюзный научно-исследовательский и проектно-конструкторский институт по автоматизированному электроприводу в промышленности, сельском хозяйстве и на транспорте Способ управлени асинхронным двигателем с фазным ротором
DE3910643A1 (de) 1989-04-01 1990-10-04 Adolf Schemel Verfahren zur serienmaessigen leistungspruefung von gleichstrom-kleinmotoren mit permanentmagneten
US5463299A (en) * 1989-06-07 1995-10-31 Hitachi, Ltd. Current controller for controlling a current flowing in a load using a PWM inverter and method used thereby
JPH03164093A (ja) * 1989-11-17 1991-07-16 Matsushita Electric Ind Co Ltd 電流検出方法
DE4124240C2 (de) 1990-08-21 1994-08-04 Heidelberger Druckmasch Ag Verfahren zur Regelung des Motorstroms eines bürstenlosen Gleichstommotors
JP3217391B2 (ja) * 1991-07-01 2001-10-09 株式会社東芝 電力変換装置
US5220259A (en) * 1991-10-03 1993-06-15 Graco Inc. Dc motor drive system and method
DE4408442A1 (de) 1994-03-12 1995-09-14 Telefunken Microelectron Schaltungsanordnung zum Regeln der Drehzahl eines elektrischen Motors
DE4408805A1 (de) 1994-03-16 1995-09-21 Detlef Klame Aktive Lüfterüberwachung für Kleinventilatoren mit akustischer und/oder optischer Signaleinrichtung
FI946209A0 (fi) * 1994-12-30 1994-12-30 Nokia Telecommunications Oy Foerfarande foer jaemfoerande av attributvaerden hos kontrollerbara objektuttryck i ett naetelement
DE19501959C2 (de) * 1995-01-24 1998-07-02 Bosch Gmbh Robert Verfahren zum Auswuchten einer elektrisch angetriebenen Luftgebläseeinheit
DE19502907C2 (de) 1995-01-31 1998-07-02 Bosch Gmbh Robert Elektrisch betriebene Luftgebläseeinheit mit Abschaltventil, insbesondere Sekundärluftgebläseeinheit
DE59609466D1 (de) * 1995-04-22 2002-08-29 Papst Motoren Gmbh & Co Kg Verfahren zum Steuern oder Regeln eines Elektromotors, und Anordnung zur Durchführung eines solchen Verfahrens
US5703456A (en) * 1995-05-26 1997-12-30 Emerson Electric Co. Power converter and control system for a motor using an inductive load and method of doing the same
US5689162A (en) * 1995-06-07 1997-11-18 Sgs-Thomson Microelectronics, Inc. Apparatus and method for current sensing for motor driver in pwm mode
DE19647983A1 (de) * 1995-12-04 1997-06-05 Papst Motoren Gmbh & Co Kg Verfahren zum Regeln einer physikalischen Größe und Anordnung zur Durchführung eines solchen Verfahrens
US6078152A (en) * 1996-01-10 2000-06-20 Papst-Motoren Gmbh & Co. Kg Bidirectional E.C. motor and method of operating the motor
DE29615089U1 (de) * 1996-08-29 1996-10-17 Lee, Richard, Taipeh/T'ai-pei Bürstenloser Gleichstromlüfter
US5825597A (en) * 1996-09-25 1998-10-20 General Electric Company System and method for detection and control of circulating currents in a motor
GB2333378B (en) * 1998-01-16 1999-12-08 Hsieh Hsin Mao PWN control circuit for a DC brushless fan
DE19826458A1 (de) 1998-06-13 1999-12-16 Papst Motoren Gmbh & Co Kg Anordnung mit einem Elektromotor
JP3591314B2 (ja) * 1998-07-15 2004-11-17 株式会社日立製作所 ブラシレスモータの制御装置及びこの制御装置を使用した機器
DE19949804A1 (de) * 1998-11-09 2000-05-11 Papst Motoren Gmbh & Co Kg Elektronisch kommutierter Motor
US6147615A (en) * 1999-08-26 2000-11-14 Perfect Three Manufacturing Co. Speed detecting device for a direct current motor, and electric fan with a motor speed detecting device
TW449199U (en) * 1999-12-06 2001-08-01 Asia Vital Components Co Ltd Speed-adjustable fan driving circuit

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
None *
See also references of WO0219510A1 *

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US6825632B2 (en) 2004-11-30
AU2001285867A1 (en) 2002-03-13
CA2421053C (fr) 2009-04-14
CA2421053A1 (fr) 2003-02-28
DE10141124A1 (de) 2002-03-28
US20040104695A1 (en) 2004-06-03
WO2002019510A1 (fr) 2002-03-07

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