EP1116076A2 - Circuit et procede pour ajuster des points de commutation d'un systeme de decision - Google Patents

Circuit et procede pour ajuster des points de commutation d'un systeme de decision

Info

Publication number
EP1116076A2
EP1116076A2 EP99969802A EP99969802A EP1116076A2 EP 1116076 A2 EP1116076 A2 EP 1116076A2 EP 99969802 A EP99969802 A EP 99969802A EP 99969802 A EP99969802 A EP 99969802A EP 1116076 A2 EP1116076 A2 EP 1116076A2
Authority
EP
European Patent Office
Prior art keywords
signal
value
deviation
input signal
continuously
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP99969802A
Other languages
German (de)
English (en)
Inventor
Dieter Draxelmayr
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Siemens AG
Original Assignee
Siemens AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Siemens AG filed Critical Siemens AG
Publication of EP1116076A2 publication Critical patent/EP1116076A2/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K5/00—Manipulating of pulses not covered by one of the other main groups of this subclass
    • H03K5/153—Arrangements in which a pulse is delivered at the instant when a predetermined characteristic of an input signal is present or at a fixed time interval after this instant
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01P—MEASURING LINEAR OR ANGULAR SPEED, ACCELERATION, DECELERATION, OR SHOCK; INDICATING PRESENCE, ABSENCE, OR DIRECTION, OF MOVEMENT
    • G01P3/00—Measuring linear or angular speed; Measuring differences of linear or angular speeds
    • G01P3/42—Devices characterised by the use of electric or magnetic means
    • G01P3/44—Devices characterised by the use of electric or magnetic means for measuring angular speed
    • G01P3/48—Devices characterised by the use of electric or magnetic means for measuring angular speed by measuring frequency of generated current or voltage
    • G01P3/481—Devices characterised by the use of electric or magnetic means for measuring angular speed by measuring frequency of generated current or voltage of pulse signals
    • G01P3/488—Devices characterised by the use of electric or magnetic means for measuring angular speed by measuring frequency of generated current or voltage of pulse signals delivered by variable reluctance detectors
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01P—MEASURING LINEAR OR ANGULAR SPEED, ACCELERATION, DECELERATION, OR SHOCK; INDICATING PRESENCE, ABSENCE, OR DIRECTION, OF MOVEMENT
    • G01P3/00—Measuring linear or angular speed; Measuring differences of linear or angular speeds
    • G01P3/42—Devices characterised by the use of electric or magnetic means
    • G01P3/44—Devices characterised by the use of electric or magnetic means for measuring angular speed
    • G01P3/48—Devices characterised by the use of electric or magnetic means for measuring angular speed by measuring frequency of generated current or voltage
    • G01P3/481—Devices characterised by the use of electric or magnetic means for measuring angular speed by measuring frequency of generated current or voltage of pulse signals
    • G01P3/489—Digital circuits therefor
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K5/00—Manipulating of pulses not covered by one of the other main groups of this subclass
    • H03K5/01—Shaping pulses
    • H03K5/08—Shaping pulses by limiting; by thresholding; by slicing, i.e. combined limiting and thresholding
    • H03K5/082—Shaping pulses by limiting; by thresholding; by slicing, i.e. combined limiting and thresholding with an adaptive threshold
    • H03K5/086—Shaping pulses by limiting; by thresholding; by slicing, i.e. combined limiting and thresholding with an adaptive threshold generated by feedback

Definitions

  • the invention relates to a circuit arrangement and a method for setting switching points of a decision-maker controlled by an analog input signal.
  • sensors are used to detect the movement or the positional state of rotating parts. Examples include crankshaft, camshaft, transmission and ABS sensors in automobiles.
  • Hall sensors are preferably used as sensors which sense the change in a magnetic field.
  • a permanent magnet is attached to a stationary part in order to generate a magnetic field. This magnetic field is then modulated by a gear wheel attached to the rotating part or another ferromagnetic sensor depending on the position.
  • the Hall sensor is preferably located between the permanent magnet and the gear or encoder and can thus detect fluctuations in the magnetic field. For example, if a tooth of the gearwheel lies in the magnetic field, a "high" output signal is provided, while a gap between the teeth results in a "low” output signal. In this way, the current position or position of a rotating part can be inferred from the signal emitted by the Hall sensor.
  • the signal supplied by a sensor is significantly influenced by the operating conditions under which the sensor is used. These operating conditions include unavoidable obstacles, such as working temperature or size of the air gap, etc. Despite the fluctuations caused by the operating conditions, the sensor should provide an output signal that is as well defined as possible. That is, the output signal should be independent of that by the
  • Fluctuations caused by operating conditions have a well-defined course.
  • the reason for this is as follows: For example, a sensor arrangement supplies a sinusoidal one
  • Sensor arrangement controlled system can be obtained when switching operations in the system by the output signal of the
  • the zero crossings are independent of the respective signal amplitude and also have a large slope.
  • a switch point other than zero crossing or signal center may also be advantageous for other signal forms of the output signal of the sensor.
  • a circuit arrangement for setting switching points of a decision-maker controlled by an analog input signal independently of a direct component, which is contained in the input signal as well as upper and lower signal peaks, comprises a control device with peak detectors controlled by the input signal for determining the upper and lower signal peaks of the input signal.
  • the control device includes a controllable reference unit for providing a reference value, an arithmetic unit downstream of the reference unit and the peak detectors for determining the center value from at least one upper and a lower signal peak, and a comparison unit for determining the signal position of the input signal by comparing the reference value with that by Computing unit provided certain mean value.
  • a first control unit downstream of the comparison unit on the input side and linked to the decision maker on the output side is provided for compensating for the DC component of the input signal by a compensation signal if a DC component is determined by the comparison unit.
  • a reference unit connected downstream on the input side and with the reference input on the output side. connected second control unit to the opposite
  • the direct component contained in an analog input signal independently of an alternating component can be determined with relatively little effort and with high accuracy and this is then used to set the switching threshold of a decision maker.
  • the signal path on which the input signal is routed practically only includes the decision-maker himself, so that the signal path is designed as simply as possible and therefore has essentially no impairment of the input signal.
  • the control device preferably has means for digital signal processing.
  • An analog-digital converter is connected upstream of the control device and a digital-analog converter is connected downstream.
  • Digital signal processing offers very precise signal processing with little effort.
  • control device is preceded by a controllable amplifier.
  • the control input of the amplifier is connected to a control output of the control device for controlling the gain of the amplifier as a function of the instantaneous value of the signal fed into the control device.
  • the controllable amplifier in connection with the analog-digital converter creates an analog-digital converter with logarithmic behavior, which enables a very fine resolution in the area of the switchover point of the decision maker. This means that analog-to-digital converters can also be used which have only a low resolution but only require a small amount of circuitry. Thus, with low switching technical effort nevertheless achieved high accuracy.
  • the amplification of the amplifier is preferably graduated in binary form and can be controlled by binary words.
  • a binary gradation has the advantage that logarithmic gain changes can be achieved simply by shifting a binary number.
  • control device can have a monitoring device for the decision maker and a timer, the output of the decision maker being connected to the control device and the control device monitoring the output of the decision maker for signal changes and, in the absence of a signal change, for one determined by the timer Time initiates a determination of the DC component. This prevents very slow changes in the DC component from not being detected by the arrangement.
  • the decision-maker regardless of a direct component contained in the input signal in addition to an alternating component, provides that a current signal curve of the input signal, preferably the temporal curve of the amplitude of the input signal, is determined, that the lower and upper signal peaks in the signal curve are determined so that the mean value is determined at least one lower and upper signal peak is calculated, that a deviation of the mean value from a predetermined reference value, which reflects the DC component, is calculated and that the deviation is subtractively linked to the input signal. Provision can also be made to continuously set the switching point without special external influences or signals triggering an adjustment process.
  • the instantaneous signal curve of the input signal is determined, at least the lower and upper signal peaks in the signal curve are determined, the mean value is calculated from the signal peaks, the deviation of the mean value is calculated from a predetermined reference value, the deviation is compared to a tolerance threshold value and the deviation is subtractively linked to the input signal when the tolerance threshold is exceeded.
  • the current signal curve of the input signal can be determined, at least the lower and upper signal peaks in the signal curve can be determined, the mean value can be calculated from these signal peaks, the deviation of the mean value from a predetermined reference value can be calculated, the deviation can be compared with zero and in the event of a deviation greater than zero, a certain constant value is subtractively linked to the input signal and, in the case of a deviation less than zero, are linked additively to the input signal. This ensures that the switching point is only changed in fixed steps.
  • the instantaneous signal curve of the input signal can also be determined, at least one lower and upper signal peak can be determined in the signal curve, the mean value can be calculated from these signal peaks, the deviation of the mean value can be calculated from a predetermined reference value, the deviation can be compared with zero , the deviation of their size is assigned to one of three areas for large, medium and small deviations and depending on which area the deviation is assigned was assigned, either the deviation, a constant value or nothing is subtractively linked.
  • the instantaneous signal curve of the input signal can be continuously determined, at least one lower and upper signal peak can be determined in the respective signal curve, the mean value can be calculated from these signal peaks, the deviation of the mean value from a predetermined reference value can be calculated, the deviation with zero are compared, the deviation is compared with a large and a small threshold value and the input signal remains unchanged when the value falls below the small threshold value, a constant value is continuously added to the input signal when the small threshold value is exceeded if the deviation is less than zero or linked subtractively if the deviation is greater than zero, and if the large threshold value is exceeded, the deviation is continuously subtractively linked to the input signal until the value falls below the small threshold value again.
  • the output signal of the decision maker can be monitored for signal changes and, if there is no signal change for a certain time, a new determination of the direct component can be initiated. This can prevent a slowly changing DC component from not being recognized.
  • the decision-maker output can be blocked during the setting process. Furthermore, it can be provided that relative extremas in the signal curve are only accepted as peak values if the signal curve on the extremas changes by a certain value. This prevents, for example smaller relative extremes caused by disturbances than
  • first signal peaks are not evaluated and only the subsequent signal peak (s) is / are evaluated. This measure also increases interference immunity.
  • the signal curve can be amplified before determining the signal peaks in such a way that a high amplification is initially provided and, if the amplification is overdriven, none is reduced Override is present.
  • the signal amplitude is determined and compared with an amplitude threshold value and that the signal is amplified at a higher amplification if the signal amplitude falls below a certain value.
  • the correction with a weighted average is particularly useful for encoder wheels with an asymmetrical course of the output signal (input of the decision maker). The invention is based on the in the figures of the
  • FIG. 1 shows the circuit diagram of an embodiment of a circuit arrangement according to the invention and
  • FIG. 2 shows the signal flow chart for a first embodiment of a method according to the invention.
  • FIG. 3 shows a flow chart for a second embodiment of a method according to the invention and
  • Figure 4 is a flow chart for a third embodiment of a method according to the invention.
  • the speed of a gear wheel 1 is detected by means of a Hall sensor 2, then amplified by means of an amplifier 3 and then converted with the aid of a comparator 4 into a pulse train, the frequency of which corresponds to the speed of the number wheel 1.
  • the pulse train can be removed at an output 5, which is connected to the output of the comparator 4.
  • DC magnetic fields and / or offset voltages acting on the sensor 2 in the amplifier 3 can lead to an alternating signal caused by the movement of the gear wheel 1 in the Hall sensor 2 being superimposed by a DC signal, which leads to the switching points changing of the comparator 4 shift and thus the pulse train at the output 5 receives a different duty cycle.
  • the direct component should now be eliminated in such a way that a correction signal determined in a special way in the comparator 4, which acts as a decision maker, with the output signal of the amplifier 3. is tractively linked. This can be done, for example, by correspondingly changing the switching threshold of the comparator 4 or - as shown in the exemplary embodiment according to FIG. 1 - by subtracting the correction signal from the output signal of the amplifier 3 by means of a subtractor 6 connected between the amplifier 3 and the comparator 4.
  • the correction signal is generated by means of a digital control device 7, to which the output signal of the subtractor 6 is fed with the interposition of a digitally controlled analog amplifier 8 and an analog-digital converter 9.
  • the analog-to-digital converter 9 works according to the tracking principle in the exemplary embodiment. For this purpose, it has a subtractor 10, one input of which is connected to the output of the amplifier 8. The output of the subtractor 10 is coupled to an input of a comparator 12, the other input of which is connected to the reference potential 11. The output of the comparator 12 is connected to the control input of a counter 13, as a result of which the counting direction of the counter 13 is controlled. The counter 13 is also connected to a clock source 14.
  • the count result can be taken off at an output of the counter 13 and is supplied as a binary word to a digital-to-analog converter 15, which generates a corresponding analog signal therefrom.
  • This analog signal is passed to the subtractor 10, where it is subtracted from the output signal of the controllable amplifier 8.
  • the sub-emitter 10, the comparator 12, the counter 13, the clock generator 14 and the digital-to-analog converter 15 form an analog-to-digital converter 9 which works according to the tracking principle.
  • the binary word at the output of the counter 13 always follows the output signal of the amplifier 8, in which the comparator 12 depends on whether the analog signal resulting from the binary word at the output of the counter 13 by the digital-to-analog converter 15 is larger or is smaller than the signal at the output of the amplifier 8, the counting direction of the counter 13 changes and thus the binary word tracks the signal at the output of the amplifier 8.
  • the binary word at the output of the counter 13 is also fed to two peak value detectors 16 and 17, one 16 of which determines the relative minima and the other 17 the relative maxima.
  • the lower and upper signal peaks determined by means of the relative minima and maxima are passed on to a computing unit for calculating the mean value, which, for example, forms the zero position of the
  • Input signal determined. This zero position is compared with a reference value by a subtractor 19, which is connected downstream of the computing unit 18.
  • the reference value is provided by a reference unit 20, which is also connected to the subtractor 19.
  • the reference value is changed by a reference control unit 21, which is connected upstream of the reference unit 20 and downstream of the subtractor 19, in such a way that the reference value is changed when the amount of the value of the computing unit for the mean value lies outside a certain predetermined range.
  • the output of the subtractor 19 is also routed to a control unit 22 which, depending on the output signal at the subtractor 19, generates a control signal for the digital-to-analog converter 23 connected downstream of it.
  • the control unit 22 generates a digital correction value, which is converted into an analog correction signal by the digital-to-analog converter 23. This is then subtracted from the output signal of the amplifier 3 by means of the subtractor 6.
  • the control device 7 also contains a control unit 24 which is connected on the output side to the control input of the controllable amplifier 8 and on the input side to the output of the counter 13.
  • the control unit 24 can for example contain a shift register, the content of which is formed by the binary word at the output of the counter 13 and is controlled by this, so that overall a logarithmization of the binary word at the output of the counter 13 results.
  • control device 7 All functions of the control device 7 are controlled by a sequence control 25.
  • the sequence control 25 is also connected to a timer 26 and a monitoring device 27.
  • the monitoring device 27 is connected on the input side to the output of the comparator 4 in order to monitor the output 5 to determine whether a signal change has occurred within a specific period of time specified by the timer 26. If no change is found for this period, a new measurement of the direct component in the output signal of the amplifier 3 is carried out.
  • the gain for example of a measurement signal to be evaluated, is first regulated in the gain.
  • the highest gain is initially assumed and, in the event of overdrive, is regulated back until overdrive no longer occurs.
  • the gain can be increased in the gain control in the event that the measurement signal falls below a certain value.
  • the instantaneous signal curve over a certain time window is then determined from the correspondingly amplified measurement signal, and the relative extremes are then determined from this signal curve.
  • the upper and lower signal peaks are then determined from the relative extremas, for example by ignoring the first relative extremes and only using the second and continuous extremes for the evaluation.
  • the mean value i.e. H. the value that lies exactly in the middle between the lower and upper tip is determined.
  • the averaging can also be carried out, for example, by forming the arith eti mean by adding the amplitude of the lower and upper signal peaks and dividing the resulting sum by 2.
  • the deviation between the mean value and a predetermined reference value is then determined, for example, by subtraction. If the deviation is greater than a tolerance threshold value, the deviation is then subtracted from the input signal.
  • the reference signal can also be tracked, whereby this can be made dependent, for example, on whether the deviation lies outside a certain predetermined range. If the deviation is not greater than the tolerance threshold value, the reference signal is neither tracked nor is the deviation subtracted from the input signal.
  • the steps shown above are carried out continuously or at certain times.
  • the decision-maker output is monitored for signal changes. This prevents, for example, the deviation from being erroneously large enough that the input signal assumes extreme values despite the subtraction of the deviation. As a result, the decision maker would be “clamped” in this direction and the output signal of the decision maker would no longer change despite the changing measurement signal.
  • the instantaneous signal curve is first determined, the upper and lower signal peaks are then determined therefrom and the mean value is then calculated from the lower and upper signal peaks. The difference between the center and reference values is then determined by subtracting the center value from the reference value. The deviation is then assigned to one of three areas.
  • One area includes small deviations
  • a second area includes medium deviations
  • the third area finally includes larger deviations.
  • a correction value is set to 0. If the deviation does not fall within this range, it is checked whether it falls within the range with medium deviations. If this is not the case, the correction value is set equal to the deviation. If, on the other hand, it is checked whether the deviation is positive, ie whether the deviation is greater than 0. If it is greater than 0, the correction value is set equal to a positive constant and if the deviation is less than or equal to 0, then the correction value is set equal to a negative constant. Finally, the correction value set in this way is then subtracted from the input signal.
  • the individual steps can be processed continuously or one after the other, with the latter starting again after the subtraction of the correction value from the input signal with the determination of the current signal curve.
  • the instantaneous signal curve is first determined again, then the upper and lower signal peaks are determined, and the mean value from lower and upper signal peaks calculated and then subtracted the center value from the reference value for the purpose of calculating the deviation from the center and reference value. Then it is checked whether the deviation is greater than a threshold value. If this is the case, a flag is set and a correction value is set equal to the deviation. If, on the other hand, the deviation is less than or equal to the threshold value, the next step is to check whether the deviation is less than a small threshold value. If this is the case, a flag that may have been set is reset and the correction value is set to 0.
  • the correction value is immediately set to the deviation. If the flag is not set, it is checked whether the deviation is positive or negative. This is done by querying whether the deviation is greater than 0. If this is the case, the correction value is set equal to a positive constant. If this is not the case, the correction value is set equal to a negative constant. The positive and negative constants can be the same or different in certain cases. Finally, the correction value set is then subtracted from the input signal. The individual steps are either processed continuously or in turn, with the processing being started again after a certain time or immediately.
  • An essential aspect of the present invention is that the signal path between the sensor and the switching output is kept as simple as possible.
  • a controllable amplifier is preferably provided in a parallel branch, the output of which is led to a comparator input for the purpose of comparison with the output signal of an output of a digital-to-analog converter connected to the other comparator input.
  • the digital-to-analog converter is a logic controlled in a control circuit so that the resultant
  • the tracking analog-digital converter has the advantage that it has a high level of accuracy with little circuit complexity, in particular in that no filters and / or sample-and-hold elements are required. If one assumes a fixed amplification of the controllable amplifier, the result is an analog-to-digital converter with a linear transmission curve. Taking into account a variable gain of the controllable amplifier, an analog-to-digital converter with logarithmic behavior is obtained.
  • controllable amplifier can be controlled by binary words and the individual amplification factors are graduated in binary (1, 2, 4, 8, 16, ). Although this is not necessary, it is very advantageous for further calculations and for the implementation, since changes in gain by a factor of 2 can be mapped and implemented simply by shifting the binary number. Furthermore, the controllable amplifier is designed in such a way that the minimum input signal of interest can still be observed with sufficient accuracy at maximum amplification. Conversely, the maximum input signal (with minimal amplification then) must not overdrive the subsequent circuit parts.
  • the signal generated by the sensor is an alternating signal with any DC component.
  • the DC component can also be significantly larger than the amplitude of the alternating signal itself.
  • the signal supplied by the sensor is digitized with sufficient accuracy by means of the analog-digital converter already described above in connection with the controllable amplifier. It is also assumed that the relationship between the digital-to-analog converter, which is connected upstream of the control device, and the digital-to-analog converter, which is connected downstream of the control device, is known and that the codes can be converted at least approximately into one another. The basic steps listed below are then followed:
  • the system output (for example output of the comparator 4 in FIG. 1) is blocked, then the current signal value is searched for. This is done by having the digital-to-analog converter connected to the control device and the comparator 4 (or the digital-to-analog converter connected to the control device and the comparator connected in front of the control device switched off when initial value of the analog-digital converter connected upstream of the control device from 0 and expediently high amplification of the controllable amplifier) as an analog-digital converter. This can be done as with a tracking analog-to-digital converter or to save time in the form of an analog-to-digital converter with successive approximation.
  • the value which corresponds to the instantaneous signal value is stored in the digital-to-analog converter downstream of the control device.
  • This value is initially regarded as the first DC component of the signal. This ensures that, regardless of the actual DC component, the controllable amplifier can be set to a sufficiently high gain and the signal can thus be well digitized.
  • the digital signal values acquired in this way are analyzed and examined for minima and maxima. Extreme values are only accepted as such if they are sufficiently strong, ie a maximum is only accepted as such if the signal then becomes significantly smaller again. The same applies to minima.
  • This condition prevents a signal from being simulated by noise or other system disturbances.
  • the first extremum is suppressed because it is usually not a real extremum, but only the beginning of the curve at the start of the observation. The process starts with the greatest gain so as not to miss small signals. If the digital-to-analog converter upstream of the control device stops, the amplification is gradually reduced until there are no more overflows. Any extrema already found will be deleted. This process of shifting up the range with simultaneous deletion of the extremes is preferably carried out automatically in all subsequent process steps, if it is necessary. If at least a minimum and at least a maximum have been found, the method step 3 is followed.
  • step 3 will now be repeated or otherwise the next edge will be waited for.
  • the associated comparator is temporarily "disabled” to prevent uncontrolled results. If it is determined in the course of the minimum-maximum determination that the signal amplitude falls below a certain threshold value, the controllable amplifier can also be switched to a more sensitive range the next time the correction value is changed.
  • the switchover criterion is expediently chosen so that there is still a certain safety margin to overflow in the more sensitive area.
  • step 3 By repeating step 3 again, any changes in the DC component can be determined and compensated for. It should be noted that any change in the DC share in step 3 a jump in at the same time
  • Switching threshold means. The following procedural steps can therefore also be used for systems that are sensitive to permanently sudden changes.
  • step 3 is suspended.
  • the correction of the DC component is only resumed when the DC component exceeds an upper limit.
  • the DC component can also be corrected minimally. The DC component is then not corrected by the calculated value but only by the binary value 1 (incremented or decremented).
  • steps 3, 4 and 5 can be combined in such a way that, depending on the size of the DC component, either Step 3 (large DC component), Step 5 (medium DC component) or nothing (small DC component) is carried out.
  • steps 3, 4 and 5 can also be combined in such a way that, after falling below a minimum DC component, the corrections are suspended, step 5 is carried out when a certain threshold is exceeded, and step 3 is carried out when a further threshold is exceeded, until again Exposure threshold is reached.
  • step 1 it can also be provided in systems with a lower cutoff frequency that if no measurement signal is detected for a certain predetermined time (the output signal of the comparator 4 does not change), step 1 is started again. It may not be necessary to reset the controllable amplifier.
  • the purpose of this procedure is that at rough System error controls, the circuit still operates independently. Such gross system disturbances occur, for example, when there is no useful signal, but at the same time there is a strong DC component drift, so that, as a result, a recurring useful signal no longer generates output edges. Overall, this measure thus increases operational safety.

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  • Physics & Mathematics (AREA)
  • Nonlinear Science (AREA)
  • General Physics & Mathematics (AREA)
  • Analogue/Digital Conversion (AREA)
  • Indication And Recording Devices For Special Purposes And Tariff Metering Devices (AREA)
  • Measurement Of Current Or Voltage (AREA)
  • Measurement Of Length, Angles, Or The Like Using Electric Or Magnetic Means (AREA)
  • Transmission And Conversion Of Sensor Element Output (AREA)
  • Electronic Switches (AREA)

Abstract

L'invention concerne un circuit pour étalonner des points de commutation d'un système de décision amorcé par un signal d'entrée analogique, indépendamment d'une composante de courant continu comprise dans le signal d'entrée, en plus d'une composante de courant alternatif. Ce circuit comprend des détecteurs de crêtes pour déterminer les crêtes supérieures et inférieures du signal d'entrée, une unité de référence pilotable pour préparer une valeur de référence, une unité de calcul pour déterminer la valeur moyenne, une unité de comparaison; une unité de régulation pour compenser la composante de courant continu du signal d'entrée et une seconde unité de régulation montée à la suite de l'unité de comparaison côté entrée, et reliée côté sortie à l'unité de référence, la seconde unité de régulation étant destinée à compenser de manière inverse la valeur de référence.
EP99969802A 1998-09-29 1999-09-28 Circuit et procede pour ajuster des points de commutation d'un systeme de decision Withdrawn EP1116076A2 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
DE19844663 1998-09-29
DE19844663A DE19844663C2 (de) 1998-09-29 1998-09-29 Schaltungsanordnung und Verfahren zum Einstellen von Schaltpunkten eines Entscheiders
PCT/DE1999/003118 WO2000019282A2 (fr) 1998-09-29 1999-09-28 Circuit et procede pour ajuster des points de commutation d'un systeme de decision

Publications (1)

Publication Number Publication Date
EP1116076A2 true EP1116076A2 (fr) 2001-07-18

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Application Number Title Priority Date Filing Date
EP99969802A Withdrawn EP1116076A2 (fr) 1998-09-29 1999-09-28 Circuit et procede pour ajuster des points de commutation d'un systeme de decision

Country Status (6)

Country Link
US (1) US6462683B2 (fr)
EP (1) EP1116076A2 (fr)
JP (1) JP3638520B2 (fr)
KR (1) KR20010079956A (fr)
DE (1) DE19844663C2 (fr)
WO (1) WO2000019282A2 (fr)

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EP1288554A1 (fr) 2001-08-28 2003-03-05 Polypress Rohrsysteme GmbH Dispositif de connexion pour un tube

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DE10129945B4 (de) * 2000-08-02 2008-11-13 Continental Automotive Gmbh Verfahren und Anordnung zur Datenübertragung in einem Kraftfahrzeug
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US20010043151A1 (en) 2001-11-22
DE19844663C2 (de) 2000-09-21
US6462683B2 (en) 2002-10-08
WO2000019282A3 (fr) 2000-06-08
KR20010079956A (ko) 2001-08-22
WO2000019282A2 (fr) 2000-04-06
JP2002526747A (ja) 2002-08-20
DE19844663A1 (de) 2000-04-06
JP3638520B2 (ja) 2005-04-13

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