EP0521742A1 - Elektronische Verzögerungseinrichtung - Google Patents

Elektronische Verzögerungseinrichtung Download PDF

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Publication number
EP0521742A1
EP0521742A1 EP19920401498 EP92401498A EP0521742A1 EP 0521742 A1 EP0521742 A1 EP 0521742A1 EP 19920401498 EP19920401498 EP 19920401498 EP 92401498 A EP92401498 A EP 92401498A EP 0521742 A1 EP0521742 A1 EP 0521742A1
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EP
European Patent Office
Prior art keywords
signal
resonator
input
circuit
resonator filters
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP19920401498
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English (en)
French (fr)
Inventor
Yves Besson
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Thales SA
Original Assignee
Thomson CSF SA
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Filing date
Publication date
Application filed by Thomson CSF SA filed Critical Thomson CSF SA
Publication of EP0521742A1 publication Critical patent/EP0521742A1/de
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    • G—PHYSICS
    • G04—HOROLOGY
    • G04F—TIME-INTERVAL MEASURING
    • G04F10/00—Apparatus for measuring unknown time intervals by electric means
    • G04F10/06—Apparatus for measuring unknown time intervals by electric means by measuring phase

Definitions

  • the present invention relates to the measurement of small delays or arrival time differences between a signal edge and a reference instant preferentially defined by another signal edge.
  • the measurement of such delays is generally carried out by processing information entered by direct sampling on the edge of the incident signal or on the edges of the incident signals. It presents serious difficulties when it is desired to detect time differences of the order of a few nanoseconds or even a nanosecond and when the front or fronts of the incident signals are brief and liable to local deformation causing errors.
  • the object of the present invention is to enable the measurement of very short delay on one or more signal edges by overcoming a certain number of faults linked to the direct temporal exploitation of the signal edges.
  • Each resonator filter with cosine response has advantageously an oscillating circuit excited by an amplifier stage input with low output impedance behaving as a voltage source.
  • Each resonator filter with a sinusoidal response advantageously consists of a parallel oscillating circuit excited by means of an input amplifier stage with high output impedance acting as a current source.
  • FIG. 1 represents a circuit for measuring the delay of a reference instant relative to a rising signal edge.
  • This circuit comprises at the input a processing path for the rising edge of the signal formed by a limiting amplifier 10 followed by a circuit for suppressing the falling edges with diode series 11 and parallel capacitance 12, and two resonator filters 13, 14 arranged in parallel.
  • the outputs of these filters lead to a computer 15 by means of two sampling switches 16, 17 controlled by a sampling control circuit 18 triggered, by means of a possible delay circuit 19, by a input signal such as a calibrated pulse identifying the reference instant.
  • the limiting amplifier 10 makes it possible to overcome amplitude deviations which may affect the rising edge of the signal.
  • the circuit for suppressing falling edges with diode series 11 and parallel capacitance 12 which attacks the inputs of the resonator filters 13 and 14 prevents a falling signal edge from disturbing the resonator filters 13, 14.
  • the resonator filters 13, 14 are tuned to the same frequency Fr, the period T of which is at least equal to the maximum duration of the delay to be measured.
  • one 13 In response to a rising signal edge, one 13 generates a response V1 of cosine shape and the other 14 a response V2 of sinusoidal shape.
  • These responses V1 and V2 which are two sinusoidal signals of the same amplitude and the same frequency triggered in quadrature can be considered as the real and imaginary components of a complex vector of modulus substantially constant if the overvoltage coefficient is sufficiently high whose phase evolves linearly over time since the moment of excitation.
  • sampling switches 16, 17 are closed for a short period of time at the reference instant in order to deliver to the computer 15 the sampled values V1r and V2r from which it deduces, by implementing the preceding formulas, the value of the delay ⁇ T of the reference instant on the rising signal edge.
  • the delay circuit 19 which is possibly arranged in front of the sampling control circuit on the path of the input signal identifying the reference time is used in the case where the reference time can be ahead of the rising edge of the signal.
  • the input signal is delayed by a sufficient value ⁇ Tr so that it is always late with respect to the rising signal edge and this value ⁇ Tr is subtracted from the calculated value ⁇ T.
  • a reset device discharging the energy from the resonator filters and the elongation capacitor 12 to authorize a new measurement. This avoids having to wait for the natural discharge of the energies of the resonator filters and of the extension capacitor.
  • FIG. 2 illustrates a possible embodiment of the resonator filter 13 generating a signal of cosine shape in response to a rising signal edge.
  • This comprises an input amplifier stage 20 with high input impedance and low output impedance behaving as a voltage source, followed by an oscillating circuit and by an output amplifier stage 21 with high impedance Entrance.
  • the oscillating circuit is produced on the one hand using an inductor 22 connected between the input of the output amplifier stage 21 and ground, and on the other hand using a resistor 23 in series with a capacitor 24 arranged in order between the output terminal of the input amplifier stage 20 and the input terminal of the output amplifier stage 21.
  • inductance 22 For an oscillation period of 100 ns, one can for example choose for inductance 22 a value of 25 ⁇ H, for resistor 23 a value of 15 ⁇ and for capacitor 24 a value of 10 pf. This gives an overvoltage coefficient of 100 and a resonance frequency equal to 10 MHz.
  • FIG. 3 illustrates a possible embodiment of the resonator filter 14 generating a signal of sinusoidal shape in response to a rising signal edge.
  • This comprises an input amplifier stage 30 with high input and output impedance behaving as a current source, followed by an oscillating circuit and an output amplifier 31 with high input impedance.
  • the oscillating circuit is produced using an inductor 32, a resistor 33 and a capacitor 34 connected in parallel between the ground and the input terminal of the output amplifier 31 which is itself connected to the output terminal of the input amplifier stage 30.
  • the inductance 32 For an oscillation period of 100 ns previously chosen, one can for example give the inductance 32 a value of 25 ⁇ H, the resistor 33 a value of 1.5 105 ⁇ and the capacitor 34 a value of 10 pf. This gives an overvoltage coefficient of 100 and a resonance frequency equal to 10 MHz.
  • the two resonator filters 13, 14 are dual from one another in a voltage / current duality.
  • FIG. 4 illustrates the form of the responses of the resonator filters 13, 14 at an excitation step.
  • the curve “a” represents the shape of the excitation step assumed to be applied simultaneously to the inputs of the resonator filters 13, 14 ,.
  • the curve “b” represents the cosine shape of the response of the resonator filter 13 tuned to the frequency 1 / T.
  • the curve “c” represents the sinusoidal shape of the response of the resonator filter 14 tuned to the frequency 1 / T.
  • these responses are two sinusoidal signals of the same amplitude and the same frequency triggered in quadrature which can be considered as the real and imaginary components of a complex vector of substantially constant modulus whose phase evolves linearly over time since the moment of excitation at speed 2 ⁇ ′ / T. Thanks to its linear evolution over time, this phase can be used for the measurement of the delay separating the excitation instant of the resonator filters from the sampling instant of their responses.
  • FIG. 5 represents a circuit for measuring the delay existing between two rising edges of signals S1, S2.
  • This circuit comprises at the input two parallel processing channels of the rising edges of the signals S1 and S2 of identical composition which each comprise an input limiting amplifier 40, 50 followed by a circuit for suppressing the falling edges with diode series 41, 51 and parallel capacity 42, 52, and two resonator filters 43, 44; 53, 54 arranged in parallel.
  • the outputs of the four resonator filters 43, 44, 53, 54 of the two input channels lead to a computer 60 by means of sampling switches 45, 46, 55, 56 controlled by a sampling control circuit 61 itself triggered by a circuit for detecting the passage of the fronts 62 having two inputs connected at the output of the limiting amplifiers 40, 50.
  • the limiting amplifier 40, 50 makes it possible to overcome amplitude differences which can affect a rising edge of the signal.
  • the circuit for suppressing falling edges with series diode 41, 51 and parallel capacitance 42, 52 prevents disturbance of the resonator filters 43, 44, 53, 54 by a falling signal edge.
  • All the resonator filters 43, 44, 53, 54 of the two input channels are tuned to the same frequency, the period T ′ of which is at least equal to the maximum duration of the delay to be measured between the two edges and preferably equal at this maximum duration increased by the operating delay of the edge passage detection circuit 62.
  • the resonator filters 43 and 53 are identical and generate, in response to a rising signal edge, an output signal V′1, V′3 cosine shape.
  • the resonator filters 44 and 54 are identical and generate, in response to a rising signal edge, an output signal V′2, V′4 of sinusoidal shape.
  • the responses V′1 and V′2 of the resonator filters 43, 44 of the input channel receiving the signal S1 are two sinusoidal signals of the same amplitude and the same frequency, triggered in quadrature, which can be considered as the real and imaginary components of a first complex vector of substantially constant module whose phase ⁇ ′1 evolves linearly over time since the moment of excitation by the rising edge of the signal S1.
  • the measurement instant is determined by the edge passage detection circuit 62 which does not need to be very precise since the phase difference between the two complex vectors whose components are delivered by the resonator filters remains practically constant on the response time of the resonator filters.
  • This circuit can be constituted for example by two flip-flops triggered by the signal fronts and followed by a logic arrangement of the door type of type "and".
  • the devices which have just been described are applicable to various fields where the wave fronts can be of various origins: electromagnetic, acoustic, light, ...
  • An example of application is unambiguous goniometry by time of arrival of pulses from radar or sonar transmitters using omnidirectional antennas spaced apart by a suitable distance according to a known arrangement.
  • Other applications relate to angular tracking by deviation measurement, telemetry and short distance altimetry.

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  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Measurement Of Resistance Or Impedance (AREA)
  • Networks Using Active Elements (AREA)
EP19920401498 1991-06-18 1992-06-02 Elektronische Verzögerungseinrichtung Withdrawn EP0521742A1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FR9107423 1991-06-18
FR9107423A FR2678071B1 (fr) 1991-06-18 1991-06-18 Dispositif electronique de mesure de retards.

Publications (1)

Publication Number Publication Date
EP0521742A1 true EP0521742A1 (de) 1993-01-07

Family

ID=9413949

Family Applications (1)

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EP19920401498 Withdrawn EP0521742A1 (de) 1991-06-18 1992-06-02 Elektronische Verzögerungseinrichtung

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US (1) US5218289A (de)
EP (1) EP0521742A1 (de)
FR (1) FR2678071B1 (de)

Families Citing this family (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6919727B2 (en) * 2002-09-26 2005-07-19 Texas Instruments Incorporated Accurate time measurement system circuit and method
WO2004104603A1 (ja) * 2003-05-23 2004-12-02 Advantest Corporation 位相測定装置、方法、プログラムおよび記録媒体
WO2004107560A1 (en) * 2003-05-27 2004-12-09 Philips Intellectual Property & Standards Gmbh Phase detector and method of phase detection
WO2005073738A1 (ja) * 2004-01-30 2005-08-11 Advantest Corporation 位相測定装置、方法、プログラムおよび記録媒体
JP2006133214A (ja) * 2004-10-04 2006-05-25 Topcon Corp 時間差測定装置および測定方法並びに測距装置および測距方法
JP4878127B2 (ja) * 2005-06-10 2012-02-15 株式会社トプコン 時間差測定装置および距離測定装置並びに距離測定方法
US7378854B2 (en) * 2005-10-28 2008-05-27 Teradyne, Inc. Dual sine-wave time stamp method and apparatus

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0166106A1 (de) * 1981-02-03 1986-01-02 MITEC Mikroelektronik Mikrotechnik Informatik GmbH Empfängerschaltung für ein Entfernungsmessgerät nach dem Prinzip der Lichtimpuls-Laufzeitmessung
EP0197801A2 (de) * 1985-02-01 1986-10-15 Schlumberger Industries Verfahren und Anordnung zur schnellen Phaseneinstellung eines Taktsignals
JPS6263885A (ja) * 1985-08-21 1987-03-20 Yokogawa Electric Corp 時間幅計測装置
JPS6385489A (ja) * 1986-09-30 1988-04-15 Yokogawa Electric Corp 微小時間差計測装置
EP0348898A2 (de) * 1988-06-29 1990-01-03 Kabushiki Kaisha TOPCON Hochauflösendes Zeitdifferenzmessgerät

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3680118A (en) * 1970-07-14 1972-07-25 Myron L Anthony Aircraft navigation receiver apparatus using active filters
IT1021779B (it) * 1974-06-25 1978-02-20 Thomson Csf Procedimento e sistema di controllo automatico di frequenza
FR2296246A1 (fr) * 1974-12-27 1976-07-23 Thomson Csf Circuit memoire analogique et systeme comportant un tel circuit
DE2634627C2 (de) * 1976-07-31 1982-08-19 MITEC Moderne Industrietechnik GmbH, 8012 Ottobrunn Laserentfernungsmeßgerät
FR2383451A1 (fr) * 1977-03-11 1978-10-06 Thomson Csf Circuit a recirculation pour repetition d'un signal analogique impulsionnel, et systeme comportant un tel circuit
US5057910A (en) * 1987-02-20 1991-10-15 Magni Systems, Inc. Method of displaying video signal phase characteristics

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0166106A1 (de) * 1981-02-03 1986-01-02 MITEC Mikroelektronik Mikrotechnik Informatik GmbH Empfängerschaltung für ein Entfernungsmessgerät nach dem Prinzip der Lichtimpuls-Laufzeitmessung
EP0197801A2 (de) * 1985-02-01 1986-10-15 Schlumberger Industries Verfahren und Anordnung zur schnellen Phaseneinstellung eines Taktsignals
JPS6263885A (ja) * 1985-08-21 1987-03-20 Yokogawa Electric Corp 時間幅計測装置
JPS6385489A (ja) * 1986-09-30 1988-04-15 Yokogawa Electric Corp 微小時間差計測装置
EP0348898A2 (de) * 1988-06-29 1990-01-03 Kabushiki Kaisha TOPCON Hochauflösendes Zeitdifferenzmessgerät

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
PATENT ABSTRACTS OF JAPAN vol. 11, no. 260 (P-608)(2707) 22 Août 1987 & JP-A-62 063 885 ( YOKOGAWA ELECTRIC ) 20 Mars 1987 *
PATENT ABSTRACTS OF JAPAN vol. 12, no. 319 (P-751)(3166) 30 Août 1988 & JP-A-63 085 489 ( YOKOGAWA ELECTRIC ) 15 Avril 1988 *

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Publication number Publication date
FR2678071A1 (fr) 1992-12-24
FR2678071B1 (fr) 1994-11-04
US5218289A (en) 1993-06-08

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