EP0415971A1 - Systeme d'alimentation en tension continue a plusieurs sources de tension continue - Google Patents

Systeme d'alimentation en tension continue a plusieurs sources de tension continue

Info

Publication number
EP0415971A1
EP0415971A1 EP89905683A EP89905683A EP0415971A1 EP 0415971 A1 EP0415971 A1 EP 0415971A1 EP 89905683 A EP89905683 A EP 89905683A EP 89905683 A EP89905683 A EP 89905683A EP 0415971 A1 EP0415971 A1 EP 0415971A1
Authority
EP
European Patent Office
Prior art keywords
voltage
output
switching
time
transistors
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
EP89905683A
Other languages
German (de)
English (en)
Inventor
Werner Pollmeier
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Wincor Nixdorf International GmbH
Original Assignee
Wincor Nixdorf International GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Wincor Nixdorf International GmbH filed Critical Wincor Nixdorf International GmbH
Publication of EP0415971A1 publication Critical patent/EP0415971A1/fr
Pending legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J9/00—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting
    • H02J9/04—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source
    • H02J9/06—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source with automatic change-over, e.g. UPS systems
    • G—PHYSICS
    • G06—COMPUTING; CALCULATING OR COUNTING
    • G06F—ELECTRIC DIGITAL DATA PROCESSING
    • G06F1/00—Details not covered by groups G06F3/00 - G06F13/00 and G06F21/00
    • G06F1/26—Power supply means, e.g. regulation thereof
    • G06F1/30—Means for acting in the event of power-supply failure or interruption, e.g. power-supply fluctuations
    • G06F1/305—Means for acting in the event of power-supply failure or interruption, e.g. power-supply fluctuations in the event of power-supply fluctuations
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J9/00—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting
    • H02J9/04—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source
    • H02J9/06—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source with automatic change-over, e.g. UPS systems
    • H02J9/061—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source with automatic change-over, e.g. UPS systems for DC powered loads

Definitions

  • the invention relates to a DC voltage supply system with a plurality of voltage outputs fed from at least two DC voltage sources, one of which is alternatively fed from a first or at least one further DC voltage source, and at least one further is permanently fed from one of the voltage sources.
  • Such a system is required to supply high-quality electronic systems, for example computer systems or security devices. If one voltage source fails, it automatically supplies the affected voltage output from another voltage source, thus ensuring an uninterruptible power supply. In many applications there is another voltage output that is permanently supplied by one of these two voltage sources.
  • the voltage supply of electronic systems can be divided up in such a way that the units sensitive to voltage loss, for example memories, are supplied from the alternatively fed voltage output and the further voltage output takes over the main load of the voltage supply.
  • Known DC voltage supply systems alternatively feed a voltage output from different DC voltage sources, for which purpose there is a coupling element between each voltage source and the voltage output. This coupling element consists of a diode which is operated in the forward direction.
  • the voltage output is then fed from the voltage source that has the higher voltage level.
  • the diodes prevent feeding back into the voltage source with a lower voltage level.
  • Such a voltage supply system has a very simple circuit structure, but has considerable disadvantages. This creates a power loss at the coupling element, the amount of which is proportional to the product of the voltage drop at the coupling element and the forward current.
  • Power supply systems for electronic devices are often designed in such a way that they have a low voltage of, for example, 5 volts at their output, but instead deliver high currents.
  • a diode as a coupling element, a high power loss is generated at this, which must be dissipated to the environment in the form of heat loss via heat sinks. This power loss increases the total power loss of the power supply system and reduces its efficiency.
  • Such voltage supply systems therefore have large housing dimensions and are relatively heavy.
  • Another disadvantage of the known systems is that the voltage levels of the voltage sources for alternatively feeding a voltage output are at least around. must differentiate the amount of forward voltage of a diode to ensure that in normal Operating state of the voltage output is fed from only one voltage source. With alternative food from the other voltage source, the voltage level at the voltage output then inevitably changes. With a typical forward voltage of a diode of approximately 0.7 volts and with an output voltage of 5 volts, the voltage difference at the voltage output can be greater than 10% with alternative supply. The permissible range of voltage fluctuations is thus clearly exceeded for sensitive electronic systems. The same applies to the further voltage output, which is permanently connected to one of the voltage sources that alternatively feed a voltage output. The voltage level of the further voltage output is at least higher than that of the alternatively fed voltage output by the forward voltage of the coupling element. The problems mentioned do not occur if the voltage drop at the coupling element can be reduced.
  • This object is achieved in a voltage supply system of the type mentioned above in that the alternative feeding of a voltage output is caused by control signals which are generated depending on the operating state of the respective DC voltage source and / or externally and the switching state of the respective coupling element designed as a switch arrangement while prolonging the switching time controls , wherein mutually opposite switching operations overlap each other.
  • the invention makes use of the knowledge that a switch arrangement, which can be designed, for example, as a semiconductor component, has a very low forward voltage and a low forward resistance. If such a switch arrangement is used as a coupling element, there is only a small voltage drop across it, even with high currents, and the power loss remains small.
  • the outlay for dissipating the lost heat or for cooling can be reduced, as a result of which the size and the weight of the voltage supply system are reduced.
  • the efficiency of the voltage supply system is increased by using a low-loss coupling element, so that its rated power can increase for a given housing size.
  • the reduction in the voltage drop at the coupling element also has the effect that the voltage levels of different voltage outputs fed from a voltage source are at approximately the same potential.
  • the voltage sources which alternatively feed a voltage output can have the same voltage, because the respective voltage source can be switched on specifically via the switch arrangement and the other voltage sources can be switched off, so that simultaneous feeding of the voltage output from two voltage sources is prevented.
  • the switching state of a switch arrangement is controlled via control signals which are generated as a function of the operating state of the respective voltage source. If, for example, the voltage of a first voltage source begins to drop below a predetermined value, a control signal is generated that the 1 controls the switch arrangement of the voltage source in question in the blocking state and thus switches off the feeding of the corresponding voltage output via this voltage source. At the same time, a second control signal is formed which controls a switch arrangement belonging to another voltage source to the conductive state and thereby ensures the voltage supply of the voltage output. To ensure a seamless power supply to the
  • a steep rise in voltage can result in a surge of current at the affected voltage source, which overloads the voltage source.
  • the extended switching time ensures that the voltage sources are switched on or off smoothly.
  • 25 switching time is meant the transition time from the off to the conducting state and vice versa the 'switch assembly.
  • control signals which are formed depending on the operating state of the respective voltage source
  • these externally e.g. to generate in a higher-level headquarters.
  • the voltage sources can be specifically activated or deactivated and the voltages at the voltage outputs can be switched on or off.
  • This measure makes it possible to control the supply of the further voltage output by means of the switch arrangement belonging to it. In this way, the switching on or switching off of the supply voltage of certain device parts can be initiated in a simple manner from a control center.
  • a further development can consist in that at least one switch arrangement as a series regulator is included in a control device provided at the associated voltage output. This ensures that a regulated voltage is provided at the voltage output.
  • the power transistor normally required for voltage regulation can be omitted if the switch arrangement is integrated into the series regulating branch of a regulating circuit and thereby takes on the task of a regulating transistor.
  • Fig. 2 shows a circuit arrangement for generating control signals
  • FIG. 3 shows the course of control signals and the state of switch arrangements in the switching arrangement according to FIG. 1 over time.
  • FIG. 1 shows a voltage supply system, the voltage output 10 of which can alternatively be supplied by a switched-mode power supply 12 connected to the 220 volt AC network or, in an emergency, from a battery 14.
  • the battery 14 is connected to the emitter of a pnp transistor T1, the collector of which is led to the voltage output 10.
  • the base of the transistor Tl is connected to the collector terminal of an auxiliary transistor TA which is of the conductivity type NPN and whose emitter electrode is connected to ground via a resistor 15.
  • the base electrode is connected to the output of an operational amplifier 16, the inverted input of which is connected to the center tap of a voltage divider consisting of resistors 18, 20, which is connected to voltage output 10.
  • the operational amplifier 16 is connected as an integrator and has a capacitor 22 between its output and its inverting input.
  • a series resistor 26 and a zener diode 24 are connected in series between the voltage output 10 and the reference potential.
  • a cathode connection of the Zener diode 24, a reference voltage 25 is tapped and fed to a voltage divider consisting of the series connection of a resistor 28, a resistor 30 and a capacitor 32.
  • the capacitor 32 is connected to the non-inverting input of the operational amplifier 16.
  • a control signal S1 is fed to the connection point of the resistors 28, 30.
  • the voltage tap of the switching power supply 12 is led out at a terminal 34, which is connected directly to a further voltage output 36 of the voltage supply system.
  • One of a first MOS transistor T2 is located between voltage output 10 and terminal 34 and a second MOS transistor T3 existing switch arrangement.
  • the gate connections of the transistors T2, T3 are routed together to the output of an operational amplifier 38.
  • the source connections of the transistors T2, T3 are connected directly to one another.
  • Transistor T2 is connected to terminal 34 and the drain connection of transistor T3 to voltage output 10.
  • the MOS transistors T2, T3 are normally-off n-channel field effect transistors and can only block in the drain-source direction. In the opposite direction, these transistors are conductive via their so-called inverse diode.
  • the inverse diodes 40 and 42 belonging to the transistors T2, T3 are shown in dashed lines in FIG. 1 between the respective drain-source connections. By interconnecting the transistors T2, T3 at their source connections, one of the transistors T2, T3 is operated inversely, in the example according to FIG. 1 the transistor T3.
  • the output of the operational amplifier 38 connected as an integrator is connected to its inverting input via a capacitor 44. This is connected to the center tap of the voltage divider consisting of resistors 46, 48, which is fed via the voltage output 10.
  • the non-inverting input of operational amplifier 38 is connected to a capacitor 50 which is connected to ground.
  • the encoder 50 is connected to the cathode connection of the Zener diode 24 via the series ends 52, 54.
  • a second control signal S2 is supplied at the connection point of the resistors 52, 54.
  • the control signals S1, S2 are generated by a controller 56, which monitors the voltage level of the switched-mode power supply 12 or processes control signals from a higher-level control center (not shown). The circuit arrangement of such a controller 56 is shown in FIG. 2.
  • a threshold value switch 58 is supplied with a reference voltage 60 at its inverting input and a voltage signal Im proportional to the line voltage of the switching power supply 12 at its non-inverting input.
  • the threshold switch 58 produces at its output an output signal Sw with a high level if the level of the voltage signal Un is higher than the reference voltage 60, otherwise an output signal Sw with a low level.
  • the output of the threshold switch 58 is connected to a timer 62 which delays the falling edge of the output signal S by a time t1 and to a timer 64 which delays the rise of the output signal Sw by the time t3. This is followed by an inverter 66 with an open collector output.
  • a further timer 68 is connected downstream of the timer 62, which delays the rising edge of the output Sw by a time t2.
  • the timer 68 controls a gate 70, which also has an open collector output and generates the control signal S2.
  • the voltage signal Un can fluctuate between a nominal value, which is indicated as 100%, and the value 0.
  • the output signal Sw of the threshold switch 58 can assume the states L (low level) and H (high level) as described.
  • the control signals S1, S2 also have two states, which are designated with logic 0 and logic 1. In the logic 0 state, the control signals S1, S2 are at ground potential, in the logic 1 state they are in a high-resistance state.
  • the transistors T1, T2 have the states “blocking” and “conducting”, which are labeled "off” and "on” in FIG. 3.
  • the transistors T1, T2 are switched back and forth between these states in a predetermined switching time, so that the voltage rise or the voltage drop at the output of the transistors T1, T2 is flat.
  • control signal S1 carries ground potential
  • the voltage at the non-inverting input of the operational amplifier 16 in FIG. 1 is approximately zero.
  • the training output voltage of the operational amplifier 16 is therefore equal to zero, and the transistors T4 and Tl block.
  • the high-resistance control signal S2 does not load the voltage divider consisting of resistors 54, 52.
  • the reference voltage 25 of the Zener diode 24 is thus supplied to the non-inverting input of the operational amplifier 38.
  • the operational amplifier 38 forms a control loop together with the transistors T2, T3. In this, the operational amplifier 38 works as a PI controller and the transistors T2, T3 as actuators.
  • the actual value is fed to the inverting input of the operational amplifier 38, and the setpoint is fed to its non-inverting input.
  • the operational amplifier 38 carries out the target / actual comparison and sets a voltage at its output such that the transistors T2, T3 are controlled in a conductive manner via their gate electrode and the target / actual value deviation is minimal.
  • the time behavior of the control loop is set by the time constant resulting from the resistors 46, 48 and the capacitor 44.
  • the threshold switch 58 in FIG. 2 switches its output signal Sw to low level, and the inverter 66 generates the control signal S1 with the logic 1 state at its output.
  • the falling edge of the output signal Sw of the threshold switch 58 is caused by the Timer 62 delays by a time tl and switches control signal S2 to logic 0 via gate 70.
  • the capacitor 32 in FIG. 1 is charged to the reference voltage 25 via the resistors 28, 30 connected in series.
  • the operational amplifier 16 operating as a controller controls the transistor T4, which supplies the transistor Tl with base current, so that the latter is switched on.
  • the switching time of the transistor T1 is determined by the time constant of the operational amplifier 16, which results from its connection to the resistors 18, 20 and the capacitor 22, and by the time constant from the resistors 28, 30 and the capacitor 32.
  • the voltage output by the transistor T1 is fed to the operational amplifier 16 via the voltage divider, consisting of the resistors 18, 20, compared with the voltage level of the zener diode 24 and regulated to a constant value.
  • control signal S2 leads to ground potential after the time t1, ie the capacitor 50 is discharged with a time constant formed by the resistor 52 and the capacitor 50.
  • the operational amplifier 38 operating as a controller thus receives a setpoint voltage going to zero and controls the MOS transistors T2, T3 in the blocking state. Since the MOS transistors T2, T3 on their source electrodes are connected, one of the inverse diodes 40, 42 is switched in the reverse direction, so that there is no feedback of the switching power supply 12.
  • the described opposite switching operations i.e. the switching on of the transistor T1 or the switching off of the transistors T2, T3 are set via the time constants mentioned in such a way that they overlap by a time t4, as shown in FIG. 3.
  • the voltage output 10 maintains its voltage level unchanged during these switching operations.
  • the operating state of the voltage return of the switched-mode power supply 12 is dealt with below, which is shown in FIG. 3 under c.
  • the voltage signal Un rises and exceeds the reference voltage 60 at the threshold value 72.
  • the threshold value 58 in FIG. 2 switches its output signal Sw from low level to high level.
  • the control signal S1 is controlled into the logic 0 state by the inverter 66, while the control signal S2 is switched to a high-resistance state after the time t2.
  • the time 12 is set so that the switching power supply l2 has reached its full operating voltage before this time has expired.
  • the control signal S2 now no longer loads the voltage divider consisting of the resistors 52, 54 and the capacitor 50, and the capacitor 50 is charged to the voltage 25 of the Zener diode 25 via the resistors 52, 54.
  • the operational amplifier 38 controls the transistors T2, T3 in accordance with the rising charging voltage on the capacitor 50 in the conductive state and the switching power supply 12 supplies the voltage output 10 with voltage.
  • the control signal S1 which has approximately ground potential, causes the capacitor 32 to discharge via the resistor 30.
  • the transistor T1 is consequently switched into the blocking state via the transistor T4 and the operational amplifier 16 and the battery 14 is decoupled from the voltage output 10.
  • the switching processes for switching transistors T2, T3 and Tl on and off are also overlapping, ie the time constants are chosen such that an overlap time t5 occurs, Q, in which the transistors T1, T2, T3 are controlled to be conductive. as shown in Fig. 3.
  • the switching times of the transistors T1, T2, T3 are each to be set such that they are longer than the settling time of the switching power supply 12. This ensures that the switching power supply 12 is not overloaded by dynamic control processes when correcting faults.
  • the voltage of the Zener diode 24, which serves as the setpoint voltage for regulating the output voltage at the voltage output 10, is tapped off at the voltage output 10 via the series resistor 26. A brief voltage drop at the voltage output 10 thus also causes the voltage at the zener diode 24 to drop, as a result of which the transistors T1, T2, T3 are regulated to a lower output voltage. 5 This means that the voltage supply system works reliably even in the event of a brief overload.
  • Fig. 1 The embodiment shown in Fig. 1 can be supplemented by various circuit measures. It is thus possible to insert further transistors, which work as a switch arrangement, between the voltage output 36 and the terminal 34.
  • the voltage output 36 can be connected or disconnected to the output voltage of the switching power supply 12 via control signals which control these transistors. Furthermore, it is also possible to connect a plurality of transistors in parallel in order to divide the current and thus reduce the power loss occurring at a transistor and the voltage drop.

Landscapes

  • Engineering & Computer Science (AREA)
  • Theoretical Computer Science (AREA)
  • Business, Economics & Management (AREA)
  • Emergency Management (AREA)
  • Power Engineering (AREA)
  • General Engineering & Computer Science (AREA)
  • General Physics & Mathematics (AREA)
  • Physics & Mathematics (AREA)
  • Direct Current Feeding And Distribution (AREA)
  • Electronic Switches (AREA)
  • Dc-Dc Converters (AREA)
  • Stand-By Power Supply Arrangements (AREA)
  • Continuous-Control Power Sources That Use Transistors (AREA)
  • Control Of Voltage And Current In General (AREA)
  • Oscillators With Electromechanical Resonators (AREA)
  • Input Circuits Of Receivers And Coupling Of Receivers And Audio Equipment (AREA)

Abstract

Un système d'alimentation en tension à plusieurs sorties de tension (10, 36) est alimenté par au moins deux sources de tension (12, 14). Une sortie de tension (10) peut être alimentée en alternance par une première source de tension (12) ou par une autre source de tension (14), au moins une autre sortie de tension (36) étant en permanence alimentée par l'une de ces sources de tension. L'alimentation en alternance de la sortie de tension (10) s'effectue au moyen de signaux de commande (S1, S2) qui commandent l'état de commutation d'agencements commutateurs (T1, T2, T3) tout en allongeant les temps de commutation. Ce faisant, des processus de commutation en sens inverse se chevauchent. Par suite de ces dispositions, la perte de puissance au niveau des agencements commutateurs (T1, T2, T3) est réduite, et des niveaux de tension largement compatibles sont produits au niveau des sorties de tension (10, 36).
EP89905683A 1988-05-18 1989-05-18 Systeme d'alimentation en tension continue a plusieurs sources de tension continue Pending EP0415971A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE3816944 1988-05-18
DE3816944A DE3816944A1 (de) 1988-05-18 1988-05-18 Spannungsversorgungssystem mit mehreren spannungsquellen

Publications (1)

Publication Number Publication Date
EP0415971A1 true EP0415971A1 (fr) 1991-03-13

Family

ID=6354633

Family Applications (2)

Application Number Title Priority Date Filing Date
EP89905683A Pending EP0415971A1 (fr) 1988-05-18 1989-05-18 Systeme d'alimentation en tension continue a plusieurs sources de tension continue
EP89109035A Expired - Lifetime EP0342693B1 (fr) 1988-05-18 1989-05-18 Système d'alimentation en courant continu avec plusieurs sources de courant continu

Family Applications After (1)

Application Number Title Priority Date Filing Date
EP89109035A Expired - Lifetime EP0342693B1 (fr) 1988-05-18 1989-05-18 Système d'alimentation en courant continu avec plusieurs sources de courant continu

Country Status (8)

Country Link
US (1) US5278453A (fr)
EP (2) EP0415971A1 (fr)
JP (1) JPH03503236A (fr)
KR (1) KR930002934B1 (fr)
AT (1) ATE96583T1 (fr)
DE (2) DE3816944A1 (fr)
ES (1) ES2046369T3 (fr)
WO (1) WO1989011749A1 (fr)

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Also Published As

Publication number Publication date
ATE96583T1 (de) 1993-11-15
DE58905996D1 (de) 1993-12-02
US5278453A (en) 1994-01-11
DE3816944C2 (fr) 1991-11-28
KR930002934B1 (ko) 1993-04-15
DE3816944A1 (de) 1989-11-30
JPH03503236A (ja) 1991-07-18
KR900702618A (ko) 1990-12-07
EP0342693A1 (fr) 1989-11-23
ES2046369T3 (es) 1994-02-01
WO1989011749A1 (fr) 1989-11-30
EP0342693B1 (fr) 1993-10-27

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