CN111343112A - 从多点通信信道接收数据的方法和装置 - Google Patents

从多点通信信道接收数据的方法和装置 Download PDF

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CN111343112A
CN111343112A CN202010140487.9A CN202010140487A CN111343112A CN 111343112 A CN111343112 A CN 111343112A CN 202010140487 A CN202010140487 A CN 202010140487A CN 111343112 A CN111343112 A CN 111343112A
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阿里·霍马提
阿明·肖克罗拉
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0264—Arrangements for coupling to transmission lines
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/38—Synchronous or start-stop systems, e.g. for Baudot code
    • H04L25/40—Transmitting circuits; Receiving circuits
    • H04L25/49—Transmitting circuits; Receiving circuits using code conversion at the transmitter; using predistortion; using insertion of idle bits for obtaining a desired frequency spectrum; using three or more amplitude levels ; Baseband coding techniques specific to data transmission systems
    • H04L25/4906—Transmitting circuits; Receiving circuits using code conversion at the transmitter; using predistortion; using insertion of idle bits for obtaining a desired frequency spectrum; using three or more amplitude levels ; Baseband coding techniques specific to data transmission systems using binary codes
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    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/38—Synchronous or start-stop systems, e.g. for Baudot code
    • H04L25/40—Transmitting circuits; Receiving circuits
    • H04L25/49—Transmitting circuits; Receiving circuits using code conversion at the transmitter; using predistortion; using insertion of idle bits for obtaining a desired frequency spectrum; using three or more amplitude levels ; Baseband coding techniques specific to data transmission systems
    • H04L25/4917—Transmitting circuits; Receiving circuits using code conversion at the transmitter; using predistortion; using insertion of idle bits for obtaining a desired frequency spectrum; using three or more amplitude levels ; Baseband coding techniques specific to data transmission systems using multilevel codes

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Abstract

本发明涉及一种从多点通信信道接收数据的方法和装置。多点通信信道可能在其频率响应中产生显著的深度陷波，导致对有效数据传输速率造成相应限制。本发明描述了一种特殊的时序性编码方法，该方法可在发送至信道的数据流的发送频谱中产生陷波，该陷波具有与信道频率响应中的陷波相同的频率，从而允许信道接收器成功解码所发送的数据流。该编码方法可应用于信道陷波频率的各种倍数以支持不同的吞吐速率，此外该方法还可与例如组信令码或向量信令码的其他编码技术相结合。

Description

从多点通信信道接收数据的方法和装置
本申请是申请号为201580039544.1，申请日为2015年7月20日，发明名称为“从多点通信信道接收数据的方法和装置”的专利申请的分案申请。
相关申请的交叉引用
本申请要求申请号为62/026,860，申请日为2014年7月21日，发明人为阿里·霍马提(Ali Hormati)和阿明〃肖克罗拉(Amin Shokrollahi)，名称为“多点数据传输”的美国临时专利申请的优先权，并通过引用将其内容整体并入本文，以供所有目的之用。
参考文献
以下参考文献通过引用整体并入本文，以供所有目的之用：
公开号为2011/0268225，申请号为12/784,414，申请日为2010年5月20日，发明人为Harm Cronie和Amin Shokrollahi，名称为“正交差分向量信令”的美国专利申请，下称《Cronie 1》；
公开号为2011/0302478，申请号为13/154,009，申请日为2011年6月6日，发明人为HarmCronie和Amin Shokrollahi，名称为“正交差分向量信令的差错控制编码”的美国专利申请，下称《Cronie 2》；
申请号为13/030,027，申请日为2011年2月17日，发明人为Harm Cronie、AminShokrollahi和Armin Tajalli，名称为“利用稀疏信令码进行抗噪声干扰、高引脚利用率、低功耗通讯的方法和系统”的美国专利申请，下称《Cronie 3》；
公开号为2011/0299555，申请号为13/154,009，申请日为2011年6月6日，发明人为HarmCronie和Amin Shokrollahi，名称为“正交差分向量信令的差错控制编码”的美国专利申请，下称《Cronie 4》；
申请号为61/763,403，申请日为2013年2月11日，发明人为JohnFox，BrianHolden，AliHormati，PeterHunt，JohnDKeay，Amin Shokrollahi，AnantSingh，AndrewKevinJohnStewart，GiuseppeSurace和Roger Ulrich，名称为“高带宽芯片间通信接口方法和系统”的美国临时专利申请，下称《Fox1》；
申请号为61/773,709，申请日为2013年3月6日，发明人为JohnFox，BrianHolden，PeterHunt，JohnDKeay，AminShokrollahi，AndrewKevinJohnStewart，GiuseppeSurace和RogerUlrich，名称为“高带宽芯片间通信接口方法和系统”的美国临时专利申请，下称《Fox2》；
申请号为61/812,667，申请日为2013年4月16日，发明人为JohnFox，BrianHolden，AliHormati，PeterHunt，JohnDKeay，Amin Shokrollahi，AnantSingh，AndrewKevinJohnStewart和GiuseppeSurace，名称为“高带宽芯片间通信接口方法和系统”的美国临时专利申请，下称《Fox 3》；
申请号为13/842,740，申请日为2013年3月15日，发明人为Brian Holden、AminShokrollahi和Anant Singh，名称为“芯片间通信用的向量信令码中的偏斜耐受方法以及用于芯片间通信的向量信令码的高级检测器”的美国专利申请，下称《Holden 1》；
申请号为13/895,206，申请日为2013年5月15日，发明人为Roger Ulrich和PeterHunt，名称为“通过差分高效检测芯片间通信用的向量信令码的电路”的美国专利申请，下称《Ulrich 1》；
申请号为14/315,306，申请日为2014年6月25日，发明人为Roger Ulrich，名称为“高速芯片间通信用多电平驱动器”的美国专利申请，下称《Ulrich 2》；
申请号为61/934,804，申请日为2014年2月2日，发明人为Ali Hormati和AminShokrollahi，名称为“利用符号间干扰比进行代码评价的方法”的美国临时专利申请，下称《Hormati 1》；
申请号为61/992,711，申请日为2014年5月13日，发明人为Amin Shokrollahi，名称为“高噪声容限向量信令码”的美国临时专利申请，下称《Shokrollahi 1》；
申请号为62/023,163，申请日为2014年7月10日，发明人为AminShokrollahi和RogerUlrich，名称为“高噪声容限向量信令码”的美国临时专利申请，下称《Shokrollahi2》。
背景技术
通信系统中的一个目的在于将信息从一个物理位置传输至另一物理位置。一般而言，此类信息传输的目标在于，可靠、快速且消耗最少的资源。一种常见的信息传输媒介为串行通信链路，此种链路可以以将地面或其他常用基准作为比较对象的单个有线电路或将地面或其他常用基准作为比较对象的多个此类有线电路为基础。常见的一例为使用单端信令(SES)。单端信令的工作原理为，在一条线路中发送信号，然后在接收器端以固定基准值为比较对象测定所述信号。串行通信链路也可以以相互间作为比较对象的多个电路为基础。此方面的常见的一例为使用差分信令(DS)。差分信令的工作原理在于，在一条线路中发送信号，并在配对线路中发送所述信号的相反信号。所述信号的信息由上述两线路之间的差值，而非其相对于地面或其他固定基准值的绝对值表示。
与差分信令相比，有多种信令方法可在增加引脚利用率的同时，保持相同的有益特性。向量信令为一种信令方法。通过向量信令，多条线路中的多个信号在保持每个信号的独立性的同时可视为一个整体。该信号整体中的每个信号均称为向量分量，而所述多条线路的数目称为向量“维数”。在一些实施方式中，与差分信令对的情况相同，一条线路中的信号完全取决于另一线路中的信号。因此，在某些情况下，向量维数可指多条线路内的信号的自由度数，而非确切指该多条线路的数目。
在二元向量信令中，每个向量分量(或称“符号”)的取值为两个可能取值当中的一值。在非二元向量信令中，每个符号的取值为从由两个以上可能取值所组成的集合中选出的一值。向量符号可取值的集合称为向量信令码的“符集”。在本文中，向量信令码为由长度均为N的称作码字的向量组成的集合C。向量信令码的任何合适子集均为该码的“子码”。此类子码可本身为一种向量信令码。《Cronie 1》中描述的正交差分向量信令码(ODVS)为本文所述向量信令码的一种具体示例。
操作中，码字的坐标为有界坐标，我们选用-1和1之间的实数对它们进行表示。集合C大小的二进制对数与长度N之间的比值称为该向量信令码的引脚利用率。
当向量信令码的所有码字的坐标之和恒为零时，该向量信令码称为“平衡”码。平衡向量信令码具有多种重要属性。举例而言，正如本领域技术人员所熟知，与非平衡码字相比，平衡码字所导致的电磁干扰(EMI)噪声较小。此外，当需要抗共模通信时，建议使用平衡码字。这是因为，不使用平衡码字时，需要消耗功率以生成在接收器内被消除的共模分量。
向量信令方法的其他示例见《Cronie 1》，《Cronie 2》，《Cronie 3》，《Cronie4》，《Fox 1》，《Fox 2》，《Fox 3》，《Holden 1》，《Shokrollahi 1》及《Hormati I》。
发明内容
多点通信信道中不可避免地发生阻抗异常现象，从而在现有系统的信道频率响应中引入相应的深度陷波，并对有效数据速率造成相应限制。即使陷波后的信道频谱并未出现高度衰减且仍然可用，上述结果仍然存在。本文描述了一种特殊的时序性编码方法，该方法可在发送至信道的数据流的发送频谱中产生陷波，该陷波具有与信道频率响应中的陷波相同或相似的频率，从而允许信道接收器成功解码所发送的数据流。
附图说明
图1所示为典型的多点通信系统，该系统包括由多线路通信信道120相互连接的发送器110和接收器130，150。
图2所示为根据至少一种实施方式使用不同速率乘数值M的数据帧序列。
图3A所示为例示信道的频率响应特性，而图3B所示为该信道的脉冲响应。
图4A为一种实施方式的接收眼图，该实施方式使用图3A信道，且M＝2。图4B为该信道的接收眼图及原始信令速率，其不具有各所述实施方式的有益效果。
图5所示为另一例示信道的频率响应特性以及使用不同速率乘数值M的实施方式的接收眼图。
图6为根据至少一种实施方式的方法流程图。
图7为根据至少一种实施方式的另一方法流程图。
具体实施方式
众所周知，在高数据速率下，必须将通信信道作为高频传输线。因此，通信信号路径中的每一连接异常均可能引入阻抗变化，从而导致正在传播的发送波形的某一部分被反射。这不但可弱化波形的后续部分，并可产生反向传播的波形。该波形可能又被其他阻抗异常反射，从而生成上述信号波形的延迟版本，其可造成主波形的失真或干扰。
如图1所示的多点通信信道可能受此传播问题的影响极大。在图示例中，发送器110将信号驱动至线路125上，这些线路共同构成通信信道120。接收器130和150均为这些信号的可能接收方。然而，将接收器150连接至通信信道120的线路128为一种在通信信道120中形成极大阻抗异常的“末梢”传输线元件，这是因为线路125内传播的信号必须分割并沿两条路径进入接收器130和150。
本领域技术人员可注意到的是，此多点结构通常在信道所测频率响应特性中存在如图3A所示的陷波，该陷波频率与信号在通信介质的传播速度下从发送器传播至阻抗异常处的距离中发生的传播延迟成反比。在时域中，此现象表现为显著的反射信号，如图3B所示，该信号的延时与通信信道传播速度下从发送器到阻抗异常处的距离成正比。本领域技术人员容易理解的是，多点连接的增加将使得上述状况进一步加剧，在最坏情况中，在多卡背板或堆叠芯片结构的总线中可发生均匀周期性间距间隔。
基本概念
当想要以不同数据速率在上述通信介质中发送数字信号时可发现，该介质的“有效吞吐量”(即可实现良好或无中断数据接收的速率)发生显著变化，其中，当速率等于或高于频率响应的陷波频率时，将发生极差的传输特性。在时域中，这可表现为，当发送信号出现于接收器中的同时，还出现之前所发送信号的延迟版本，其导致极差或完全不可用的检测结果。
相反，可以发现，当通过将传输速率设置为陷波频率的整数倍以生成由N个数据单元D1,...,DN组成的“帧”时，举例而言，数据单元DN必然与前一发送数据单元D1,...,DN-1中的一个发生数据单元传输干扰。已知DN中的待传输数据允许选出一值在前一(如干扰)时间间隔内传输，从而与DN相长性交互，以促进其接收，这方面的一例为在前后时间间隔内均传输相同信道信号值。或者，也可在前一时间间隔内发送不对DN的接收造成影响的值，此方面的一例为在数据信号为+1和-1的信道上发送静态或“零”值，另一例为当延迟干扰信号反转时，也将所述数据反转。
顺序传输数据帧
第一实施方式采用周期T等于1/fnotch的数据帧，其中，fnotch为信道频率响应中的第一陷波频率。所述帧划分为具有相等持续时间的2×M个部分，其中M为通常大于1的整数，各部分组成的序列表示数据流的连续发送信号单元间隔。所述帧的前一半在本文中可称为前一发送帧，其具有M个符号。该帧的后一半在本文中可称为后一发送帧，其具有M个符号。该帧的一般形式为：
Figure BDA0002398911980000071
其中，Di表示用于传输的信令方案的电平，例如二元数据传输的电平为±1，所述M个数据单元D1,...,DM中的每一个均传输两次，其中，在后一发送帧中以相同顺序重复发送与前一发送帧中相同的M个传输值，从而使得总吞吐量等于M×fnotch。本领域技术人员可发现，此周期性重复消息格式的频谱在频率为(2K+1)×fnotch处具有陷波，因此，我们可通过以(2×M)×fnotch的速率采样，丢弃第一组M个样本(即前一发送帧内的样本)并保持后一组M个样本，以令其表示D1,...,DM的方式，在接收器中成功恢复数据序列D1,D2,D3,...,DM。
上述数据帧序列还示于图2，该图示出了M＝2，M＝3和M＝4时的二元数据传输。后一发送帧中发送的顺序数据值示为D1,...,DM，而前一发送帧中发送的补偿值示为D1',...,DM'。因此，对于M＝2的示例，原始传输速率为4×fnotch，数据单元D1和D2中的每一个均在跨越时间t0至时间t3的数据帧内发送两次，该帧总持续时间如图所示为1/fnotch。
在时域中，带陷波的多点信道在fnotch下将输入信号的延迟衰减版本叠加至其自身，其中，所述延迟等于t＝1/(2*fnotch)。从所述数据帧可明显看出，前一发送帧内发送的数据元素将干扰后一发送帧内的数据元素，从而造成信道所致叠加。该信道所致叠加可与上述定时和重复数据传输相加，从而实现更大的接收器眼开度。
替代实施方式
在一种替代实施方式中，在前一发送帧内发送半帧零值或发送类似静态信道信号，并在后一发送帧内发送数据，以衰减上述干扰性延迟信号。因此，如图2所示，在此实施方式中，补偿值D1',...,DM'为零。然而，由于此实施方式不能实现可增强接收信号的相长干涉，因此与上述将每个数据值发送两次的方法相比，其接收垂直眼开度较小。可以注意到，在此方法中，接收器在后一帧的前一半内仍可检测到信号，这些信号包括近零值以及来自前一帧的后一半的延迟数据值，从而为实施方式同一组M个比特提供两种独立检测结果提供了可能性。
另一替代实施方式在前一发送帧内发送半帧反转数据值，然后在后一发送帧内发送半帧未反转数据值，从而实现信道所致叠加，该叠加表示干扰性延迟信号因反射而被反转的状况下发生的相长干扰。再次参考图2，在此实施方式中，补偿值D1',...,DM'为发送值D1,...,DM的逻辑反转值。
对本领域技术人员容易理解的是，数据帧的等效模式包括数据后跟随反转数据，数据后跟随零值等。
其他变形
应该注意的是，上述实施方式的应用方式为一种按线路应用的方式，因此其可与已知的多线路编码方案以明显的方式组合，也就是说，在多条线路上发送向量信令码的码字序列，而非在单条线路上发送单个比特，同时在帧的后一半重复所述码字序列。类似地，虽然以上示例为了描述目的展现了二元信道信令，但这并不意味着限制，本实施方式还可直接应用于三元，四元和更高阶信令。
由于上述数据帧的传输速率根据信道陷波频率决定，因此，理想地，需要至少事先知道该陷波频率的大约值。对于背板、堆叠芯片等常用结构，由于其信道尺寸和组成是固定的，因此其预期特性众所周知。或者，在其它实施方式中，可对信道进行测量并将通信数据速率的设置作为电路设置及初始化过程的一部分，其中，所述信道既可直接测量为信号强度对频率曲线图，也可通过测量脉冲反射时间而间接测量(即作为时域反射计或TDR测量)。
在一些实施方式中，为了优化特定接收器位置处预期、计算或测量反射组合的接收效果，每个接收器或每组接收器可具有维持各自的信道补偿参数。在其他实施方式中，所有接收器可使用一致或平均的补偿参数。这些补偿参数可包括所述陷波频率，乘数M以及数据帧格式，该格式包括其内所含校正信号的极性和类型。针对不同发送器，上述补偿参数可不同：作为具体一例，信道在两个方向上可具有不同特性，因此具有不同优选补偿参数。
在实际实施方式中，传输速率可仅接近最优速率2×M×fnotch，并同时牺牲适度的接收信号质量，其部分由信道陷波的深度和宽度决定。
图示结果
在一种实施方式中，使用如图3A所示约为900MHz频率响应陷波的信道且数据帧的M＝2，所得原始发送数据速率为1.8Gbps。所使用发送FIR滤波器等于[0.7，-0.3]。此配置下的接收眼图如图4A所示。为了比较目的，如图4B所示为当在该信道中以1.8Gbps发送任意数据(即不使用上述数据帧且不按重复发送方式发送)时的接收眼图。如图所示，与上述信令方法相比，信号接收效果大幅下降。
图5所示为另一实施方式的性能特性。本实施方式所用信道的深度陷波频率响应特性示于标记为“信道”的第一幅图中，而标记为“M＝2”至“M＝6”的后续各图所示为M值逐渐增加时所述信道传输的接收器眼图。
其他实施方式
下文中使用δ作为信道频率响应陷波深度的相对度量，其中，δ＝1表示极深陷波，而δ＝0表示完全没有陷波。
在使用单端NRZ编码的其他实施方式中，以数据帧[d1 d2 d1 d2 d3 d4]代替上述例示数据帧[d1 d2 d1 d2]。在接收器处，比特d1和d2(处于第3和第4位)可直接确定，而比特d3和d4可使用已知判定反馈均衡(DFE)技术确定。d3的检测需要d1(与其相干扰的前一信号)为已知值，类似地，d4的检测需要d2为已知值。判定反馈均衡可将此类前一接收信号从当前样本中减除，从而生成消歧样本用于检测。在此实施方式中，帧长([d1 d2 d1 d2 d3d4]的时长)设为1.5/fnotch，从而可实现4/1.5×fnotch＝2.66×fnotch的数据传输速率。判定反馈均衡水平取决于δ且可以自适应方式设置。该技术还可用于[0 0d1 d2 d3 d4]结构的数据帧。
在第二种其他实施方式中，使用5电平驱动器，并在1.5/fnotch的时间内发送序列[ab a b c-a d-b]。本领域技术人员可注意到的是，此方式下的预期接收序列为[无用，无用，a×(1+δ)，b×(l+δ)，c-a×(l-δ)，d-b×(1-δ)]。当δ接近1时(如-20dB左右)，则c-a×(l-δ)和d-b×(1-δ)的垂直眼开度略小于正常垂直眼开度(水平眼开度也如此)，而且符号主要为二进制符号(因此，根据《Hormati 1》的教示内容，符号间干扰比为1)。此实施方式可在1.5/fnotch的时间内发送4个比特，因此总速率为每线路每秒2.666×fnotch个比特。
第三种其他实施方式适用于反射程度不大，即δ例如为0.3数量级的情况。在本实施方式中，使用[1，0-δ]的发送FIR滤波器对发送数据进行滤波。在接收器处，所得数据形式为d2-δ2d0～＝d2，而且由于δ较小，其不会导致眼开度的大幅下降。此实施方式要求提前获知或测量δ。
当δ接近1时(即深度陷波)，第四种实施方式使用长度为2/fnotch的[d0d1 d0 d1(d0×d2)(d1×d3)(d0×d2×d4)(d1×d3×d5)]形式的帧，以在6/2×fnotch＝3×fnotch的速率下发送数据。在接收器处，该帧的前两个单元间隔被前一帧破坏。第3和第4位的比特d0和d1可通过PAM2检测进行提取。对于下一比特，可得d0×d2+δ×d0＝d0×(δ+d2)～＝d0×(1+d2)。通过实施PAM3检测以视d0×(1+d2)是否为零的方式，可实现d2的提取。如果上式为零，则d2＝-1，否则，d2＝1。通过此方式，还可获得比特d3，d4和d5。此技术的另一优点在于其可限制误差的传播。
实施方式
如图6所示，根据至少一种实施方式的方法600包括：在步骤602中，从多线路总线的线路上接收M个接收符号的帧，该多线路总线具有陷波频率fnotch，其中，所接收的M符号帧中的每个接收符号包括前一M符号发送帧的发送符号与后一M符号发送帧的相应发送符号的信道所致叠加，所述前一和后一发送帧具有2×M×fnotch的符号速率；以及在步骤604中，通过利用至少一个先前解码的发送符号对所述M个接收符号进行解码而形成一组输出符号。
在至少一种实施方式中，所述前一M符号发送帧与后一M符号发送帧相同。
在至少一种实施方式中，所述前一M符号发送帧包括所有静态符号。
在至少一种实施方式中，所述前一M符号发送帧为所述后一M符号发送帧的反转版本。
在至少一种实施方式中，所述前一M符号发送帧与后一M号符发送帧不同。在至少一种实施方式中，所述前一M符号发送帧包括至少一个先前解码的发送符号，对所述M个接收符号进行解码包括通过将所述至少一个先前解码的发送符号与所述后一发送帧的相应发送符号叠加而形成至少一个输出符号。
在至少一种实施方式中，所述陷波频率由阻抗异常决定。
在至少一种实施方式中，所述阻抗异常表示为与所述多线路数据总线连接的多个接收器。
在至少一种实施方式中，所述相应发送符号表示至少两个不同输入符号的组合。
如图7所示，根据至少一种实施方式的方法700包括：在步骤702中，接收一组输入符号；在步骤704中，生成包括M个符号的帧；在步骤706中，生成包括M个符号的后一发送帧；在步骤708中，将所述发送帧的符号以2×M×fnotch的符号速率在多线路总线的线路上发送，其中，fnotch为与所述多线路总线相关联的陷波频率；以及在步骤710中，随后将所述后一发送帧的符号以2×M×fnotch的符号速率在所述多线路总线的线路上发送。
在至少一种实施方式中，一种装置，包括：多线路总线的线路，该线路配置为接收M个接收符号的帧，该多线路总线具有陷波频率fnotch，其中，所接收的M个接收符号的帧中的每个接收符号包括前一M符号发送帧的发送符号与后一M符号发送帧的相应发送符号的信道所致叠加，所述前一和后一发送帧具有2×M×fnotch的符号速率；以及解码器，该解码器配置为通过利用至少一个先前解码的发送符号对所述M个接收符号进行解码而形成一组输出符号。
在至少一种实施方式中，所述前一M符号发送帧与后一M符号发送帧相同。
在至少一种实施方式中，所述前一M符号发送帧包括所有静态符号。
在至少一种实施方式中，所述前一M符号发送帧为所述后一M符号发送帧的反转版本。
在至少一种实施方式中，所述前一M符号发送帧与后一M符号发送帧不同。
在至少一种实施方式中，所述前一M符号发送帧包括至少一个先前解码的发送符号，所述解码器进一步配置为通过将所述至少一个先前解码的发送符号与所述后一发送帧的相应发送符号叠加而形成至少一个输出符号。
在至少一种实施方式中，所述陷波频率由阻抗异常决定。
在至少一种实施方式中，所述阻抗异常表示为与所述多线路数据总线连接的多个接收器。
在至少一种实施方式中，所述装置还包括：一组输入线路，每条输入线路配置为接收一组输入符号；编码器，该编码器配置为生成包括M个符号的发送数据帧以及包括M个符号的后一发送数据帧；以及驱动器，该驱动器配置为将所述发送数据帧的符号以2×M×fnotch的符号速率在所述多线路总线的线路上发送，然后将所述后一发送数据帧的符号以2×M×fnotch的符号速率发送，其中，fnotch为与所述多线路总线相关联的陷波频率。
在至少一种实施方式中，所述相应发送符号表示至少两个输入符号的组合。
为了描述的简洁性，本文所呈实施例描述了发送器和多个接收器在多点网络配置中的互连。然而，不应以任何方式将此视为对所描述实施方式的范围构成了限制。本申请中所公开的方法同等适用于具有显著频率响应陷波的其他互连拓扑以及其他通信协议，这些协议包括全双工、半双工和单工通信协议。类似地，有线通信仅用作说明性示例，上述实施方式还可应用于包括光学性、电容性、电感性及无线通信在内的其他通信介质。因此，“电压”和“信号水平”等描述性词语应视为包括其在其他度量系统中的同等概念，如“光强”、“射频调制”等。本文所使用的“物理信号”一词包括可传送信息的物理现象的任何适用形态和属性。此外，物理信号可以为有形的非暂时性信号。

Claims (15)

1.一种从多点通信信道接收数据的方法，其特征在于，包括：
经由多线路总线的线路接收符号帧，其中所接收的符号帧包括具有相等数目符号的多个部分，数据符号帧中的每个数据符号以2*M*fnotch的速率被接收，其中，fnotch是与所述多线路总线相关联的陷波频率，M为表示所述多个部分中的每个部分中的符号数目的整数并且M大于1；
从所述多个部分中的第一部分确定第一组M个数据符号，所述第一部分对应于第一数据符号发送帧和初始符号帧的第一信道所致叠加；以及
从所述多个部分中的第二部分确定第二组M个数据符号，所述第二部分对应于第二数据符号发送帧和所述第一数据符号发送帧的第二信道所致叠加，其中至少基于所述第一组M个数据符号确定所述第二组M个数据符号。
2.如权利要求1所述的方法，其特征在于，所述初始符号帧中的符号具有静态值。
3.如权利要求1所述的方法，其特征在于，所述初始符号帧为所述第一数据符号发送帧的副本。
4.如权利要求1所述的方法，其特征在于，所述初始符号帧为所述第一数据符号发送帧的反转副本。
5.如权利要求1所述的方法，其特征在于，根据所述第一数据符号发送帧中的符号对所述第二数据符号发送帧中的符号进行预均衡。
6.如权利要求1所述的方法，其特征在于，根据所测量的所述陷波频率的陷波深度对所述第二数据符号发送帧中的符号进行预均衡。
7.如权利要求1所述的方法，其特征在于，在t＝1/(2*fnotch)的时间周期内接收每个部分。
8.如权利要求1所述的方法，其特征在于，所述陷波频率与与所述多线路总线相关的阻抗异常相关。
9.一种从多点通信信道接收数据的装置，其特征在于，包括：
多线路总线中的线路，用于接收符号帧，所接收的符号帧包括具有相等数目符号的多个部分，数据符号帧中的每个数据符号以2*M*fnotch的速率被接收，其中，fnotch是与所述多线路总线相关联的陷波频率，M为表示所述多个部分中的每个部分中的符号数目的整数并且M大于1；
解码器，用于确定多组M个数据符号，每组M个数据符号从所述多个部分的相应部分中确定，所述多组M个数据符号包括：
从所述多个部分中的第一部分确定的第一组M个数据符号，所述第一部分对应于第一数据符号发送帧和初始符号帧的第一信道所致叠加；和
从所述多个部分中的第二部分确定的第二组M个数据符号，所述第二部分对应于第二数据符号发送帧和所述第一数据符号发送帧的第二信道所致叠加，其中至少基于所述第一组M个数据符号确定所述第二组M个数据符号。
10.如权利要求9所述的装置，其特征在于，还包括预均衡电路，用于根据所述第一数据符号发送帧中的符号对所述第二数据符号发送帧中的符号进行预均衡。
11.如权利要求9所述的装置，其特征在于，所述预均衡电路用于根据所测量的所述陷波频率的陷波深度对所述第二数据符号发送帧中的符号进行预均衡。
12.如权利要求9所述的装置，其特征在于，在t＝1/(2*fnotch)的时间周期内接收每个部分。
13.如权利要求9所述的装置，其特征在于，在1.5/fnotch的时间帧内发送所述初始化符号帧，所述第一数据符号发送帧和所述第二数据符号发送帧。
14.如权利要求9所述的装置，其特征在于，所述多线路总线上的总数据吞吐率大于M*fnotch。
15.如权利要求9所述的方法，其特征在于，所述陷波频率与与所述多线路总线相关的阻抗异常相关。
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