WO2023156457A1 - Circuit de commande pour un électrofiltre - Google Patents

Circuit de commande pour un électrofiltre Download PDF

Info

Publication number
WO2023156457A1
WO2023156457A1 PCT/EP2023/053761 EP2023053761W WO2023156457A1 WO 2023156457 A1 WO2023156457 A1 WO 2023156457A1 EP 2023053761 W EP2023053761 W EP 2023053761W WO 2023156457 A1 WO2023156457 A1 WO 2023156457A1
Authority
WO
WIPO (PCT)
Prior art keywords
voltage
drive circuit
circuit
control signal
transformer
Prior art date
Application number
PCT/EP2023/053761
Other languages
German (de)
English (en)
Inventor
Anton Wolf
Benjamin Nützenadel
Jan-Arne KÖNIG
Original Assignee
Woco Gmbh & Co. Kg
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Woco Gmbh & Co. Kg filed Critical Woco Gmbh & Co. Kg
Publication of WO2023156457A1 publication Critical patent/WO2023156457A1/fr

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B03—SEPARATION OF SOLID MATERIALS USING LIQUIDS OR USING PNEUMATIC TABLES OR JIGS; MAGNETIC OR ELECTROSTATIC SEPARATION OF SOLID MATERIALS FROM SOLID MATERIALS OR FLUIDS; SEPARATION BY HIGH-VOLTAGE ELECTRIC FIELDS
    • B03C—MAGNETIC OR ELECTROSTATIC SEPARATION OF SOLID MATERIALS FROM SOLID MATERIALS OR FLUIDS; SEPARATION BY HIGH-VOLTAGE ELECTRIC FIELDS
    • B03C3/00—Separating dispersed particles from gases or vapour, e.g. air, by electrostatic effect
    • B03C3/34—Constructional details or accessories or operation thereof
    • B03C3/66—Applications of electricity supply techniques
    • B03C3/68—Control systems therefor
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from ac input or output
    • H02M1/126—Arrangements for reducing harmonics from ac input or output using passive filters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05K—PRINTED CIRCUITS; CASINGS OR CONSTRUCTIONAL DETAILS OF ELECTRIC APPARATUS; MANUFACTURE OF ASSEMBLAGES OF ELECTRICAL COMPONENTS
    • H05K1/00—Printed circuits
    • H05K1/02—Details
    • H05K1/0213—Electrical arrangements not otherwise provided for
    • H05K1/0216—Reduction of cross-talk, noise or electromagnetic interference
    • H05K1/0218—Reduction of cross-talk, noise or electromagnetic interference by printed shielding conductors, ground planes or power plane
    • H05K1/0224—Patterned shielding planes, ground planes or power planes
    • H05K1/0227—Split or nearly split shielding or ground planes
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05K—PRINTED CIRCUITS; CASINGS OR CONSTRUCTIONAL DETAILS OF ELECTRIC APPARATUS; MANUFACTURE OF ASSEMBLAGES OF ELECTRICAL COMPONENTS
    • H05K1/00—Printed circuits
    • H05K1/18—Printed circuits structurally associated with non-printed electric components
    • H05K1/181—Printed circuits structurally associated with non-printed electric components associated with surface mounted components
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05K—PRINTED CIRCUITS; CASINGS OR CONSTRUCTIONAL DETAILS OF ELECTRIC APPARATUS; MANUFACTURE OF ASSEMBLAGES OF ELECTRICAL COMPONENTS
    • H05K2201/00—Indexing scheme relating to printed circuits covered by H05K1/00
    • H05K2201/09—Shape and layout
    • H05K2201/09209—Shape and layout details of conductors
    • H05K2201/09654—Shape and layout details of conductors covering at least two types of conductors provided for in H05K2201/09218 - H05K2201/095
    • H05K2201/0969—Apertured conductors
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05K—PRINTED CIRCUITS; CASINGS OR CONSTRUCTIONAL DETAILS OF ELECTRIC APPARATUS; MANUFACTURE OF ASSEMBLAGES OF ELECTRICAL COMPONENTS
    • H05K2201/00—Indexing scheme relating to printed circuits covered by H05K1/00
    • H05K2201/10—Details of components or other objects attached to or integrated in a printed circuit board
    • H05K2201/10007—Types of components
    • H05K2201/10015—Non-printed capacitor
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05K—PRINTED CIRCUITS; CASINGS OR CONSTRUCTIONAL DETAILS OF ELECTRIC APPARATUS; MANUFACTURE OF ASSEMBLAGES OF ELECTRICAL COMPONENTS
    • H05K2201/00—Indexing scheme relating to printed circuits covered by H05K1/00
    • H05K2201/10—Details of components or other objects attached to or integrated in a printed circuit board
    • H05K2201/10007—Types of components
    • H05K2201/1003—Non-printed inductor
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05K—PRINTED CIRCUITS; CASINGS OR CONSTRUCTIONAL DETAILS OF ELECTRIC APPARATUS; MANUFACTURE OF ASSEMBLAGES OF ELECTRICAL COMPONENTS
    • H05K2201/00—Indexing scheme relating to printed circuits covered by H05K1/00
    • H05K2201/10—Details of components or other objects attached to or integrated in a printed circuit board
    • H05K2201/10007—Types of components
    • H05K2201/10174—Diode

Definitions

  • the invention relates to a control circuit for generating a high voltage which is applied to the electrodes of an electrostatic precipitator. Another aspect is the use of such a control circuit in a device, e.g. a room air filter or a fine dust filter.
  • the invention further relates to a circuit board on which a control circuit according to the invention is implemented by means of discrete components.
  • Electrostatic separators are used, for example, in room air filters, fine dust filters or similar devices.
  • the electrodes of the electrostatic precipitator are conventionally driven with a pulsed positive high voltage in order to generate a plasma between the electrodes of the electrostatic precipitator.
  • control circuits are used in the end devices, which convert the input-side low voltage into high voltage.
  • transformers are often used that provide a correspondingly high multiplication factor by appropriately selecting the number of turns on the primary side and the secondary side of the transformer.
  • the patent application WO 2021/224017 Ai describes a room air cleaner in which an emission electrode surrounded by water is located opposite an arrangement of counter-electrodes in order to form the desired electric field between the emission electrode and the counter-electrode.
  • the counter emission electrodes are formed of needles.
  • US Pat. No. 8,529,830 B2 describes an air cleaning device.
  • the air cleaning device comprises a plasma reactor which is driven by a voltage supply circuit with voltage pulses, the Width of the voltage pulses can be varied by the voltage supply circuit.
  • the voltage supply circuit is supplied with an AC voltage on the input side, which is first converted into a DC voltage by means of a rectifier circuit and subsequent filter.
  • a digital control circuit of the power supply circuit controls the primary side of a transformer using a switch with pulses of DC voltage, so that high-voltage pulses of 10-2 ps of a positive high voltage in the range of 12 kV to 16 kV (peak-valley value ) are generated, by means of which a plasma is generated.
  • the control circuit is regulated based on the primary-side current flowing through the switch in the primary-side part of the voltage supply circuit.
  • the pulse frequency of the power supply circuit is in the range of 20-100 kHz.
  • Patent application US 2004/0033176 Ai describes an electrokinetic air conditioning system that removes particles from the air in order to generate a particle-free air flow.
  • the air conditioner includes an ion generator having an electrode assembly that includes a first row of emitter electrodes, a second row of collector electrodes, and a high voltage generator.
  • the high-voltage generator generates AC voltage from the input side, which is first converted into a DC voltage using an oscillator which switches a switch statically at a frequency of 20 kHz in order to generate voltage pulses.
  • the voltage pulses are stepped up into high-voltage pulses by means of a transformer. Another voltage multiplier is used on the secondary side of the transformer to generate high-voltage pulses.
  • This patent application is based, among other things, on the object of proposing an improved drive circuit for generating a high voltage for driving an electrostatic precipitator.
  • One or more of the following considerations may be considered in improving the drive: the stability of the drive circuit over the desired temperature range in which it is operated (e.g. -40°C to +160°C); a high speed of response of the control loop to the ambient temperatures and parameters (e.g. rapid temperature changes, undesired breakdowns of the plasma, etc.); high requirements for electromagnetic compatibility (EMC); possibility of discrete construction of the circuit; miniaturization of the individual components, especially the transformer, the control circuit.
  • EMC electromagnetic compatibility
  • a further aspect and a further object of this patent application lies in the design of a circuit board which implements the control circuit and can reliably prevent creepage currents and arcing on the circuit board. This object is solved by the subject matter of independent patent claim 22 .
  • a significant further aspect and a further object of this invention is to improve a room air cleaner, as known for example from patent application WO 2021/224017 Ai, in particular to specify a control and/or electronic control in order, with regard to the use of a liquid, which wets the counter-electrode, to ensure adequate cleaning results on the one hand, and on the other hand the high demands on the safety of the people in the room to be cleaned.
  • This object is solved by the subject matter of independent patent claim 31 .
  • One aspect of the invention relates to a drive circuit for generating a high voltage which is applied to the electrodes of an electrostatic precipitator.
  • the electrodes of the electrostatic precipitator are not controlled with a pulsed high voltage, but with a DC voltage in the high voltage range, so that a direct current flows through the electrodes of the electrostatic precipitator.
  • the control circuit of the control circuit includes a current measuring unit that measures the direct current flowing across the electrodes of the electrostatic precipitator.
  • the control circuit regulates the output power of the control circuit based on the measured value of the direct current flowing and regulates the direct current to a reference current value.
  • the control loop can, for example, have a control cycle of 5 ms or less, preferably 2 ms or less, more preferably 1 ms or less. The shorter the control cycle, the faster fluctuations in the measured direct current can be detected and corrected.
  • One embodiment of the invention relates to a device with a control circuit that is set up to generate a high voltage from a low voltage of a DC voltage source and to apply the high voltage to the one or more emission electrodes and their counter-electrode of the electrostatic precipitator in order to generate a DC plasma between the emission electrode(s). ) and the counter electrode.
  • the control circuit includes a control circuit with a current measuring unit.
  • the current measuring unit measures the direct current flowing through the emission electrode(s) via the direct current plasma to the counter electrode of the electrostatic precipitator to the common reference potential of the drive circuit.
  • the control circuit is set up to regulate the output power of the control circuit (or its output current) based on the value of the measured direct current flowing to a reference current value.
  • the reference potential of the drive circuit can be, for example, the reference potential that is used to define all voltages in the drive circuit. This reference potential is also referred to as internal ground. This may or may not correspond to earth mass (common ground).
  • control circuit is set up to set the output power of the control circuit (or its output current) based on the measured value of the direct current relative to the reference current value to an operating point at which a spark discharge of the direct current plasma between the emission electrodes and the counter-electrode is prevented.
  • spark discharge/breakdown of the direct current plasma is regarded as an error case and the regulation by the control circuit prevents such a breakdown of the direct current as far as possible.
  • Whether breakdowns occur depends, among other things, on the series resistances of the emission electrodes, their insulation and the conditions in the separation room. Pressure fluctuations (e.g. slamming doors) or macroscopic particles (e.g. hair) can lead to breakdowns in the separation room. While breakdowns due to macroscopic particles can only be corrected with difficulty, pressure fluctuations in the separation chamber, for example, can be reliably prevented by means of the control system according to the invention.
  • a breakdown rate can be estimated as follows. If a restart lasts 5 s (parameterizable), then 10 m 3 /h corresponds to approximately 0.5 breakdowns per minute. The breakdown rate of conventional electrostatic precipitators is often in the range of 40 or more breakdowns per minute.
  • the control circuit of the control circuit includes a control unit which receives the measured value of the flowing direct current from the current measuring unit and generates a control signal.
  • the control unit can, for example, by means of a microprocessor, a discrete circuit or an integrated circuit (e.g. Application Specific Integrated Circuit (ASIC) or programmable logic (e.g. Field Programmable Gate Array (FPGA), Programmable Logic Device (PLD), etc.) or combinations of the A microcontroller from the S12ZVM family from NXP, such as the microprocessor S912ZVMBA6F0WLF from NXP, can be used as a possible microprocessor, for example.
  • the control signal generated by the control unit is, for example, a transistor-transistor logic (TTL) control signal or CMOS control signal
  • TTL transistor-transistor logic
  • the control unit can also be set up to vary the frequency of the control signal based on the value of the direct current and the reference current value in order to direct the direct current flowing through the emission electrodes via the direct current plasma to the counter electrode of the electrostatic precipitator to the common reference potential of the drive circuit and the electrostatic precipitator to the reference current value regulate
  • control signal has a frequency in the range 120.0 kHz to 200.0 kHz inclusive, preferably in the range 130.0 kHz to 170.0 kHz inclusive.
  • the resonant frequency of the transformer is higher than the frequency of the control signal; it is preferably in the range 200.0 kHz to 240.0 kHz inclusive.
  • control circuit has a transformer and a high-voltage cascade connected to a secondary-side coil of the transformer in order to convert the low voltage of the low-voltage DC voltage source or a DC voltage derived therefrom into the high voltage.
  • the current measuring unit measures the direct current at a center tap of a voltage divider, the voltage divider being connected to the secondary coil of the transformer on one side and to the counter electrode of the electrostatic precipitator and the reference potential of the control circuit on the other side.
  • a further aspect of the invention relates to the construction of the transformer, which can be used in the different embodiments of the control circuit.
  • the transformer contains either a primary side coil and a secondary side stage, or alternatively, two primary side coils wound in the same direction and connected in series and one secondary side coil. in the latter In this case, the coils on the primary side can optionally be nested in order to make the transformer more compact.
  • the windings of the secondary-side coil are divided into a number of partial coils.
  • the transformer can further comprise a non-conductive housing (eg a bobbin) which is divided into a plurality of housing sections which are arranged parallel to one another in one direction and are separated from one another by a non-conductive material and in which the respective partial coils are arranged.
  • the transformer can be integrated in an EFD20 housing, for example.
  • the resonant frequency of the transformer is preferably in the range 200.0 kHz to 240.0 kHz inclusive.
  • the ratio of the number of turns of the (one) primary-side coil or each of the two primary-side coils of the transformer and the number of turns of the secondary-side coil of the transformer is in the range 0.015 to 0.025 inclusive. In an exemplary embodiment, this ratio is 0.02.
  • the number of turns of the primary-side coil(s) of the transformer is between 13 turns and 18 turns inclusive
  • the number of turns of the secondary-side coil of the transformer is between 700 turns and 800 turns inclusive.
  • the transformer is controlled with two power switches.
  • the two power switches can be designed as n-channel metal-oxide-semiconductor field effect transistors (NMOS MOSFETs).
  • the drive circuit includes a transformer with two coils on the primary side, wound in the same direction, and one coil on the secondary side. Each coil on the primary side has one end that is connected to the low voltage of the DC voltage source or to a DC voltage derived therefrom.
  • the control circuit also includes a first power switch (e.g.
  • PWM control signal pulse-width-modulated control signal
  • second power switch e.g. power transistor or thyristor
  • the "inverted variable-frequency PWM control signal” is a signal that is in phase with the variable-frequency PWM control signal but is inverted: A rising edge of the PWM control signal corresponds in time to a falling edge of the inverted PWM control signal and a falling edge of the PWM control signal corresponds in time to a rising edge of the inverted PWM control signal.
  • the control circuit also comprises a first driver circuit, which is designed as a one-stage or multi-stage level converter in order to adapt the signal level of the TTL/CMOS control signal to the signal level of the first power switch and to supply the adapted control signal to the first power switch as the frequency-variable PWM control signal; and a second driver circuit configured as a single or multi-stage level shifter to adjust the signal level of the TTL/CMOS control signal to the signal level of the second power switch and to supply the adjusted control signal to the first power switch as the inverted variable-frequency PWM control signal.
  • each of the first and second driver circuits can optionally have a plurality of resistors, diodes and transistors and be set up to coordinate the charging and discharging of the gate capacitances of the transistors in the individual stages of the level converter in such a way that respective transistor pairs in each stage of the driver circuits which are connected in series between a direct voltage corresponding to the low voltage or derived therefrom and the reference potential, in a predetermined temperature range in which the control circuit is operated, preferably around the range
  • the driver circuits can be designed identically, so that it can be ensured that the driver circuits show fluctuations in temperature fluctuations, ie that, for example, changes in the rise times and fall times of the signal edges, particularly due to the Fluctuations in the resistance values of the resistors at different temperatures are the same in the individual driver circuits.
  • the transformer is controlled with four power switches or, alternatively, by means of two power switches and two capacitors that form a full bridge.
  • the driving circuit comprises a transformer with a primary-side coil and a secondary-side coil.
  • the one coil on the primary side can be formed by a series connection of coils wound in the same direction, in particular two coils.
  • the drive circuit also includes a first power switch (e.g. power transistor or thyristor), which is driven with a variable-frequency PWM control signal and, depending on the control signal of a control unit of the control circuit, connects a second end of the primary-side coil to a DC voltage that corresponds to the low voltage or is derived therefrom; a second power switch (e.g.
  • a power transistor or thyristor which is driven by the inverted variable-frequency PWM control signal and which, in response to the inverted control signal, connects a first end of the primary-side coil to the direct voltage corresponding to or derived from the low voltage; a third power switch (e.g. power transistor or thyristor) which is driven by the inverted variable-frequency PWM control signal and which, depending on the inverted control signal, connects the second end of the primary-side coil to the reference potential of the drive circuit; and a fourth power switch (eg power transistor or thyristor) which is driven by the frequency-variable PWM control signal and which, depending on the control signal, connects the first end of the primary-side coil to the reference potential of the drive circuit.
  • a third power switch e.g. power transistor or thyristor
  • a fourth power switch eg power transistor or thyristor
  • a capacitor can optionally be connected between the gate connection and drain connection of the power switches designed as power transistors in order to suppress conducted interference.
  • the first and second power switches can be implemented as p-channel metal-oxide-semiconductor field effect transistors (PMOS MOSFETs), for example.
  • the third and the fourth power switch can be embodied as n-channel metal-oxide-semiconductor field effect transistors (NMOS MOSFETs), for example.
  • the first and third power switches are each replaced by a capacitor, so that a virtual ground point is formed between the two capacitors, which is connected to the second end of the coil. In this case, no driver circuits for the first and third Circuit breakers are provided, ie in this embodiment only the remaining two (second and fourth) circuit breakers are controlled accordingly by driver circuits.
  • the drive circuit comprises a plurality of driver circuits which adapt the TTL or CMOS control signal from the control unit of the control loop to the signal level of the power switches.
  • the control circuit accordingly comprises a first driver circuit, which is designed as a one or more stage level converter to adapt the signal level of the TTL/CMOS control signal to the signal level of the first power switch and to supply the adapted control signal to the first power switch as the variable-frequency PWM control signal; a second driver circuit, which is designed as a single or multi-stage level shifter, in order to adapt the signal level of the TTL/CMOS control signal to the signal level of the second power switch and to supply the adapted control signal to the first power switch as the inverted frequency-variable PWM control signal; a third driver circuit, which is designed as a single or multi-stage level converter, to adapt the signal level of the TTL/CMOS control signal to the signal level of the third power switch and to supply the adapted control signal to the first power switch as the frequency-variable PWM control signal; and
  • each of the first, second, third and fourth driver circuits can have a plurality of resistors, diodes and transistors and be set up to coordinate the charging and discharging of the gate capacitances of the transistors in the individual stages of the level converter in such a way that respective transistor pairs in each stage of the driver circuits, which are connected in series between a DC voltage corresponding to or derived from the low voltage and the reference potential, in a predetermined temperature range in which the drive circuit is operated, preferably around the range -40° C. to 160° C., not simultaneously are conductive.
  • the driver circuits can be constructed identically, so that it can be ensured that the driver circuits exhibit the same behavior in the event of temperature fluctuations, ie that, for example, changes in the rise times and fall times of the signal edges, which are particularly due to the Fluctuations in the resistance values of the resistors at different temperatures are the same in the individual driver circuits.
  • the driver circuit(s) receiving the inverted PWM control signal may alternatively receive the PWM control signal as well.
  • the corresponding driver circuit(s) can comprise an inverter, which first inverts the PWM control signal in order to obtain the inverted PWM control signal.
  • the respective other driver circuit(s) comprise a delay loop for the PWM control signal, which compensates for the delay in the PWM control signal resulting from the inversion.
  • the driver circuit(s) that receive the PWM control signal can also receive the inverted PWM control signal and correspondingly first invert it.
  • the other driver circuit(s) would compensate for the delay in the control signal by inverting it using a delay loop.
  • the PWM control signal can have a duty cycle of 50%, so that the one or more primary-side coils of the transformer can be switched quasi-continuously with the low voltage of the low-voltage source or a DC voltage derived therefrom.
  • the duty cycle of the PWM control signal could alternatively or additionally be reduced in order to prevent these control errors.
  • this could possibly increase the ripple of the secondary-side output voltage of the transformer, so that further rectification measures on the secondary-side circuit side of the drive circuit could become necessary.
  • the drive circuit can have a multi-stage, in particular 3-stage, 4-stage, 5-stage or 6-stage high-voltage cascade, which boosts the output-side AC voltage of the transformer to the DC high voltage.
  • the high-voltage cascade is designed to Transformer to convert into a DC voltage in the high-voltage range, the AC component (AC component) compared to their DC voltage component (DC component) is 4% or less, preferably 3% or less, more preferably 2% or less.
  • the high-voltage cascade can be, for example, a Villard cascade or a high-voltage cascade with full-wave rectification, it being possible for the Villard cascade to be made significantly more compact.
  • each stage of the high-voltage cascade can include a series connection of a plurality of diodes and a series connection of a plurality of capacitors, which are designed as discrete components. In this case, the number of necessary discrete components is significantly lower in a Villard cascade compared to a high-voltage cascade with full-wave rectification.
  • the drive circuit also has an impedance matching circuit.
  • the impedance matching circuit can be connected between the two outputs of the secondary-side coil of the transformer of the drive circuit and the inputs of the high-voltage cascade.
  • the impedance matching circuit is used to match the impedance between the power switches of the drive circuit, the transformer of the drive circuit and the high-voltage cascade of the drive circuit.
  • control circuit also has an input stage which is connected to the DC voltage source, the input stage comprising a common-mode choke and/or a filter which are set up to attenuate conducted interference from the transformer and/or from the DC voltage source into the Control circuit to limit current flowing.
  • control circuit also includes an input stage that includes a filter, the output of the filter providing a direct voltage derived from the low voltage of the DC voltage source, which is applied to the primary-side coils of the transformer of the control circuit.
  • Another aspect of the invention relates to the design of a circuit board that implements a control circuit according to the invention.
  • this aspect relates to the discrete construction of at least the high-voltage part of the drive circuit.
  • the complete drive circuit can also be constructed discretely.
  • Another embodiment therefore relates to a circuit board on which a drive circuit is implemented with discrete components.
  • the drive circuit has a low voltage part and a high voltage part implemented on the circuit board.
  • the circuit board can have a substantially rectangular shape, but the invention is not limited to rectangular shapes of the circuit board.
  • the circuit board extends in a longitudinal and transverse direction, and the circuit board has an upper area in which the high-voltage part of the drive circuit is implemented and a lower area in which the low-voltage part of the drive circuit is implemented. having.
  • a transformer of the drive circuit can be installed at a point on the circuit board that defines the transition between the low-voltage part and the high-voltage part of the drive circuit. Viewed in the longitudinal direction of the board, the transformer can be arranged on one side of the board in a border area between the upper (high-voltage) area and the lower (low-voltage) area of the board.
  • the remaining portion of the board has a longitudinally extending slot at the boundary between the top (high voltage) and bottom (low voltage) areas of the board, separating the top of the board from the bottom of the board to avoid potential leakage paths for leakage currents between the upper (high-voltage) area and the lower (low-voltage) area of the circuit board. This makes it possible to prevent leakage currents and/or arcing from the high-voltage part of the control circuit to the low-voltage part of the control circuit.
  • the control circuit comprises a high-voltage cascade, which is implemented in the upper area of the circuit board using discrete components.
  • the high voltage cascade consists of a plurality of capacitors and diodes, with a portion of the capacitors being arranged in a capacitor strip at an upper edge of the top portion of the board and another portion of the capacitors being arranged in a longitudinally extending capacitor strip at a lower edge of the top portion of the board which is adjacent to the longitudinally extending slot in the board.
  • the diodes of the high voltage cascade are arranged in a plurality of transverse diode strips between the bottom edge and the top edge of the top portion of the circuit board.
  • the circuit board has cut-outs between the respective diode strips and the capacitor strips at the bottom edge and at the top edge of the upper area To prevent leakage currents and / or arcing between the diodes and capacitors of the high-voltage cascade of the drive circuit.
  • groups of discrete diodes are connected in series in a zigzag arrangement in each diode strip, with slots in the circuit board extending from the recesses between the individual discrete diodes of the groups to prevent leakage currents and/or arcing between the discrete prevent diodes.
  • the anodes and cathodes of the discrete diodes in the groups extend in the longitudinal direction.
  • the slots emanating from the recesses also extend longitudinally in the circuit board between adjacent diodes.
  • the capacitors can be arranged in groups in the capacitor strips at the lower edge and at the upper edge of the upper area, with the circuit board having a transverse slot between the two poles of each discrete capacitor in order to prevent leakage currents and/or prevent arcing between the two poles of the discrete capacitors.
  • one of the diode strips is arranged in the longitudinal direction next to the transformer.
  • the board has a transverse slot extending between the one diode strip and the transformer to prevent leakage currents and/or arcing between the diodes of the one diode strip and the secondary side terminals of the transformer in the high voltage part of the drive circuit .
  • slots in the circuit board can extend in the longitudinal direction between the adjacent discrete diodes of one diode strip in order to prevent leakage currents between the discrete diodes of one diode strip.
  • the board has a further slot in the lower area of the board on an output side of the high-voltage cascade, which is essentially at least partially parallel to the longitudinally extending slot in the board, which separates the upper area of the board from the lower area of the Circuit board separates, runs.
  • This additional slot can be from one of the circuit boards on the output side of the high-voltage cascade delimiting edge in the lower area of the circuit board and extend away from the edge. The further slot can thus interrupt the edge of the circuit board.
  • an essential aspect of this invention is to improve room air cleaners, as are known in particular from patent application WO 2021/224017 Ai.
  • an electronic control should be proposed in order to ensure sufficient cleaning results on the one hand with regard to the use of a liquid that wets the counter-electrode and on the other hand the high demands on the safety of the people in the room to be cleaned.
  • this aspect of the invention relates to a device that is independent and/or can be combined with a control circuit described herein, namely a room air cleaner, and a method for treating, in particular humidifying, cleaning and/or washing air.
  • This device can be an air humidifier, an air purifier, an air washer, or the like.
  • These generic room air cleaners are used to condition, in particular to humidify, clean and/or wash air that is present in closed rooms and/or buildings.
  • This air treatment device can have numerous areas of application, for example in medical technology or in the health industry, especially in doctor's offices, isolation rooms, sick rooms, intensive care units or clean rooms, in private households, especially in bedrooms, living rooms, kitchens or children's rooms, in public buildings and industrial buildings such as museums, theaters , Government buildings, offices, classrooms, and/or universities, and/or in mobility, for example for cleaning vehicle interiors, in particular for taxis, rental cars, vehicle sharing concepts.
  • the so-called room air cleaners are standing devices and/or small electrical devices that can be placed in buildings or rooms on the floor or on shelves such as tables and that do not exceed a weight of 15 kilograms.
  • a particularly effective cleaning of room air is achieved by using so-called air cleaners with electrostatic precipitator technology, in which a liquid reservoir is also provided in order to wet the counter-electrode of the electrostatic precipitator with a flowable mass, such as a liquid, at least partially, in particular completely, in particular to wash around
  • a flowable mass such as a liquid
  • the particles electrically charged by the electrostatic precipitator are attracted by its counter electrode and can thus be the wetting of the liquid on the counter-electrode, which can in particular be designed as a continuously flowing liquid film, and transported away, in particular while the air flow cleaned of it is carried on separately and finally released back into the environment.
  • the liquid is generally a free-flowing flushing and/or collector medium, for example water, in particular also rainwater, a hygroscopic collecting material, for example sodium hydroxide dissolved in a liquid, a gel which is heated to a specific temperature, for example , So that a liquid state of aggregation is reached, such as a wax or the like, an ionic liquid, such as molten or dissolved salts, or highly viscous oils, which are mixed with electrically conductive particles, such as copper, are used.
  • the liquid can have a predetermined minimum electrical conductivity, for example at least 0.005 S/m.
  • the liquid reservoir can be designed as a local liquid reservoir.
  • the liquid reservoir is part of and/or directly associated with the room air cleaner as opposed to a separate liquid reservoir or supply.
  • the liquid reservoir is arranged below the electrostatic precipitator.
  • the liquid can then be pumped upwards with a pump, for example to the top of the counter-electrode, and then return to the liquid reservoir via the counter-electrode in a structurally simple manner using the force of weight.
  • the particles separated by the electrostatic precipitator can be entrained by the liquid, transported to the liquid reservoir and collected there.
  • the device according to the invention comprises an electrostatic precipitator, as is described in particular above.
  • the electrostatic precipitator includes an emission electrode assembly consisting of a plurality of emission needles, and a counter electrode.
  • the emission electrode arrangement and the counter-electrode are electrically coupled to the control device according to the invention.
  • An embodiment of the invention accordingly provides an apparatus, in particular a room air cleaner, for treating air.
  • This device comprises an electrostatic precipitator with an emission electrode, which is formed from a plurality of emission needles and one of the counter-electrodes, which is formed at a distance from the emission needles and which is at least partially wetted, preferably washed around, by a liquid; and a control unit that operates the electrostatic precipitator.
  • the control unit includes a control circuit that is set up to apply a high voltage, in particular a DC voltage in the high voltage range, to the emission needles of the emission electrode and the counter electrode of the electrostatic precipitator in order to generate DC plasma between the emission electrode and the counter electrode.
  • control circuit comprises a control circuit which is set up to adjust the output power of the control circuit to an operating point based on a measured value of a direct current flowing through the emission electrode via the direct current plasma to the counter-electrode of the electrostatic precipitator to the common reference potential of the control circuit relative to the reference current value set, in which a spark discharge of the DC plasma between the emission needles of the emission electrode and the counter electrode is prevented.
  • control circuit includes a current measuring unit, the current measuring unit measuring the direct current flowing through the emission electrode via the direct current plasma to the counter-electrode of the electrostatic precipitator to the common reference potential of the drive circuit.
  • control circuit comprises a control unit which receives the measured value of the flowing direct current from the current measuring unit and generates a control signal, the control unit being set up to adjust the frequency of the control signal based on the measured value of the flow through the emission needles of the emission electrode via the direct current plasma to vary the direct current flowing to the common reference potential of the drive circuit and the reference current value in order to regulate the direct current flowing to the common reference potential of the drive circuit and the electrostatic precipitator to the reference current value.
  • control circuit is arranged adjacent to the emission electrode and in particular distally to the counter-electrode.
  • control unit and/or the control circuit drives a fan.
  • Figure i shows an exemplary system structure according to an embodiment of the invention, in which a drive circuit according to an embodiment of the invention is fed from a DC voltage source with a low voltage and converts this into a high voltage in order to charge the emission electrodes and the counter electrode of an electrostatic precipitator with a high voltage ;
  • FIG. 2 shows an exemplary embodiment of the drive circuit of FIG. 1
  • FIG. 3 shows a first exemplary embodiment and circuitry of the circuit breakers of FIG. 2 in order to step up the low voltage on the primary side by means of the transformer;
  • FIG. 4a shows a second exemplary embodiment and circuitry of the circuit breakers of FIG. 2 in order to step up the primary-side low voltage by means of the transformer;
  • FIG. 4b shows a third exemplary embodiment and circuitry of the circuit breakers of FIG. 2 in order to step up the primary-side low voltage by means of the transformer;
  • FIG. 5 shows a first exemplary embodiment of a high-voltage cascade in FIG. 2;
  • FIG. 6 shows a second exemplary embodiment of a high-voltage cascade in FIG. 2;
  • FIG. 7 shows a first exemplary embodiment of one of the driver circuits of the driver in FIG. 2
  • FIG. 8a shows a second exemplary embodiment of one of the driver circuits of the driver in FIG. 2 when the power switches to be driven are PMOS MOSFETs;
  • FIG. 8b shows a second exemplary embodiment of one of the driver circuits of the driver in FIG. 2 when the power switches to be driven are NMOS MOSFETs;
  • FIG. 9 shows a first exemplary embodiment of the regulation of the output power of the drive circuit in FIG. 2 based on the direct current flowing via the emission electrodes to the counter-electrode of the electrostatic precipitator at a reference potential (GND);
  • FIG. 10 shows a second exemplary embodiment of the regulation of the output power of the drive circuit in FIG. 2 based on the direct current flowing via the emission electrodes to the counter-electrode of the electrostatic precipitator to a reference potential (GND) and a measured temperature of the drive circuit;
  • GND reference potential
  • FIG. 11 shows an exemplary front-end filter for use in the power limiter 212 of FIG. 2 in accordance with an exemplary embodiment of the invention
  • FIG. 12 shows an exemplary structure of a transformer according to an embodiment of the invention
  • Figure 13 shows the frequency response of an exemplary transformer according to an embodiment of the invention
  • FIG. 14a shows an embodiment of a circuit board that implements a drive circuit according to an embodiment of the invention
  • FIG. 14b shows the embodiment of the circuit board of FIG. 14a, the components of the one drive circuit shown in FIG. 2 being identified;
  • FIG. 15 shows portions of the circuit board of FIG. 14a and the arrangement of slots and recesses in the circuit board
  • FIG. 16 illustrates, by way of example, the realization of the high-voltage cascade, the impedance matching and the transformer in FIG. 5 on the circuit board in FIG. 14a; and
  • FIG. 17 shows an enlarged view of portions in the high voltage area of the circuit board of FIG. 14a and the arrangement of slots and recesses in the high voltage area of the circuit board;
  • FIG. 18 shows a schematic, perspective sectional view of a detail of an exemplary room air cleaner according to an embodiment of the invention, which contains a control circuit according to an embodiment of the invention.
  • Figure 19 is a schematic sectional side view of the room air cleaner of Figure 18.
  • the invention relates to a control circuit for generating a high voltage which is applied to the electrodes of an electrostatic precipitator.
  • a further aspect is the use of such a control circuit in a device with an electrostatic precipitator.
  • This device can, for example, be an air treatment device, e.g. a room air filter, an air humidifier, an air washer, an air sterilizer, an aerosol filter or a fine dust filter.
  • control circuit can be used in all end devices that separate particles, liquids or impurities from a gas flow using a low-energy plasma.
  • PCT application WO 2021/224017 Ai and patent application DE 10 2021128345.0 by the applicant of Oct. 29, 2021, which describes an air treatment device with an electrostatic precipitator in which the control circuit according to the invention can be used.
  • the disclosure of the PCT application WO 2021/224017 Ai and the disclosure of the patent application DE 10 2021128345.0 is hereby incorporated in its entirety by referencing.
  • An electrostatic precipitator essentially works according to the following principle: release of electrical charges, in particular electrons or positive ions; charging particles that may be present in the air in an electric field; transport of the electrically charged particles to an opposite pole; discharging the charged particles at the opposite pole; and removing the particles from the opposite pole.
  • the principle of charge generation on which the electrostatic precipitator is based can be impact ionization. When a so-called corona onset field strength is exceeded, electrons can be released and interact with the surrounding gas molecules in the air, causing a corona to form. Whether this is a positive or negative corona depends on the high voltage applied to the electrodes.
  • Airborne free Electrons are strongly accelerated in the electrostatic field of the corona, so that a gas discharge can occur. When hitting gas molecules in the air, more electrons can be split off or attached to the gas molecules.
  • the negative charges move within the air treatment device, particularly within the electrostatic precipitator. When a particle-laden air flow enters, the negatively charged charges accumulate on the particles.
  • the negatively charged particles are deflected by the acting electrostatic force of the applied DC voltage field, which can be oriented transversely to the flow direction of the air within the device, and can thus be separated from the air flow.
  • a further aspect and further embodiments of the invention relate to the use of the control circuit according to the invention in devices, in particular air treatment devices with an electrostatic precipitator.
  • the invention relates to the use of such a control circuit in a room air filter, comprising an electrostatic precipitator with an emission electrode, which is formed from a plurality of emission needles and one of the counter-electrodes formed at a distance from the emission needles, which is at least partially wetted by a liquid, preferably washed around it .
  • the embodiments of the invention can in particular air treatment devices with a volume flow rate of the air to be treated (at a CADR of more than 250 inclusive) up to and including 500 m 3 /h, preferably up to and including 350 m 3 /h and more preferably up to and including 300 m 3 /h regarding. Further embodiments may relate to air treatment devices in which the output power of the drive circuit is in the range between 0.5 W and 20 W inclusive, preferably between 0.7 W and 17 W.
  • the drive circuit can generate a high voltage, the amount of the direct component of which is in the range between 8 kV and 17 kV inclusive, preferably between 10 kV and 13 kV inclusive.
  • the DC component of the direct current which the control circuit provides to an electrostatic precipitator is in the range between 0.100 pA and 1.000 pA, preferably in the range between 0.150 pA and 0.400 pA inclusive.
  • the invention is not limited to these power ranges, voltage ranges and/or direct current ranges.
  • the exact operating parameters with regard to power, output voltage and/or output current of the drive circuit result from the field of application of the drive circuit and can vary from the specified areas differ. However, the specified ranges and parameters are typical for the use of the cabin air filter or fine dust filter control circuit.
  • FIG. i shows an exemplary system structure according to an embodiment of the invention.
  • the system includes a control circuit 120 according to the invention, which is fed by a DC voltage source 110 with a low voltage V DC -ext .
  • the DC voltage source 110 can be, for example, a commercially available 12 V direct current (DC) power pack or a battery.
  • the control circuit 120 implements a DC/DC converter that converts the input-side low voltage (or a voltage derived from it voltage into a high voltage.
  • the high voltage is applied to the output side of the emission electrodes 130 and the counter electrode 140 of an electrostatic precipitator to generate a DC plasma between the respective emission electrodes 130 and the counter electrode 140.
  • direct current plasma is used to separate particles/impurities in a gas stream, as is described in detail, for example, in the aforementioned PCT application WO 2021/224017 Ai.
  • the individual emission electrodes 130 can each be connected in series with a series resistor (not shown) in order to limit the current flow through the respective emission electrode 130 .
  • High voltage Vpiasma is a negative DC voltage.
  • the arrow of the direct current I plasma in FIG. 1 and the other figures indicates the technical current flow.
  • the high voltage V plasma it is also conceivable for the high voltage V plasma to be a positive direct voltage that is generated by the drive circuit 120 .
  • the application of a negative DC voltage has the advantage that the separation performance tends to be higher and more ozone is generated, which in turn actively supports air purification.
  • the drive circuit 120 also includes a control loop 122 which regulates the output power of the drive circuit 120 . Included the control circuit 122 regulates the flow on the output side to the electrostatic precipitator direct current to a desired reference current value).
  • the Counter-electrode 140 of the electrostatic precipitator and one end of the secondary-side coil of a transformer in control circuit 120 can, as will be explained in more detail below, be connected to the reference potential (GND) of control circuit 120, so that the direct current I plasma flowing to the reference potential on the output side is detected and can be fed to the control loop 122 as an input variable.
  • GND reference potential
  • the control circuit 120 Based on the measured direct current I plasma , the control circuit 120 varies the frequency f [n] of a control signal with which the power generator in the control circuit 120 controls the primary-side coil(s) of a transformer, so that the desired reference current value is adjusted on the output side and the output power of the control circuit is regulated to the desired value.
  • the cycle time of the control circuit is selected to be very short and is preferably in the range of 5 ms or less, preferably 2 ms or less, more preferably 1 ms or less. The shorter the control cycle, the faster fluctuations in the measured direct current can be detected and corrected.
  • FIG. 2 shows an exemplary embodiment of the drive circuit 120 from FIG. 1.
  • the drive circuit 120 is supplied on the input side by the DC voltage source 110 with a low voltage provided.
  • the low voltage is, for example, in the range of a few 10 V, ie it is preferably 50 V or less inclusive, particularly preferably 20 V or less inclusive.
  • the input voltage is a power limiter 212 of the drive circuit 120 fed.
  • the power limiter 212 contains, for example, a circuit that limits the power consumed by the drive circuit 120, which limits the power flowing into the drive circuit 120, in particular in the event of a short circuit on the output side (e.g. breakdown of the DC plasma), and thus protects its components from destruction. As will be discussed in more detail below in connection with FIG.
  • the power limiter can also have an input filter which, for example, suppresses line-bound interference by means of an EMC filter.
  • the power limiter 212 makes available a low voltage derived from the input voltage.
  • the derived low voltage in the embodiments of the invention is, for example, in the range of a few 10 V, ie it is preferably inclusive 50 V or less, more preferably 20 V or less inclusive.
  • the derived low voltage V' DC ext is defined in relation to the reference potential GND of the drive circuit 120, while the input-side low voltage V DC_ext can also be defined in relation to another reference potential (eg the negative pole of a battery).
  • the power limiter 212 also provides a TTL or CMOS supply voltage V TTL derived from the input low voltage V DC_ext to supply the digital components (e.g. a microprocessor in the control unit 214) and/or more responsive to TTL/CMOS levels Devices/components in the driver 216 or the power switch (e.g., NMOS-based devices/components).
  • Typical voltage values for the TTL or CMOS supply voltage V TTL are, for example, 5.0 V, 3.3 V, 2.5 V, 1.8 V, etc. In principle, it is also conceivable for the power limiter 212 to have different TTL or CMOS - provides supply voltages.
  • the control circuit 122 consists of the "controlled system", which comprises the control unit 214, the driver 216, the power switches 218, the transformer 220, the optional impedance matching 252 and the high-voltage cascade 254, so that between the electrodes 130, 140 of the Electrostatic precipitator a direct current plasma is formed.
  • the control circuit also includes the current measuring unit 256, which measures the controlled variable, the plasma current I plasma , and feeds it back to the controller, the control unit 214.
  • the control unit 214 varies the frequency of the control signals (manipulated variable), which the control unit 214 supplies to the driver 216, based on the measured plasma current I plasma - the control unit 214 can also be set up to adjust the frequency of the control signal based on the value of the plasma current I plasma and the reference current value I Ref (not shown) in order to regulate the direct current I plasma flowing to the common reference potential GND of the drive circuit 120 and the electrostatic precipitator to the reference current value I Ref . If the plasma current I Plasma on the output side increases in comparison to the reference current value I Ref , the control unit 214 reduces the frequency of the control signals.
  • the control unit 214 reduces the frequency of the control signals.
  • the control unit 214 increases the frequency of the control signals.
  • the control unit 214 can be formed, for example, by means of a microprocessor, a discrete circuit or an integrated circuit (e.g. ASIC or programmable logic (e.g. FPGA, PLD, etc.) or combinations of the options mentioned.
  • the control unit 214 generates the control signals and where the control signal is the inverted control signal V PWM (f).
  • the control signals V PWM (f) and the control unit 214 are pulse width modulated signals that have a duty cycle of about 50%, preferably 50%.
  • the control signals have a TTL or CMS signal level that corresponds to the TTL or CMOS supply voltage V TTL .
  • control signals V PWM (f) have a frequency in the range 120.0 kHz to 200.0 kHz inclusive kHz, preferably in the range 130.0 kHz to 170.0 kHz inclusive.
  • the control unit 214 can change the frequency of the control signals regulate in the said area.
  • a predetermined frequency reference value in this range corresponds to the reference current value I Ref .
  • the control unit 214 correspondingly reduces or increases the frequency of the control signals ) and by this Frequency reference value, depending on whether the plasma current I Plasma on the output side increases or decreases relative to the reference current value I Ref .
  • the resonant frequency of the transformer 220 is higher than the frequency of the control signals
  • the resonant frequency of the transformer 220 is preferably in the range of 200.0 kHz to 240.0 kHz inclusive.
  • the resonant frequency of the transformer 220 can only be adjusted exactly with difficulty, since typical frequency responses of a transformer rise or fall sharply in the range around the resonant frequency. As a result, in these “steep” ranges of the frequency response, a small change in the frequency would cause a large change in the output power of the matching circuit 120 or in the plasma current.
  • control signals have a frequency that is as high as possible
  • the linear range of the frequency response of the transformer 220 is, in the example shown, in the range 130.0 kHz to 170.0 kHz inclusive.
  • the control signals are sent to driver 216 in Figure 2 supplied to the drive circuit 120 .
  • the driver 216 serves to drive the signal levels of the control signals PWM (f) PWM (f) to match the power switches 218 that drive the transformer 220 in terms of current and/or voltage.
  • the driver 216 includes a plurality of driver circuits. Two such driver circuits 216-1 and 216-2, which control the corresponding two power switches in stage 218, are shown in FIG. 2 as an example.
  • the driver circuits 216-1, 216-2 retain the relative timing of the control signals a predetermined temperature range in which the control circuit is to be operated. As mentioned at the outset, this temperature range is between ⁇ 40° C.
  • the driver circuits 216-1, 216-2 include one or more stages of level shifters connected in series to convert the control signals to the desired To bring signal level, and with the adjusted control signals and to drive the stage 218 circuit breakers.
  • the driver circuits 216-1, 216-2 maintain the frequency control signals so that the adjusted control signals ) the same frequency (and duty cycle) as the control signals exhibit.
  • the power switches 218 alternately apply the low voltage to the primary-side coil(s) of the transformer 220 so that in the secondary-side coil of the transformer 220, an AC voltage in the high-voltage range is output.
  • the output voltage ⁇ Trafo of the transformer 220 is in the range of 2 kV or more, preferably 2.5 kV or more.
  • This output voltage on the secondary side of the transformer 220 is then passed through an impedance adjustment 252 and rectified by a high-voltage cascade 254 and at the same time converted to the desired output DC voltage V plasma , which can be applied to the emission electrodes 130 and the counter-electrode 140 of the electrostatic precipitator, as in Figure 1 shown.
  • the high-voltage cascade 254 is designed to convert the secondary-side output voltage of the transformer 220 into a DC voltage Vplasma in the high-voltage range, the alternating component (AC component) of which is 4% or less, preferably 3% or less, compared to its direct voltage component (DC component). is less, more preferably 2% or less.
  • the direct voltage component of the direct voltage V plasma at the output of the cascade 254 is, for example, in the range between 8 kV and 17 kV inclusive, preferably between 10 kV and 13 kV inclusive.
  • the direct voltage I plasma at the output of the cascade 254 is a negative voltage, so that the technical current direction of the direct current I plasma is directed towards the cascade 254 .
  • the direct component of the plasma current I plasma that the control circuit 120 can provide to the electrostatic precipitator is, for example, in the range between 0.100 pA and 1.000 pA, preferably in the range between 0.150 pA and 0.400 pA inclusive. Exemplary configurations of the high-voltage cascade 254 are described below with reference to FIGS.
  • the drive circuit 120 also includes a current measuring unit 256, which measures the plasma current I plasma flowing on the output side and feeds it back to the control unit 214 as a controlled variable.
  • the capture of Plasma current Ipiasm is described in more detail with respect to Figures 9 and 10.
  • the driving circuit 120 can be divided into a low-voltage part 210 and a high-voltage part 250 .
  • the high-voltage part 250 includes the secondary-side coil of the transformer 220 and the downstream parts of the drive circuit 120, in particular the impedance matching 252, the high-voltage cascade 254 and the current measuring unit 256.
  • the low-voltage part 210 of the drive circuit 120 includes the power limiter 212, the control unit 214, the driver 216, the power switch 218 and the primary-side coil(s) of the transformer 220.
  • the transformer 220 thus forms the transition from the low-voltage range 210 to the high-voltage range 250.
  • FIG. 3 shows a first exemplary embodiment and interconnection of the circuit breakers 218 of FIG. 2 to the low voltage on the primary side by means of the transformer 220.
  • the transformer 220 includes two primary-side coils that are co-wound and connected in series. The center tap of the coils on the primary side, which is formed at the connection point of the first coil and the second coil, is connected to the low voltage. The respectively The other ends of the two coils are alternately connected to the reference potential GND based on the control signals. control signals are connected to the gate terminal of the power switches 302 and 304, which are formed by NMOS MOSFETs in the exemplary embodiment shown.
  • an impedance adjustment 252 can be provided on the secondary-side coil of transformer 220.
  • this is represented by the capacitance 310, which is connected between the two outputs of the coil of the transformer 220 on the secondary side.
  • This capacitance can be formed, for example, by means of one or more discrete capacitors connected in series.
  • the impedance matching 252 serves the Match impedance between the power switches 218, the transformer 220 under the downstream high voltage cascade 254 to each other.
  • the parasitic impedances, such as winding capacitances or leakage inductances, of the transformer 220 can only be simulated correctly with difficulty and generally have to be determined analytically.
  • the structure of the transformer 220 is not particularly complex, it is preferably designed to match the overall system.
  • FIG. 4a shows a second exemplary embodiment and circuitry of the circuit breakers 218 from FIG .
  • the transformer 220 includes a primary-side coil and a secondary-side coil.
  • the coil on the primary side can also be formed from two coils that are wound in the same direction and connected in series. The coils can be pushed into each other so that the size can be reduced.
  • the circuit breakers 218 include a full bridge (H-bridge) of four circuit breakers 402, 404, 406, 408. It has been shown that the control of the primary-side coil(s) of the transformer 220 with circuit breakers that are interconnected in an H-bridge, conducted interference can be reduced in comparison to the solution shown in FIG.
  • power switches 218 are MOSFETs
  • power switches 402 and 404 are PMOS MOSFETs
  • power switches 406 and 408 are NMOS MOSFETs.
  • the power switches 402 and 408 are in this case supplied by corresponding driver circuits 216 with the control signal driven, while the power switches 404 and 406 from respective driver circuits 216 with the control signal be controlled.
  • the low voltage V′ DC ext is alternately applied to one end of the primary-side coil of the transformer 220, while the respective other end is connected to the reference potential GND.
  • the power transistor 402 and the power transistor 408 are opened, so that the low voltage across the open power transistor 402 on the second End of the primary-side coil is applied and the first end of the primary-side coil is connected via the power transistor 408 to the reference potential GND.
  • the power transistor 404 and the power transistor 406 are open, so that the low voltage V' DC ext over the open Power transistor 404 is present at the first end of the primary-side coil and the second end of the primary-side coil is connected via the power transistor 406 to the reference potential GND.
  • a capacitor may be connected between the gate and source of each of the power switches 402 , 404 , 406 and 408 .
  • this is not shown in FIG. 4a. It has been shown that the use of capacitors between the gate connection and source connection of each of the power switches 402, 404, 406 and 408 can further reduce conducted interference compared to the solution shown in FIG.
  • the drain connection of the power switches 402 and 404 cannot be connected directly to the low voltage V DC ext , but via a filter 412.
  • the filter 412 can in this case conduct interference due to parasitic impedances and the high-frequency switching of the power switches 402, 404, Reduce 406 and 408.
  • the output of the secondary coil of the transformer 220 may be connected to a circuit 252 that matches the impedances of the power switches 218, the transformer 220 and the subsequent high voltage cascade 254.
  • FIG. 4b shows a third exemplary embodiment and circuitry of the circuit breakers 218 from FIG .
  • the design of the control of the coil(s) on the primary side of the transformer 220 corresponds to the design shown in FIG. 4a.
  • the two power switches 402 and 406 are connected by the capacitors 414 and 416, which can have the same capacitance. This creates a virtual ground point 418 between the two capacitors 414 and 416 .
  • the current I prim ⁇ r flowing into the primary-side coil is due to the Creation of the virtual ground point 418 of a triangular voltage with half the frequency f of the drive signals 12 as shown in the figure 4b is shown as an example.
  • the advantage of the embodiment shown in FIG. 4b is that the two capacitors 414 and 416 and the created virtual ground point 418 cause line-related interference can be reduced by the parasitic impedances, in particular the winding capacitances or leakage inductances of the transformer 220.
  • FIG. 5 shows a first exemplary embodiment of a high-voltage cascade 254 in FIG.
  • the output voltage V Trafo of the transformer 220 is present at the input of the cascade 254 .
  • the high voltage cascade 254 includes five stages 502, 504, 506, 508 and 510. Each stage 502, 504, 506, 508 and 510 doubles the AC component of the output voltage V Trafo of the transformer 220.
  • the cascade 254 can be noticeably lossy.
  • the diodes have a relevant reverse current, especially at higher temperatures, and the amplitude of the AC component of the output voltage V Trafo is slightly smoothed. It therefore makes no sense to line up any number of cascade stages.
  • Cascade stages 502, 504, 506, 508 and 510 form a "ladder".
  • Each of the cascade stages 502, 504, 506, 508 and 510 consists of two capacitors and two diodes.
  • the second end 514 of the secondary side coil of the transformer 220 is (as will be explained below) connected to the reference potential GND.
  • the first end 512 of the secondary-side coil of the transformer 220 is connected to the first capacitor of the first cascade stage 502 on the input side.
  • the other end of the capacitor is connected to the anode of the first diode, the cathode of which in turn is connected to the second end of the secondary coil of the transformer.
  • the anode of the second diode of the first cascade stage 502 is connected to the cathode of the first diode of the first cascade stage 502 via the second capacitor of the first cascade stage 502 .
  • the cathode of the second diode is in turn connected to the anode of the first diode and the other end of the capacitor.
  • the other stages 504, 506, 508 and 510 are also constructed accordingly.
  • the output voltage V plasma of the cascade 254 is taken from the anode of the second diode in the last stage 510 of the cascade 254 .
  • the arrangement of the cascade stages 502, 504, 506, 508 and 510 shown generates a negative DC voltage V plasma on the output side.
  • the anode and cathode of the individual diodes in the stages 502, 504, 506, 508 and 510 only have to be swapped with one another.
  • FIG. 6 shows a second exemplary embodiment of a high-voltage cascade 254 in FIG. 2.
  • the high-voltage cascade 254 is designed as a high-voltage cascade 600 with full-wave rectification, which also consists of a number of stages.
  • five cascade stages 602, 604, 606, 608 and 610 are shown as in FIG. 5, but the number of cascade stages is not limited to five here either.
  • the structure of the high-voltage cascade 600 is based on a Villard cascade 500, which is mirrored on the signal path between the second end 514 of the secondary-side coil and the tap of the output voltage.
  • the two cascades 500 and 600 in Figures 5 and 6 differ essentially in the number of their elements, which in the high-voltage cascade 600 with full-wave rectification is almost twice as high as that in the Villard cascade 500.
  • the individual diodes and capacitors which are The two embodiments of the cascades 500 and 600 can be formed by discrete components. In this case, a single diode can be formed by connecting a plurality of discrete diodes in series.
  • the capacitors can also be formed by means of a series connection of discrete capacitors.
  • the embodiment of FIG. 5 appears to be advantageous if the miniaturization of the drive circuit 120 is an important design aspect.
  • FIG. 7 shows a first exemplary embodiment of one of the driver circuits 216-1, 216-2 of the driver 216 in FIG. 2.
  • the control unit 214 provides the control signals are available, each of which is supplied to a driver circuit 216-1, 216-2.
  • the number of driver circuits corresponds to the number of power switches 218.
  • Driver circuits with the control signal and the other driver circuit with the control signal of the control unit 214 is controlled.
  • four driver circuits are provided, two of the driver circuits having the control signals and the other two driver circuits with the control signal of the control unit 214 are controlled.
  • the structure of the driver circuits is identical in the different embodiments. Only the (type of) transistors used in the individual stages of the driver circuits can be designed differently, for example depending on which voltage level is switched or which (type of) power switch controls the respective driver circuit.
  • the mutually corresponding resistors and diodes of the individual stages 700, 720 of the driver circuits can, however, be constructed in the same way. This has the advantage that the effects of fluctuations in the operating temperature on the resistance values and thus the rise times and fall times of signal edges of the driver circuits 216-1, 216-2 are uniform in all driver circuits 216-1, 216-2 and the switching timing is therefore not negative influenced.
  • the reliable operation of the drive circuit 120 over the desired temperature range in which the drive circuit 120 is intended to be operated can thereby be ensured.
  • This also makes it possible in particular to prevent a possible “shoot through” in the individual stages 700, 720 of the driver circuits 216-1, 216-2.
  • resistors which have the same resistance value as one another are denoted by the same value RX.
  • resistors 708, 712, 710, and 730 have the same resistance Ri (eg, 100 ⁇ ), while resistor 728 has resistance R2 (eg, 330 ⁇ ).
  • Identical diodes are also identically designated DX.
  • the diodes 706, 714 and 726 can be constructed in the same way.
  • the driver circuit 216 which is shown in FIG. 7, comprises two driver stages 700 and 720, for example.
  • the two driver stages 700 and 720 in particular amplify the current which is supplied to the gate contact of the power switch 218 so that it switches more quickly.
  • the driver stages 700 and 720 can also raise the voltage level applied to the gate contact of the power switch 218, ie increase it to the voltage value of the rail voltage V TTL or the low voltage t .
  • the first driver stage 700 includes a voltage divider consisting of two parallel circuits, each with a resistor and a diode.
  • the first parallel circuit is formed by the resistor 708 and the diode 706.
  • the second parallel circuit is formed by the resistor 712 and the diode 714.
  • the control signal is fed to the center tap of the voltage divider.
  • the first driver stage 700 also includes a series connection of the PMOS MOSFET 702 with the NMOS MOSFET 704 via the resistor 710, which serves to limit the current.
  • the drain of the PMOS MOSFET 702 is connected to the TTL/CMOS supply voltage V TTL or low voltage tied together. A tap between that of the PMOS MOSFET 702 and the NMOS MOSFET 704 provides the output of the driver stage 700.
  • the anode of diode 706 is connected to the gate of NMOS MOSFET 704 .
  • the cathode of the diode 706 is connected to the center tap of the voltage divider so that the control signal or. at the
  • Cathode of transistor 706 is applied.
  • the anode of diode 714 is connected to the center tap of the voltage divider, so that the control signal F P u/ M (/) or FPIVMC/) is present at the anode of diode 714.
  • the cathode of diode 714 is connected to the gate of PMOS MOSFET 702 .
  • the second driver stage 720 receives the output signal provided at the tap between that of the PMOS MOSFET 702 and the NMOS MOSFET 704 . This output signal is fed to the gate of the PMOS MOSFET 722 .
  • the money terminal of the NMOS MOSFET 724 is connected to the tap between that of the PMOS MOSFET 702 and the NMOS MOSFET 704 via a parallel connection of the diode 726 and the resistor 728 .
  • the output signal of the first driver stage 700 is present at the cathode of the diode 226, while its anode is connected to the gate terminal of the NMOS MOSFET 724.
  • the PMOS MOSFET 722 and the NMOS MOSFET 724 are connected in series across the resistor 730 with a center tap between the PMOS MOSFET 722 and the NMOS MOSFET 724 the output signal provides, with which a corresponding power switch in the stage 218 of the drive circuit 120 is driven.
  • PMOS MOSFET 722 has its drain connected to the TTL/CMOS supply voltage V TTL or low voltage tied together.
  • the individual driver stages 700 and 720 each form a level shifter that converts the signal level of the TTL/CMOS control signal to the Adjust the signal level of the power switch 218 and the adjusted control signal to the power switch 218 as a variable frequency PWM control signal.
  • Whether the transistors 702 and 722 are connected to the TTL/CMOS supply voltage V TTL or the low voltage can depend, for example, on whether the power switch 218 to be driven is a PMOS-based or an NMOS-based power switch. Since PMOS-based power switches usually require a higher gate voltage due to their higher gate capacitance in order to achieve short switching times, it makes sense, sometimes even necessary, to use at least the last driver stage (here driver stage 720) with the low voltage connect to.
  • the other driver stages can either be connected to the TTL/CMOS supply voltage V TTL or the low voltage, depending on the structure of the driver stage.
  • the diodes 706 and 714, or 726 allow the discharge of the gate capacitance at the gate connection of the NMOS transistors 704 and 724 can take place quickly and thus the charging of the gate capacitance of the PMOS transistors 702 and 722 and their Switching time is accelerated. Due to the reverse direction of the diodes, the money capacitance of the NMOS transistors 704 and 724 is charged via the resistors 708 and 712 or 728.
  • This circuit arrangement allows the switching times of the PMOS transistors 702 and 722 and the NMOS transistors 704 and 724 be matched so that a "shoot through" of the transistor pairs in each of the driver stages 700, 720 can be prevented.
  • FIG. 8a shows a second exemplary embodiment of one of the driver circuits 216-1, 216-2 of the driver 216 in FIG. 2 when the power switch 218 to be driven is a PMOS MOSFET.
  • FIG. 8b shows a second exemplary embodiment of one of the driver circuits 216-1, 216-2 of the driver 216 in FIG. 2 when the power switch 218 to be driven is an NMOS MOSFET.
  • the two embodiments of driver circuits 216-1, 216-2 of driver 216 in FIGS. 8a and 8b can therefore be considered a further development of the driver circuit in FIG.
  • driver stages 800, 700, 720 both contain a cascade of driver stages 800, 700, 720, with the driver stage 800 being added on the input side in comparison to FIG.
  • Driver stages 700, 720 in FIGS. 8a and 8b essentially correspond to driver stages 700, 720 in FIG. 7.
  • power switch 218 is a PMOS-based switching element.
  • the transistors 702 and 722 in the driver stages 700, 720 are connected to the low voltage t with their source connection.
  • the source connection of the PMOS transistor 722 can be connected to the reference potential GND via a filter capacitor (C2).
  • the additional input stage 800 of the driver circuit 216-1, 216-2 in FIGS. 8a and 8b implements a level converter which converts the TTL/CMOS voltage of the control signal using the operational amplifier circuit. Due to the high-impedance input of the operational amplifier 802, to which the control signal is connected via the resistor 804 is, it can be prevented that suddenly occurring overvoltages or current peaks in the subsequent stages 700, 720 can damage the control unit 214.
  • the output of the operational amplifier 802 is connected to the center tap of the input-side voltage divider of the driver stage 700, which consists of a parallel circuit of the diode 706 with the resistor 708 and a parallel circuit of the diode 714 with the resistor 712. As already explained in connection with FIG. 7, it is advantageous if all driver circuits 216-1, 216-2 are designed to be structurally identical.
  • FIG. 9 shows a second exemplary embodiment of the current measurement unit 256 for determining a current measurement value, based on which the output power of the control circuit 120 in FIG. 2 is regulated.
  • the measured current value gives the value via the emission electrodes 130 to the counter electrode 140 of the electrostatic precipitator to a reference potential GND flowing direct current Ipiasma.
  • the counter-electrode 140 of the electrostatic precipitator is connected to the reference potential GND. To the direct current flowing in the electrostatic precipitator I piasma .
  • the secondary-side coil more precisely the second end 514 of the secondary-side coil of the transformer 220, is connected to the reference potential GND via a voltage divider formed from the resistors 902 and 904.
  • the direct current Ipiasma- is thus measured on the secondary side of the transformer 220 in the embodiment of the invention.
  • resistors 902 and 904 have the same resistance R6. Because of Kirchhoff's rules, the plasma current I plasma flows through the voltage divider because of this connection, so that a measurement voltage V measurement drops at the center tap between the resistors 902 and 904, which voltage represents the plasma current I plasma .
  • the measuring unit 256 Since the measuring unit 256 is connected to the center tap of the voltage divider with a very high resistance (cf. operational amplifier 918), only a negligible current flows into the measuring unit 256.
  • the measuring unit 256 here includes, for example, an input-side RC element (low-pass filter) made up of the resistors 910 and the Capacitor 912 and ESD protection formed by diodes 914 and 916.
  • the potential at the center tap of the voltage divider between the resistors 902 and 904 is therefore present at the non-inverting input of the operational amplifier 918—because of the negligible current in the measuring unit 256.
  • the interconnection of the 918 operational amplifier implements a gain buffer or unity gain buffer.
  • control unit 214 includes A/D converter 924. As previously mentioned, control unit 214 may be implemented as a microprocessor.
  • the control cycle of the control circuit 122 is preferably in the range of 5 ms or less, preferably 2 ms or less, more preferably 1 ms or less. The shorter the control cycle, the faster fluctuations in the measured plasma current I plasma can be detected and corrected. In one embodiment, the control cycle is 1 ms. Accordingly, the control unit 214 adjusts the frequency value f[n] at intervals of 1 ms to the respective measured current value /[n] in order to adjust the output power of the control circuit 120, or its output current I plasma , to a reference output power or a reference current value I ref regulate.
  • FIG. 10 shows a second exemplary embodiment of the current measurement unit 256 for determining a current measurement value, based on which the output power of the drive circuit 120 in FIG. 2 is regulated.
  • the control unit 214 also takes a temperature reading into account.
  • the measured current value indicates the direct current I piasma flowing via the emission electrodes 130 to the counter-electrode 140 of the electrostatic precipitator to a reference potential GND.
  • the embodiment of FIG. 10 is based on the embodiment of FIG. 9.
  • the current measuring unit 256 in FIG. 10 corresponds to the current measuring unit 256 in FIG. 9.
  • the control unit 214 receives a measured temperature value T[t].
  • This can, for example, be converted into a digital temperature measurement value T[n] using a further A/D converter (not shown in FIG. 10).
  • This additional AD converter can also be integrated into the control unit 214, for example.
  • the measured temperature value can, for example, measure the temperature in the vicinity of the circuit board on which control circuit 120 is implemented.
  • the temperature sensor can optionally also be a component of the control circuit 120 .
  • the temperature can be recorded at various points on the circuit board or on the end device in which the control circuit 120 is installed.
  • Different temperatures can also be recorded at different points on the circuit board or on the end device in which the control circuit 120 is installed, and the control unit 214 in be supplied in analogue/digital form.
  • the control unit 214 can use the one or more measured temperature values that it receives in different ways to regulate the output power of the drive circuit 120 .
  • the control unit 214 could use this, for example, to vary the duty cycle of the control signals, so that the duty cycle is not 50% but slightly more or slightly less.
  • control unit 214 uses the measured temperature(s) to adjust the frequency f[n] of the control signals taken into account together with the measured current value /[n]. For example, in one embodiment, the control unit 214 could reduce the input power of the transformer 220 when a critical temperature, for example of the transformer 220, is measured in order to protect the circuit 120 from overload. The efficiency of the transformer 220 typically decreases as the core material approaches its Curie temperature.
  • the controller 214 is configured to detect a thermal runaway based on the temperature reading representing the temperature of the transformer 220 (e.g., by comparison to a forgiving threshold temperature chosen based on the Curie temperature of the transformer 220 , and detecting exceeding the threshold temperature) and reducing the input power of the transformer 220, for example by changing the duty cycle of the control signals PWM (f) b PWM (f) and/or by reducing the frequency f[n] of the control signals so that thermal runaway occurs can be prevented.
  • one or more temperature sensors may sense the temperature of the diodes in the cascade 254 (if multiple temperature sensors, at different locations of the cascade 254).
  • the control unit 214 receives the temperature readings of the one or more temperature sensors and can detect an imminent thermal runaway based thereon (eg, by comparing to a forgiving threshold temperature and detecting an exceeding of the threshold temperature). If thermal runaway is imminent, the control unit 214 can reduce the input power of the transformer 220, for example by changing the duty cycle of the control signals and/or by reducing the frequency f[n]. the control signals , so that thermal runaway can be prevented
  • control circuit 120 could be switched off in an emergency, in that the control unit 214 suppresses the control signals, if or as long as the threshold temperature is exceeded.
  • FIG. 11 shows an exemplary front-end filter 1100 for use in the power limiter 212 of FIG. 2 according to an exemplary embodiment of the invention.
  • the input filter 1100 includes a common mode choke (“common mode choke”) with a plurality of windings wound in the same direction. The current from the DC voltage source 110 flows through the windings. The magnetic fields in the core cancel each other out, so that interference currents on the forward and return lines are dampened.
  • the input filter includes an EMC filter 1104 that conducts EMC interference due to the parasitic impedances of the transformer 220 are filtered.
  • the EMC filter 1104 can be implemented using an H filter or a T filter, for example, and can be adapted to the implementation-specific interference.
  • the input filter 1100 can, for example, at its output, the derived low voltage t and provide the reference potential GND.
  • the reference potential GND is separated from the external ground by the filter circuit 1104 and the common mode choke 1102 .
  • Filter circuit 1104 and common mode choke 1102 are only effective for high-frequency signals, so that the DC plasma current I plasma is not influenced by filter circuit 1104 and common mode choke 1102 .
  • the direct current component of the low voltage can therefore also correspond to the input voltage.
  • the power limiter 212 changes the level of the DC component of the input voltage, for example by changing the reference potential GND compared to the reference potential (e.g. external ground) of the DC voltage source no and/or change in the DC voltage level of the input voltage t .
  • control unit 214 provides the control signals ready. Basically, it is also conceivable that the control unit 214 only the control signal provides. In this case, individual driver circuits 216-1, 216-2 that require an inverted version of this control signal could have an inverter to convert the control signal to create. The other driver circuits 216-1, 216-2 which drive the non-inverted control signal could also include a delay loop to compensate for the propagation delay into the inverters of the other driver circuits 216-1, 216-2. A further possibility is that the operational amplifier 802 is connected in the stage 800 of the driver circuits 216-1, 216-2 in such a way that the operational amplifier 802 transmits the control signal inverted.
  • stages 700 and 720 of the driver circuits 216-1, 216-2 in the described embodiments the inverted control signal need, transistor pairs of each stage 700, 720 (eg, transistors 702 and 704, and transistors 722 and 724) not between the positive TTL / CMOS supply voltage V TTL and the derived positive low voltage t and the reference potential GND, but are connected between the reference potential GND and a negative TTL/CMOS supply voltage -V TTL or a derived negative low voltage.
  • a further aspect of the invention relates to the design of the transformer 220 so that it can be implemented as compactly as possible.
  • the transformer 220 has a housing with a rectangular or square basic shape.
  • the edge length of this basic form is, for example, between 30 mm and 18 mm inclusive.
  • the transformer 220 may include an EFD20 package.
  • the secondary-side coil 1218 of the transformer 220 can be arranged in a plurality of chambers of the transformer housing 1228 that are insulated from one another by means of a dielectric material.
  • FIG. 12 shows an exemplary structure of a transformer 220 according to an embodiment of the invention.
  • the transformer can be divided into a primary side and a secondary side, the primary side includes, among other things, and for example one or more primary-side coil(s), here by way of example two coils 1206, 1212.
  • the primary side can be the low-voltage part of the Control circuit 220 may be assigned.
  • the secondary side in turn includes, among other things, the secondary-side coil 1218 .
  • the transformer 220 includes the transformer housing 1228, which can also be referred to as a bobbin. This is made of an insulating material.
  • the transformer 220 comprises two primary-side coils 1206 and 1212.
  • the first coil 1206 has the connections 1208 and 1210, the first connection 1208 also being the first end 1208 of the primary-side coil 1206 and the second connection 1210 also being the second End 1210 of primary-side coil 1206 is designated.
  • the second coil 1212 also has two terminals 1214 and 1216 . Terminals 1214 and 1216 are also referred to as first end 1214 and second end 1216 of coil 1212, respectively.
  • the second end 1210 of the coil 1206 and the first end 1214 of the second primary-side coil 1212 can be short-circuited with one another or short-circuited on the circuit board (see FIGS. 3, 4a and 4b).
  • the coils 1206 and 1212 are wound in the same direction. If the coils 1206 and 1212 are connected in series, the multiplication factor of the transformer 220 is halved.
  • the secondary-side coil 1218 of the transformer 220 is divided into three partial coils 1218-1, 1218-2 and 1218-3 in the exemplary embodiment shown in FIG. Each of these partial coils is arranged in a chamber 1224 - 1 , 1224 - 2 , 1224 - 3 of the transformer housing 1228 .
  • the individual chambers 1224-1, 1224-2, 1224-3 are separated from one another by partition walls 1226-1, 1226-2, 1226-3, or from a chamber 1230 containing the coils 1206 and 1212 on the primary side. It should be pointed out that three chambers 1224-1, 1224-2, 1224-3 for accommodating the partial coils 1218-1, 1218-2 and 1218-3 of the secondary-side windings of the coil 1218 are shown here merely as an example. However, the windings of the secondary-side coil 1218 can also be arranged in more or fewer chambers, for example two chambers, four chambers, five chambers, six chambers, seven chambers, eight chambers, etc. Chambers 1224-1, 1224-2, 1224-3 and 1230 may also be referred to as housing sections.
  • the division of the windings of the secondary-side coil 1218 into a plurality of chambers 1224-1, 1224-2, 1224-3, which are insulated from one another, makes it possible to reduce the potential differences between the winding layers. This makes it possible to reduce the thickness of the insulation around the individual conductors of the secondary-side coil 1218, which in turn enables a more compact design of the Transformer 220 allows. This also makes it possible to manufacture the transformer 220 using industrial processes. In previously used, hand-made transformers 220, the individual sub-coils 1218-1, 1218-2 and 1218-3 of the secondary-side windings of the coil 1218 were insulated from one another by means of insulating foils inserted by hand.
  • the outputs 1220 (512) and 1222 (514) of the secondary-side coil 1218 output the AC voltage V Trafo of the transformer 220 induced in the secondary-side coil 1218 .
  • the outputs 220 (512) and 1222 (514) of the secondary side coil 1218 are connected to the impedance matching 252 and the high voltage cascade 254 as shown in FIG.
  • the transformer 220 further includes two E-shaped interconnected cores of conductive material which transport the induced magnetic field.
  • the cores can be made of iron, for example, but other materials, in particular soft magnetic materials, can also be used.
  • the number of turns of the primary-side coils 1206 and 1212 of the transformer 220 is between 13 turns and 18 turns inclusive
  • the number of turns of the secondary-side coil 1218 of the transformer 220 is between 700 turns and 800 turns inclusive.
  • the number of turns of the coils 1206 and 1212 is 15 each and the number of turns of the secondary side study 1218 is 750.
  • FIG. 13 shows the frequency response of an exemplary transformer 220 according to an embodiment of the invention.
  • the x-axis designates the frequency, while the amount of the magnetic flux in the transformer 220 designates on the y-axis.
  • the resonant frequency of the transformer 220 is preferably in the range of 200.0 kHz to 240.0 kHz inclusive.
  • the resonant frequency of the transformer 220 is fixed at 230.0 kHz due to the design.
  • the control frequency of the control signals PWM f) PWM f) is therefore, for example, in a range of 130 kHz and 170 kHz inclusive.
  • a further aspect of the invention relates to the design of a circuit board that implements an am drive circuit according to the invention.
  • this aspect relates to the discrete construction of at least the high-voltage part of the drive circuit 120 on a circuit board and the use of such a circuit board in a room air cleaner, the room air cleaner having an electrostatic precipitator with an emission electrode formed from a plurality of emission needles and one of the emission needles at a distance formed, counter-electrode, which is at least partially wetted by a liquid, preferably flushed.
  • the complete drive circuit can also be constructed discretely.
  • FIG. 14a shows an embodiment of such a circuit board 1400, which implements a drive circuit 120 according to an embodiment of the invention.
  • the board shown extends lengthwise by about 140 mm and by about 70 mm in the transverse direction.
  • FIG. 14b shows the embodiment of the circuit board from FIG. 14a, the components of the one drive circuit 120 shown in FIG. 2 being identified.
  • the high-voltage cascade 254 is arranged in an upper region of the circuit board 1400 viewed in the transverse direction.
  • On the longitudinally right side is the transformer 220 with the secondary side coil 1218 oriented transversely upward.
  • a plurality of discrete capacitors connected in series that implement impedance matching 252 are shown at the upper right edge of circuit board 1400 .
  • the structure of the high-voltage cascade using the individual discrete components shown is illustrated in FIG.
  • the components of the low-voltage part 210 of the control circuit 120 can be found in the lower area of the circuit board 1400 .
  • the lower section of the board includes the power limiter 212 with the input filter.
  • connection pins, plugs or the like
  • the connection for the low-voltage source 110 is also provided in the vicinity of the input filter.
  • the measuring unit 256, the control unit 214, as well as the driver 216 and the circuit breaker 218 can also be found in the lower area of the circuit board.
  • FIG. 15 shows partial areas of the circuit board of FIG 1400 should penetrate completely and prevent arcing between the individual components of the high-voltage part 250, or from the high-voltage part 250 into the low-voltage part 210 and/or the leakage current paths (see arrows 1720, 1722 in FIG. 17) from extending in such a way that no harmful leakage currents, that can form on the surface of the circuit board, damage the components of the drive circuit 120 and/or the DC power source 110 connected to the circuit board 1400.
  • the control unit 214 in particular can react sensitively to overvoltages.
  • the board 1400 can be divided into a high-voltage area 1502 in the upper area of the board and a low-voltage area 1504 in the lower area of the board.
  • the transformer 220 is attached to one side, here the right side (in the longitudinal direction) of the circuit board 1400 and represents the transition between the low-voltage area 1504 and the high-voltage area 1502.
  • a boundary area 1506 is defined between the high-voltage area 1502 and the low-voltage area 1504, which extends substantially in the longitudinal direction of the board.
  • a slot 1510 is formed in this border area 1506, starting next to the transformer 220 and extending substantially the remaining width of the circuit board 1400 longitudinally.
  • this slot 1510 does not break through the edge of the circuit board 1400 opposite the transformer 220 so that the circuit board 1400 maintains its stability. Slot 1510 penetrates board 1400 completely. In the exemplary embodiment shown, the slot 1510 has a width of approximately 3 mm, so that it can reliably prevent leakage currents from spreading from the high-voltage area 1502 into the low-voltage area 1504 . Furthermore, this slot 1510 extends possible leakage current paths (see e.g. arrow 1720 in Figure 17) from the high-voltage area 1502 to the low-voltage area 1504.
  • the high-voltage cascade 254 of the drive circuit 120 is implemented by means of discrete diodes and capacitors.
  • the output of the high-voltage cascade 254 is in the left-hand area 1520 of the high-voltage area 1502. The highest voltages are therefore to be expected there.
  • the voltage level increases from the high voltage V Trafo at the output of the transformer 220 in the high voltage range 1502 to the output value v PLAsma at the end of the cascade 254.
  • the high voltage cascade 254 corresponds to in 5.
  • the capacitors are placed in a longitudinally extending, strip-shaped area 1516 at the upper edge of the high-voltage area 1502 and in a longitudinally extending, strip-shaped area 1514 at the lower edge of the high-voltage area 1502.
  • the capacitors of the high-voltage cascade 254 are implemented by connecting groups of capacitors in series. In the embodiment shown on board 1400, each of these groups consists of four capacitors, but the invention is not so limited.
  • the diodes 1704 of the cascade 254 are also formed by a series connection of individual discrete diodes 1704 . Each diode of the cascade 254 is implemented in the embodiment shown in FIG.
  • diodes 1704 are connected in a zigzag or meandering pattern, as can be seen, for example, from the enlarged representation in FIG.
  • the diode strips 1518 extend in the transverse direction between the strip-shaped areas 1514 and 1516 in which the capacitors of the cascade 254 on the circuit board 1400 are mounted. Between the individual adjacent diode strips 1518 there are cutouts 1524 in the circuit board 1400 (not all cutouts are marked with reference symbols in FIG. 15 in order to promote clarity).
  • a slot 1522 Adjacent to the diode strip 1518 which is formed immediately adjacent to the transformer 220 on the circuit board 1400, a slot 1522 is also formed in the circuit board 1400.
  • FIG. This extends essentially in the transverse direction. At the transversely upper end of the slot 1522, it may extend longitudinally, such as in the illustrated embodiment where the slot 1522 is generally T-shaped. The lengthening of the slot 1522 in the longitudinal direction serves to increase the length of the creepage current path (see, for example, arrow 1720 in FIG. 17), so that the risk of damage to components in the low-voltage area 1504 of the circuit board 1400 by creepage currents can be reduced.
  • FIG. 17 shows an enlarged view of partial areas in the high-voltage area 1502 of the circuit board 1400 of FIG. 14a and the arrangement of slots 1702, 1706 which break through the circuit board and recesses 1524 in the High-voltage area 1502 of circuit board 1400.
  • a group of series-connected capacitors from high-voltage cascade 254 in high-voltage area 1502 is shown in FIG.
  • the capacitors extend in the longitudinal direction, ie the two connections 1710, 1712 of each capacitor as well as the conductor tracks for connecting the capacitors of the group extend in the longitudinal direction.
  • a slot 1702 is provided below each capacitor in the board 1400 between the two terminals 1710, 1712 to which each of the discrete capacitors is connected to the board (e.g. soldered), so that the propagation of leakage currents between the respective terminals 1710, 1712 of each capacitor is prevented as far as possible.
  • the slots 1702 extend in the transverse direction and protrude in the transverse direction on both sides beyond the housing of the respective capacitor.
  • the diodes 1704 are connected to one another in a zigzag shape on the circuit board 1400, i.e. the cathodes of a diode 1704 (except for the last diode in the diode strip 1518) is connected to the anode of the next diode 1704.
  • the diodes 1704 are implemented as discrete components. Their anode and cathode extend essentially in the longitudinal direction.
  • each diode 1704 extend substantially in the transverse direction to form a zigzag pattern.
  • a recess 1524 is provided between adjacent diode strips 1518 .
  • further slots 1706 extend in the longitudinal direction of the board 1400 between adjacent diodes 1704 in order to prevent the propagation of leakage currents between the adjacent diodes 1704 within the respective diode strips 1518 as far as possible.
  • Corresponding slots 1706 in the longitudinal direction of circuit board 1400 also extend, starting from cutouts 1524, above and below the first and last diode of each diode strip 1518, as is also shown in the detail enlargement in FIG.
  • slots 1706 also extend from the slot 1522 between the individual adjacent diodes 1704 of the diode strip 1518 lying next to the transformer 202 .
  • a further slot 1512 extends in the circuit board 1400 below the slot 1510 and is located at least in part in the area of the power limiter 212. In the embodiment shown, this slot 1512 extends from the edge of circuit board 1400 and breaks the edge. In the exemplary embodiment shown, the slot 1512 extends (approximately) in the area of the input filter 110 in which the connection of the DC voltage source 110 is also located.
  • the slit 1512 is formed at least partially in the longitudinal direction of the circuit board 1400 .
  • No components of the drive circuit 120 are provided in the area between the slot 1510 and the slot 1512 or attached to the circuit board 1400 .
  • the slot 1512 lengthens the leakage current path between the output area 1520 of the cascade 254 and the connection of the DC voltage source 110 on the circuit board 1400 (in the area of the input filter 1100), so that the external DC voltage source 110, which is connected to the circuit board 1400 or control circuit 120, can be better protected against leakage currents.
  • FIG. 18 shows an exemplary embodiment of a section of a room air cleaner 1 according to the invention, illustrated in a schematic sectional view, which contains a control circuit 120 according to an embodiment of the invention.
  • the control circuit 120 can be part of a control unit of the room air cleaner 1 that controls and/or operates the room air cleaner 1 .
  • the control circuit 120 can be implemented on a separate board 1400 .
  • the control circuit 120 can also be part of a circuit board that implements further control functions of the room air cleaner 1 .
  • the room air cleaner 1 has a rotary design and comprises the following main components: A control circuit 120 according to one of the previously described embodiments of the invention, an electrostatic precipitator 3 for separating liquid and/or solid particles from the air to be treated with a rotary counter-electrode 5 (that of the counter-electrode 140 in the previously described embodiments of the invention) and an emission electrode 7, which in the exemplary embodiment is an array of emission electrode needles 9 (corresponding to the emission electrodes 130 in the previously correspond to the described embodiments of the invention) which is arranged above the rotary-shaped counter-electrode 5 .
  • the control circuit 120 provides the electrostatic precipitator with a DC voltage V Piasm in the high-voltage range, which is applied and regulated to the counter electrode 5 and the emission electrode 7, in particular the array of emission electrode needles 9, when the room air cleaner 1 is in operation.
  • the main components of the room air cleaner 1 may further include: a liquid reservoir 11; a liquid conveyor 13 connected to the liquid reservoir 11 for wetting the counter-electrode 5 with liquid from the liquid reservoir 11; a rotary air duct 15 for supplying the air to be treated to the electrostatic precipitator 3 and for conveying the air cleaned by the electrostatic precipitator 3 to a deflection body 17 which is arranged downstream of the electrostatic precipitator 3 in the center of rotation of the air cleaner 1 or the air duct 15, which directs the cleaned air against the Gravity direction, i.e. upwards, deflects in order to discharge the cleaned air back into the environment via a flow outlet 26; and a fan 27 for generating airflow through the room air cleaner 1.
  • the fan 27 can be controlled by a control unit of the room air cleaner 1.
  • the liquid reservoir 11 is arranged below the other components of the room air cleaner 1.
  • the liquid feed 13, the counter-electrode 5, the deflection body 17, the emission electrode 7 and the fan 27 are arranged above this from bottom to top.
  • the components are housed in a housing 67 made up of several parts.
  • the outside of the air cleaner 1 is formed by a cylindrical housing part 69 and the top by a disk-shaped housing part.
  • the housing part 69 and the further housing part can also be designed in one piece.
  • the housing 3 can also have a connection for an external DC voltage source 110, which can be connected to the control circuit 120 of the room air cleaner 1 by means of the connection (eg a plug connector).
  • the air to be treated which is generally provided with the reference number 17 and which contains liquid and/or solid particles, is introduced laterally into the interior of the housing 67 via an air inlet 19 and fed to the electrostatic precipitator 5 .
  • the separated liquid and/or solid particles which are generally identified by the reference number 20, are transported away to a collection container 21, which is also arranged inside the housing 67, while the cleaned fresh air, which is identified by the reference number 22, is deflected in particular by means of the deflection body 17 .
  • the air can pass through an air after-treatment system, which can include an ozone filter, for example, and finally the cleaned and possibly reduced in ozone content clean air, which is provided with the reference number 24, exits via the air outlet 26, which can have, for example, grid-shaped or lamellar-shaped outlet openings 29.
  • the housing 67 or the room air cleaner 1 in the direction of the environment.
  • the liquid for wetting the counter-electrode 5 is pumped from the liquid reservoir 11 to a top side 25 of the counter-electrode 5 via a line 23 connected to the liquid reservoir 11 with the aid of a pump (not shown).
  • the liquid reservoir 11 and the collecting container 21 can be the same component or can comprise different liquid basins.
  • the operation of the room air cleaner 1 according to the invention is described in detail with reference to Figure 19 and takes place as follows in relation to the air flow 17 to be cleaned.
  • the air 17 to be treated reaches an air duct structure 31 via the air supply 15 and finally into the interior of the room air cleaner 1.
  • the inflow direction E is indicated in FIG. 19 by an arrow on the inlet side.
  • the air supply 15 like the room air cleaner as a whole, is designed in a rotational manner, so that there is a circumferential air inflow and the air supply 15 essentially has a ring shape with the same cross section distributed over the circumference.
  • the air supply 15 defines an air duct structure 31 which delimits a curved passageway for the air to be treated into the interior of the room air cleaner 1 .
  • the air supply duct comprises an upstream duct wall 43 at which the inflowing air undergoes a first deflection by at least 30° with respect to the inflow direction E.
  • the upstream duct wall 43 is shaped concavely in relation to the inflow direction E, so that the inflowing air can flow against the duct wall 43 with as little pressure loss as possible and can continue to flow guided thereon towards the interior of the room air cleaner 1.
  • the air supply duct also comprises a downstream duct wall 45 opposite the upstream duct wall 43, which is also shaped in such a way that the air flow deflected by the upstream duct wall 43 into an intermediate flow direction Z flows against the duct wall 45 with as little pressure loss as possible and is guided therein Can continue to flow towards the interior of the room air cleaner 1 along an outflow direction A.
  • the channel wall 45 is also designed and shaped concavely in relation to the intermediate flow direction Z. At the downstream channel wall 45 the air flow undergoes a further deflection by at least 30° with respect to the intermediate flow direction Z and is finally discharged in the direction of the separation space formed between emission electrode needles 9 and counter-electrode 5 .
  • Both the downstream duct wall 45 and the upstream duct wall 43 each include a convexly curved flow separation edge 47,49, at which the air flow leaves the duct walls 43,45 as a free jet into the interior of the room air cleaner, i.e. without further structural guidance and/or support in the course of the flow.
  • the convex curvature of the flow separation edges 49 , 47 also results in the lowest possible flow losses/pressure losses in the area of the flow outlet 6 .
  • a laminar flow can form over the entire course of the air supply duct, which can spread without turbulence and/or pressure loss.
  • the air supply 15 in the area of the flow outlet 6 is a flow outlet surface.
  • This flow outlet area is smaller than a separation space cross-sectional area delimited by the counter-electrode 5 and the emission electrode 7, which represents the height or the distance between the emission electrode needles 9 and the counter-electrode 5, as indicated.
  • an imaginary extension T of the air guidance guide surface beyond the flow separation edge is shown, which does not cross the emission electrode needles 9, but in the direction of the counter-electrode 5 is oriented and crosses it.
  • the flow separation edge 47,49 has a diffuser and/or spoiler-like effect on the air flow and causes the air flow to be introduced in a targeted manner into the separation space between the emission electrode needles 9 and the counter-electrode 5, because the orientation of the air guidance guide surface according to the invention can be reliable it can be ensured that the air to be treated and cleaned largely, in particular exclusively, reaches the electrode cloud forming a so-called plasma cone 39 below the emission electrode needles 9 .
  • the counter-electrode 5 is wetted with a liquid in order to collect and transport away the particles separated from the air.
  • Arrow 20 indicates the removal of the particles.
  • the liquid runs particularly evenly and/or as a calm liquid film on the surface 25 of the counter electrode 5, which has a funnel shape according to the preferred embodiment, in its center of rotation and is finally collected in the collecting container 21.
  • the air to be treated flows without obstacles first through the electrostatic precipitator 3 and finally through the condenser 33, whose functioning and construction are explained below.
  • the emission electrode 7 comprises an array of emission electrode needles 9, which are attached to a rear side of an air guiding wall 35 delimiting the air flow path, facing away from the separation space between emission electrode needles 9 and counter-electrode 5.
  • the driving circuit 120 is conductively connected to the emission electrode 7 and the counter electrode 5 in order to apply a high voltage to the emission electrode 7 and the counter electrode 5 .
  • the counter-electrode 5 is connected to the reference potential GND of the drive circuit 120 .
  • the control circuit 120 can regulate the plasma current flowing from the emission electrode 7 via the DC plasma to the counter-electrode 5, so that the desired plasma current is established.
  • the air duct wall 35 is designed essentially parallel to the counter-electrode contour and extends in a rotational manner from radially outward to radially inward in the direction of the central deflection body 17.
  • the air duct wall 35 is electrically conductive and has a capacitor plate 37 forming downstream of the electrostatic precipitator 3, in particular the emission electron needles 9 Section on which is connected to the drive circuit 120, and builds up an electric high-voltage field F together with the counter-electrode ( Figure 19).
  • the emission electrode needles In the area of the electrostatic precipitator 3, the emission electrode needles generate dense electron clouds in the form of so-called plasma cones 39, in which the particles present in the air are electrically charged, around the charged particles 41 to separate from the air. Separation takes place in that the charged particles are attracted by the grounded counter-electrode 5 in accordance with the technical current direction TR.
  • the downstream capacitor plate arrangement 37 and the electrical high-voltage field F built up therein are used to counteract a negative charged particles 41 to impose an attractive force Fc, which causes the electrically charged particle 41 to be deflected or deflected in the direction of the counter-electrode 5 and finally entrained there by the wetting of the liquid and transported away into the collection container 21 .
  • the cleaned air 22 is deflected vertically upwards via the deflection body 17 and finally fed to the environment (reference number 24).

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Automation & Control Theory (AREA)
  • Microelectronics & Electronic Packaging (AREA)
  • Power Conversion In General (AREA)
  • Inverter Devices (AREA)

Abstract

L'invention concerne un circuit de commande destiné à générer une haute tension appliquée aux électrodes d'un électrofiltre. Un autre aspect de l'invention concerne l'utilisation d'un tel circuit de commande dans un dispositif, p. ex., dans un filtre à air propre ou un filtre à particules. L'invention concerne également une carte de circuit imprimé sur laquelle un circuit de commande selon l'invention est mis en œuvre au moyen de composants individuels.
PCT/EP2023/053761 2022-02-15 2023-02-15 Circuit de commande pour un électrofiltre WO2023156457A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102022103550.6 2022-02-15
DE102022103550.6A DE102022103550B4 (de) 2022-02-15 2022-02-15 Ansteuerschaltung für einen Elektroabscheider

Publications (1)

Publication Number Publication Date
WO2023156457A1 true WO2023156457A1 (fr) 2023-08-24

Family

ID=85278104

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/EP2023/053761 WO2023156457A1 (fr) 2022-02-15 2023-02-15 Circuit de commande pour un électrofiltre

Country Status (2)

Country Link
DE (1) DE102022103550B4 (fr)
WO (1) WO2023156457A1 (fr)

Citations (17)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE2341626A1 (de) * 1973-08-17 1974-09-05 Braun Ag Elektrostatisches filter
EP0206160A1 (fr) * 1985-06-24 1986-12-30 Metallgesellschaft Ag Alimentation de courant pour filtre électrostatique
DE3531025A1 (de) * 1985-08-30 1987-03-05 Bosch Gmbh Robert Schaltungsanordnung zur regelung der hochspannungsversorgung eines elektrostatischen filters
JPH081042A (ja) * 1994-06-16 1996-01-09 Brother Ind Ltd 静電式空気清浄機
EP0763759A2 (fr) * 1995-09-14 1997-03-19 Sumitomo Electric Industries, Inc. Méthode et appareil de décharge électrique
DE69506712T2 (de) * 1994-07-20 1999-07-22 Jacques Leon Georges Breton Positive oder negative ionengenerator im gasmedium mit plasmaeinschluss
JP2002273267A (ja) * 2001-03-21 2002-09-24 Origin Electric Co Ltd 電気集塵用電源装置及びその制御方法
US20040033176A1 (en) 2002-02-12 2004-02-19 Lee Jim L. Method and apparatus for increasing performance of ion wind devices
EP2025411A1 (fr) * 2006-06-08 2009-02-18 Panasonic Electric Works Co., Ltd Appareil d'atomisation electrostatique
TW201128896A (en) * 2010-02-01 2011-08-16 Chao-Cheng Lu Portable positive charge transmitter
DE102011112821A1 (de) * 2011-09-12 2013-03-14 Brose Fahrzeugteile GmbH & Co. Kommanditgesellschaft, Würzburg Elektromotor, insbesondere Kühlerlüftermotor
US8529830B2 (en) 2009-12-31 2013-09-10 Shanghai Tianyun Environmental Protection Technology Co., Ltd. Plasma sterilizing-purifying device and method for air sterilizing and purifying
KR20150068212A (ko) * 2013-12-11 2015-06-19 주식회사 포스코아이씨티 마이크로 펄스 시스템, 마이크로 펄스 시스템의 제어방법, 및 마이크로 펄스 시스템을 포함하는 전기 집진장치
JP2016188925A (ja) * 2015-03-30 2016-11-04 ブラザー工業株式会社 画像形成装置
EP3220522A1 (fr) * 2015-01-30 2017-09-20 Kyosan Electric Mfg. Co., Ltd. Circuit pilote de grille d'isolation haute fréquence et procédé de pilotage de circuit de grille
JP2019146744A (ja) * 2018-02-27 2019-09-05 Hoya株式会社 内視鏡システム、及びプロセッサ
WO2021224017A1 (fr) 2020-05-08 2021-11-11 Woco Gmbh & Co. Kg Laveur d'air à séparation électrostatique

Family Cites Families (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5629844A (en) 1995-04-05 1997-05-13 International Power Group, Inc. High voltage power supply having multiple high voltage generators
JP3472555B2 (ja) 1999-12-15 2003-12-02 川崎重工業株式会社 電気集塵機
US8023274B2 (en) 2007-02-19 2011-09-20 Arris Group, Inc. System for increasing isolation boundary withstand voltage

Patent Citations (17)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE2341626A1 (de) * 1973-08-17 1974-09-05 Braun Ag Elektrostatisches filter
EP0206160A1 (fr) * 1985-06-24 1986-12-30 Metallgesellschaft Ag Alimentation de courant pour filtre électrostatique
DE3531025A1 (de) * 1985-08-30 1987-03-05 Bosch Gmbh Robert Schaltungsanordnung zur regelung der hochspannungsversorgung eines elektrostatischen filters
JPH081042A (ja) * 1994-06-16 1996-01-09 Brother Ind Ltd 静電式空気清浄機
DE69506712T2 (de) * 1994-07-20 1999-07-22 Jacques Leon Georges Breton Positive oder negative ionengenerator im gasmedium mit plasmaeinschluss
EP0763759A2 (fr) * 1995-09-14 1997-03-19 Sumitomo Electric Industries, Inc. Méthode et appareil de décharge électrique
JP2002273267A (ja) * 2001-03-21 2002-09-24 Origin Electric Co Ltd 電気集塵用電源装置及びその制御方法
US20040033176A1 (en) 2002-02-12 2004-02-19 Lee Jim L. Method and apparatus for increasing performance of ion wind devices
EP2025411A1 (fr) * 2006-06-08 2009-02-18 Panasonic Electric Works Co., Ltd Appareil d'atomisation electrostatique
US8529830B2 (en) 2009-12-31 2013-09-10 Shanghai Tianyun Environmental Protection Technology Co., Ltd. Plasma sterilizing-purifying device and method for air sterilizing and purifying
TW201128896A (en) * 2010-02-01 2011-08-16 Chao-Cheng Lu Portable positive charge transmitter
DE102011112821A1 (de) * 2011-09-12 2013-03-14 Brose Fahrzeugteile GmbH & Co. Kommanditgesellschaft, Würzburg Elektromotor, insbesondere Kühlerlüftermotor
KR20150068212A (ko) * 2013-12-11 2015-06-19 주식회사 포스코아이씨티 마이크로 펄스 시스템, 마이크로 펄스 시스템의 제어방법, 및 마이크로 펄스 시스템을 포함하는 전기 집진장치
EP3220522A1 (fr) * 2015-01-30 2017-09-20 Kyosan Electric Mfg. Co., Ltd. Circuit pilote de grille d'isolation haute fréquence et procédé de pilotage de circuit de grille
JP2016188925A (ja) * 2015-03-30 2016-11-04 ブラザー工業株式会社 画像形成装置
JP2019146744A (ja) * 2018-02-27 2019-09-05 Hoya株式会社 内視鏡システム、及びプロセッサ
WO2021224017A1 (fr) 2020-05-08 2021-11-11 Woco Gmbh & Co. Kg Laveur d'air à séparation électrostatique

Also Published As

Publication number Publication date
DE102022103550A1 (de) 2023-08-17
DE102022103550B4 (de) 2024-01-04

Similar Documents

Publication Publication Date Title
EP0088973B1 (fr) Circuit pour un fonctionnement à impulsions de un ou plusieurs ozoniseurs
DE2714126A1 (de) Elektrofilter fuer luftreinigung
DE2727858A1 (de) Elektrische entstaubungsvorrichtung
DD257590A5 (de) Anordnung zur erzeugung einer elektrischen koronaentladung in der luft
DE2215852A1 (de) Verfahren und Gerät zum Erzeugen von Ionen und zum Steuern elektrostatischer Potentiale
WO2017029099A1 (fr) Générateur de plasma et procédé de réglage d'un rapport d'ions
WO2019034496A1 (fr) Module de génération de plasma et utilisation dudit module
DE10084799T5 (de) Universelle eigensichere Schaltstromversorgung
DE102013109797A1 (de) Ionisator
DE102022103550B4 (de) Ansteuerschaltung für einen Elektroabscheider
DE2929048A1 (de) Elektrostatische einrichtung zur reinigung der luft in einem kraftfahrzeug
DE102009033827B3 (de) Entladevorrichtung
EP3934811A1 (fr) Unité de filtration électrostatique pour un dispositif de purification d'air et dispositif de purification d'air
DE2341541C2 (de) Elektroabscheider
EP2713807A1 (fr) Dispositif de production de décharges électriques de faible énergie, en particulier pour éliminer des poux
DE3114009C2 (fr)
DE202010000639U1 (de) Gerät zur Luftaufbereitung und elektrostatischer Reinigungsfilter für dieses Gerät
DE3609698A1 (de) Vorrichtung und verfahren zur ionisierung oder neutralisation eines gasstroms und der in ihm enthaltenen partikel
DE102005063069B4 (de) Luftreinigungsgerät mit luftdurchsatzabhängiger Hochspannungserzeugung
DE2253601C2 (de) Hochspannungsspeisung für einen elektrostatischen Staubabscheider
EP4061534A1 (fr) Unité de filtration pour dispositif de purification d'air et dispositif de purification d'air
DE102021130189B3 (de) Ionisationsvorrichtung
DE4033679A1 (de) Verfahren zum steuern der funktion eines elektrischen filtergeraets und elektrisches filtergeraet
DE4008561C2 (de) Verfahren zum Betreiben einer Spannungsversorgungseinrichtung für ein Elektrofilter
DE2332270A1 (de) Einrichtung fuer gasstrombehandlung durch elektrische entladung

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 23705532

Country of ref document: EP

Kind code of ref document: A1