WO2020217708A1 - アンテナ結合回路、アンテナ結合素子及びアンテナ装置 - Google Patents

アンテナ結合回路、アンテナ結合素子及びアンテナ装置 Download PDF

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Publication number
WO2020217708A1
WO2020217708A1 PCT/JP2020/008501 JP2020008501W WO2020217708A1 WO 2020217708 A1 WO2020217708 A1 WO 2020217708A1 JP 2020008501 W JP2020008501 W JP 2020008501W WO 2020217708 A1 WO2020217708 A1 WO 2020217708A1
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Prior art keywords
coil
radiation element
conductor pattern
antenna
antenna coupling
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PCT/JP2020/008501
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English (en)
French (fr)
Japanese (ja)
Inventor
冬夢 田邊
石塚　健一
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株式会社村田製作所
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Application filed by 株式会社村田製作所 filed Critical 株式会社村田製作所
Priority to JP2021515842A priority Critical patent/JP7067670B2/ja
Priority to CN202090000283.9U priority patent/CN214754159U/zh
Publication of WO2020217708A1 publication Critical patent/WO2020217708A1/ja

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/30—Combinations of separate antenna units operating in different wavebands and connected to a common feeder system
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/10—Resonant antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/30—Arrangements for providing operation on different wavebands
    • H01Q5/378—Combination of fed elements with parasitic elements

Definitions

  • the present invention relates to an antenna coupling circuit suitable for widening the bandwidth of an antenna device, an antenna coupling element provided with the same, and an antenna device.
  • a mobile phone communication antenna needs to cover a wide band such as 0.7 GHz or more and 2.7 GHz or less.
  • a wide band such as 0.7 GHz or more and 2.7 GHz or less.
  • it has conventionally been common to shift the resonance frequency of the antenna with a switch according to the frequency band used.
  • Patent Document 1 discloses a technique for obtaining a wide band by adding a transformer and a non-feeding element to a feeding radiation element and making the antenna double-resonant in response to such a request.
  • a feeding circuit is connected to the feeding radiating element via the first coil of the transformer, and the second coil of the transformer is connected to the non-feeding radiating element.
  • An object of the present invention is to provide an antenna coupling circuit, an antenna coupling element, and an antenna coupling element thereof, which enable widening by double resonance between a fed radiation element and a non-feeding radiation element while maintaining impedance matching over a wide band.
  • the purpose is to provide an antenna device to be provided.
  • the antenna coupling circuit as an example of the present disclosure is It comprises a first coil having a first end and a second end, a second coil having the first and second ends, and a third coil having the first and second ends.
  • the second end of the first coil and the first end of the second coil are connected, The winding direction from the first end to the second end of the first coil and the winding direction from the first end to the second end of the second coil are the same direction.
  • the second coil is magnetically coupled to the first coil and the third coil.
  • the first end of the first coil is used as the feeding end.
  • the first end of the second coil is used as the power feeding radiation element connection end.
  • the second end of the second coil is used as the grounding end.
  • the first end of the third coil is used as the connecting end of the non-feeding radiation element.
  • the second end of the third coil is the grounding end.
  • the antenna coupling element as an example of the present disclosure is It is a chip component in which a conductor pattern is formed on a laminate of a plurality of insulating base materials to form the antenna coupling circuit.
  • the first coil, the second coil, and the third coil are composed of a coil conductor pattern in which their winding axes are aligned or parallel to each other.
  • On the outer surface of the laminate The power supply terminal to which the first end of the first coil is connected and The power feeding radiation element connection terminal to which the first end of the second coil is connected, The non-feeding radiation element connection terminal to which the first end of the third coil is connected, A ground terminal to which the second end of the second coil and the second end of the third coil are connected, To be equipped.
  • the antenna device as an example of the present disclosure is The antenna coupling circuit, the fed radiation element connected to the feeding radiation element connection end, and the non-feeding radiation element connected to the non-feeding radiation element connection end are provided.
  • the antenna is double-resonated by coupling the fed radiation element and the non-feeding radiation element, and an auto transformer is configured by the first coil and the second coil, and impedance conversion by this auto transformer is performed.
  • the double-resonant resonant circuit is impedance-matched over a wide band.
  • the antenna coupling element of the present invention by simply providing this single antenna coupling element between the feeding circuit and the feeding radiation element and the non-feeding radiation element, the feeding radiation is maintained while maintaining impedance matching over a wide band. Widening the band by double resonance between the element and the non-feeding radiation element becomes effective.
  • impedance matching is maintained over a wide band, and a wide band is achieved by double resonance between the fed radiation element and the non-feed radiation element.
  • FIG. 1A is a circuit diagram showing a configuration of a main part of an antenna coupling circuit 10 according to a first embodiment, an antenna device 201 including the antenna coupling circuit 10, and a communication device 301.
  • FIG. 1B is a circuit diagram showing the antenna coupling circuit 10 portion of the communication device 301 shown in FIG. 1A as an equivalent circuit.
  • FIG. 2 is an equivalent circuit diagram of a transformer composed of the first coil L1 and the second coil L2.
  • FIG. 3A is a diagram showing the frequency characteristics of the reflection coefficient S11 of the antenna device 201 as viewed from the first end T11 (feeding end) of the first coil L1 of the antenna device 201 according to the first embodiment.
  • FIG. 1A is a circuit diagram showing a configuration of a main part of an antenna coupling circuit 10 according to a first embodiment, an antenna device 201 including the antenna coupling circuit 10, and a communication device 301.
  • FIG. 1B is a circuit diagram showing the antenna coupling circuit 10 portion of the communication device 301 shown in
  • FIG. 3B is a diagram showing the frequency characteristics of the impedance of the antenna device 201 viewed from the first end T11 (feeding end) of the first coil L1 on the Smith chart.
  • FIG. 4A is a circuit diagram of an antenna device as a comparative example
  • FIG. 4B is a diagram showing the frequency characteristics of the reflection coefficient S11 when the feeding radiation element 11 is viewed from the feeding circuit 9.
  • FIG. 4C is a diagram showing the frequency characteristics of the impedance of the feeding radiation element 11 viewed from the feeding circuit 9 on a Smith chart.
  • FIG. 5A is a circuit diagram of an antenna device including a transformer composed of a first coil La and a second coil Lb, a feeding radiation element 11 and a non-feeding radiation element 12, and FIG.
  • FIG. 5B is a power supply. It is a figure which shows the frequency characteristic of the reflection coefficient S11 of the antenna device seen from the circuit 9.
  • FIG. 5C is a diagram showing the frequency characteristics of the impedance of the antenna device as seen from the feeding circuit 9 on a Smith chart.
  • FIG. 6 is a perspective view showing the structure of the antenna coupling element 101 according to the second embodiment.
  • FIG. 7 is a perspective view showing a conductor pattern of the intermediate layer 1C of the laminated body 1 shown in FIG.
  • FIG. 8 is an exploded plan view showing a conductor pattern formed on a plurality of insulating base materials constituting the laminated body 1.
  • FIG. 9 is a diagram showing a difference in the coil opening diameter of the coil conductor pattern.
  • FIG. 10 is a circuit diagram showing the configuration of the antenna coupling element 101 according to the second embodiment and the antenna device 201 including the antenna coupling element 101.
  • FIG. 11A is a circuit diagram of a portion including the antenna coupling element 101 and the connection path from the fourth terminal T4 to the ground.
  • FIG. 11B is a circuit diagram in which the transformer by the second coil L2 and the third coil L3 is replaced with an equivalent circuit.
  • FIG. 12 is an exploded plan view showing conductor patterns formed on a plurality of insulating base materials in the antenna coupling element according to the third embodiment.
  • FIG. 13 is a circuit diagram showing the configuration of the antenna coupling element 102 according to the third embodiment and the antenna device 202 including the antenna coupling element 102.
  • FIG. 14 is a diagram showing a region on the Smith chart of the impedance locus shown in FIG. 5 (C).
  • the "antenna device" shown in each embodiment can be applied to both the transmitting side and the receiving side of the signal. That is, even if the transmission / reception relationship is reversed, the same effect is obtained.
  • FIG. 1A is a circuit diagram showing a configuration of a main part of an antenna coupling circuit 10 according to a first embodiment, an antenna device 201 including the antenna coupling circuit 10, and a communication device 301.
  • FIG. 1B is a circuit diagram showing the antenna coupling circuit 10 portion of the communication device 301 shown in FIG. 1A as an equivalent circuit.
  • the communication device 301 includes a power supply circuit 9 and an antenna device 201.
  • the antenna device 201 includes an antenna coupling circuit 10, a fed radiation element 11, and a non-feed radiation element 12.
  • Both the fed radiation element 11 and the non-feed radiation element 12 are, for example, monopole antennas.
  • the basic resonance (fundamental wave) of each of the fed radiation element 11 and the non-feeding radiation element 12 covers the low band frequency band from 700 MHz to 960 MHz.
  • the middle band and high band frequency bands from 1710 MHz to 2.7 GHz are covered by higher-order resonances (harmonics) of the fed radiation element 11 and the non-feeder radiation element 12, respectively.
  • the basic resonance frequency on the feeding radiation element 11 side covers the low frequency side of the low band
  • the basic resonance frequency on the non-feeding radiation element 12 side covers the low frequency side of the low band.
  • the basic resonance frequency of the feeding radiation element 11 is, for example, 900 MHz in the low band (for example, 700 MHz to 960 MHz).
  • the basic resonance frequency of the non-feeding radiation element 12 is, for example, 800 MHz.
  • the fundamental resonance frequency of the feeding radiation element 11 may cover the low frequency side of the low band
  • the fundamental frequency of the non-feeding radiation element 12 may cover the high frequency side of the low band
  • the power supply circuit 9 is a high-frequency circuit section of a communication circuit, and handles, for example, a communication frequency band of 0.7 GHz to 2.7 GHz.
  • the antenna coupling circuit 10 includes a first coil L1, a second coil L2, and a third coil L3.
  • the second end T12 of the first coil L1 and the first end T21 of the second coil L2 are connected, and the winding direction from the first end T11 to the second end T12 of the first coil L1 and the winding direction of the second coil L2.
  • the winding direction from the first end T21 to the second end T22 is the same.
  • the dot marks attached to the first coil L1 and the second coil L2 indicate the winding directions of the first coil L1 and the second coil L2.
  • K1 in FIG. 1A represents the coupling between the first coil L1 and the second coil L2 and its coefficient.
  • the second coil L2 is magnetically coupled with the third coil L3.
  • the dot marks attached to the third coil L3 indicate the winding direction of the third coil L3 with respect to the second coil L2.
  • k2 in FIG. 1A represents the coupling between the second coil L2 and the third coil L3 and their coefficients.
  • k3 in FIG. 1A represents the coupling between the first coil L1 and the third coil L3 and their coefficients.
  • the first end T11 of the first coil L1 is a feeding end, and the feeding circuit 9 is connected to this feeding end.
  • the first end T21 of the second coil L2 is a feeding radiation element connecting end, and the feeding radiation element 11 is connected to the feeding radiation element connecting end.
  • the second end T22 of the second coil L2 is a grounding end, and this grounding end is connected to the ground of the circuit.
  • the first end T31 of the third coil L3 is a non-feeding radiation element connection end, and the non-feeding radiation element 12 is connected to the non-feeding radiation element connection end.
  • the second end T32 of the third coil L3 is a ground end, and this ground end is connected to the ground of the circuit.
  • the mutual inductance M generated by the coupling between the first coil L1 and the second coil L2 becomes the self-inductance of the first coil L1 and the self-inductance of the second coil L2, respectively. Since they are added in series, the self-inductance of the first coil L1 can be reduced accordingly. Further, by adding the mutual inductance, the impedance conversion ratio of the transformer by the first coil L1 and the second coil L2 can be increased. Note that in FIG. 1B, the mutual inductance due to the coupling of the third coil L3 with the first coil L1 and the second coil L2 is not shown separately.
  • the impedance conversion ratio is expressed as L1 for the self-inductance of the first coil L1, L2 for the self-inductance of the second coil L2, and M for the mutual inductance.
  • (-M + L2 + M) (L1 + L2 + 2M): L2 Therefore, a large impedance conversion ratio can be obtained.
  • the wire length of the coil conductor pattern can be shortened, and thereby impedance matching can be achieved while reducing the insertion loss due to the resistance component due to the coil conductor pattern.
  • FIG. 2 shows a transformer composed of the first coil L1 and the second coil L2 as an equivalent circuit including an ideal transformer.
  • the transformer can be represented by the ideal transformer T, the parallel parasitic component LE, and the series parasitic component LL.
  • the impedance conversion ratio of the ideal transformer T is n: 1.
  • the parallel parasitic component LE effectively acts as a shunt-connected inductor in a low frequency band as compared with a high frequency band.
  • the parallel parasitic component LE is converted to a high impedance, and the ideal transformer T is converted to a higher impedance.
  • the high frequency band it is converted to a predetermined high impedance mainly only by the ideal transformer T.
  • the feeding radiation element 11 has, for example, a real impedance part of about 10 ⁇ in the low band frequency band and a real part of impedance of about 19 ⁇ in the high band frequency band.
  • the feeding radiation element 11 is impedance-matched with the feeding circuit of 50 ⁇ .
  • the parallel parasitic component LE matches from 10 ⁇ to 19 ⁇ , and the ideal transformer T converts it to 50 ⁇ .
  • the first end T11 (feeding end) of the first coil L1 is not directly connected to the feeding circuit 9, but is indirectly connected via another circuit or element. May be good. Further, the second end T22 (grounded end) of the first coil L1 may not be directly connected to the ground of the circuit, but may be indirectly connected to the ground of the circuit via another circuit or element. Similarly, the second end T32 (grounded end) of the third coil L3 may not be directly connected to the ground of the circuit, but may be indirectly connected to the ground of the circuit via another circuit or element.
  • FIG. 3A is a diagram showing the frequency characteristics of the reflection coefficient S11 of the antenna device 201 as viewed from the first end T11 (feeding end) of the first coil L1 of the antenna device 201 according to the present embodiment.
  • FIG. 3B is a diagram showing the frequency characteristics of the impedance of the antenna device viewed from the first end T11 (feeding end) of the first coil L1 on the Smith chart.
  • the frequency f1 of the fundamental resonance on the high frequency side of the low band is 900 MHz
  • the frequency f2 of the fundamental resonance on the low frequency side of the low band is 800 MHz.
  • the resonance of the frequency f1 is mainly caused by the feeding radiation element 11 and the second coil L2
  • the resonance of the frequency f2 is mainly caused by the non-feeding radiation element 12 and the third coil L3.
  • the resonance of the frequency f1 is mainly generated by the non-feeding radiation element 12 and the third coil L3
  • the resonance of the frequency f2 is mainly generated by the feeding radiation element 11 and the second coil L2. May be good.
  • FIG. 3B is an impedance locus when the frequency is swept in the range of 700 MHz to 960 MHz.
  • the reflection coefficient S11 becomes as small as the frequencies f1 and f2, impedance matching is maintained over a wide band, and the wide band is widened by the double resonance of the fed radiation element and the non-feed radiation element. Be done.
  • FIG. 4A is a circuit diagram of an antenna device as a comparative example
  • FIG. 4B is a diagram showing the frequency characteristics of the reflection coefficient S11 when the feeding radiation element 11 is viewed from the feeding circuit 9.
  • FIG. 4C is a diagram showing the frequency characteristics of the impedance of the feeding radiation element 11 viewed from the feeding circuit 9 on a Smith chart.
  • the feeding radiation element 11 resonates at a frequency f1 at which the imaginary portion (jX) of its impedance becomes 0, but in this example, the size of the feeding radiation element 11 is small and impedance matching is insufficient.
  • FIG. 5A is a circuit diagram of an antenna device including a transformer composed of a first coil La and a second coil Lb, a feeding radiation element 11 and a non-feeding radiation element 12, and FIG. 5B is a power supply. It is a figure which shows the frequency characteristic of the reflection coefficient S11 of the antenna device seen from the circuit 9.
  • FIG. 5C is a diagram showing the frequency characteristics of the impedance of the antenna device as seen from the feeding circuit 9 on a Smith chart.
  • FIG. 14 is a diagram showing a region on the Smith chart for the impedance locus shown in FIG. 5 (C).
  • the region Rn is the impedance in the vicinity of the frequency f2.
  • the region Ro is the impedance in the vicinity of the frequency f1, and the region Rp is the impedance in the frequency band higher than the frequency f1.
  • the region Rn is in the third quadrant of the Smith chart (the real part of the impedance is 1 or less and the imaginary part is the negative quadrant), if the inductor is connected to the shunt, the impedance locus is moved along the arrow A1 to obtain the impedance. Consistency can be achieved. However, since the region Ro is at the left end of the Smith chart (the region where the real part of the impedance is about 0 and the imaginary part is about 0), impedance matching cannot be achieved even if the reactance element is shunted.
  • the impedance locus is moved along the arrow A2.
  • the frequency of the harmonic resonance of the circuit by the feeding radiation element 11 and the second coil L2 moves significantly. Impedance is still inconsistent in the high frequency range.
  • the impedance conversion is performed by the auto transformer composed of the first coil L1 and the second coil L2. It matches the impedance of the circuit by the feeding radiation element 11 and the second coil L2. That is, the impedance locus shown in FIG. 5B is reduced and shifted to the right (the direction in which the actual portion of impedance increases), and impedance matching is performed at frequencies f1 and f2. As a result, impedance matching is maintained over a wide band, and a wide band is achieved by double resonance between the feeding radiation element and the non-feeding radiation element.
  • FIG. 6 is a perspective view showing the structure of the antenna coupling element 101 according to the second embodiment.
  • the antenna coupling element 101 is configured with the antenna coupling circuit 10 shown in FIGS. 1 (A) and 1 (B).
  • the antenna coupling element 101 is configured by forming a conductor pattern inside and outside the laminated body 1 of the insulating base material.
  • a first terminal T1 as a power feeding radiation element connection terminal, a second terminal T2 as a power supply terminal, a third terminal T3 as a non-feeding radiation element connection terminal, and a fourth terminal T4 as a ground terminal. are formed respectively.
  • the conductor patterns of the first coil L1, the second coil L2, and the third coil L3 are formed on the intermediate layer 1C.
  • FIG. 7 is a perspective view showing the conductor pattern of the intermediate layer 1C. In FIG. 7, it is enlarged in the thickness direction.
  • FIG. 8 is an exploded plan view showing a conductor pattern formed on a plurality of insulating base materials constituting the laminated body 1.
  • the insulating base material Sb is the bottom layer insulating base material
  • the insulating base material St is the top layer insulating base material
  • the insulating base materials S1 to S10 are the insulating base materials of the intermediate layer 1C.
  • a plurality of insulating base materials having no conductor pattern are provided between the insulating base material Sb and the insulating base material S1 and between the insulating base material St and the insulating base material S10.
  • conductor patterns of the first terminal T1, the second terminal T2, the third terminal T3, and the fourth terminal T4 are formed on the lower surface of the insulating base material Sb, respectively. Similarly, conductor patterns of the first terminal T1, the second terminal T2, the third terminal T3, and the fourth terminal T4 are formed on the upper surface of the insulating base material St, respectively.
  • the broken line conceptually shows the interlayer connecting conductor.
  • Coil conductor patterns L11 and L12 are formed on the insulating base materials S1 and S2.
  • the coil conductor patterns L11 and L12 form the first coil L1.
  • Coil conductor patterns L21 to L26 are formed on the insulating base materials S2 to S7.
  • the coil conductor patterns L21 to L26 form the second coil L2.
  • Coil conductor patterns L31 to L33 are formed on the insulating base materials S8 to S10.
  • the coil conductor patterns L31 to L33 form the third coil L3.
  • ⁇ L33 overlap over the entire circumference when viewed from the winding axis direction (direction parallel to the Z axis). That is, the coil winding shafts of the first coil L1, the second coil L2, and the third coil L3 are in the same direction or common. Therefore, the first coil L1, the second coil L2, and the third coil L3 are magnetically coupled to each other. In other words, the magnetic flux passing through the coil openings of the first coil L1, the second coil L2 and the third coil L3 is shared, and the coupling coefficient between the coils is high.
  • the coil conductor patterns L21 to L26 forming the second coil L2 are arranged between the coil conductor patterns L11 and L12 forming the first coil L1 and the coil conductor patterns L31 to L33 forming the third coil L3.
  • k1 can be made larger than the coupling coefficient k3 shown in FIG.
  • the number of turns of the second coil L2 is about 5 turns
  • the number of turns of the first coil L1 is about 1.5 turns
  • the number of turns of the third coil L3 is about 2.5 turns. That is, the number of turns of the second coil L2 is larger than the number of turns of the first coil L1 and the third coil L3.
  • the power feeding radiation element 11 since the number of turns of the coil conductor pattern constituting the second coil L2 connected to the power feeding radiation element 11 is larger than the number of windings of the coil conductor pattern forming the first coil L1, the power feeding radiation element 11 The induced electromotive force can be increased while suppressing the influence on the resonance frequency.
  • the interlayer distance between the first coil L1 and the third coil L3 can be increased, whereby the above coupling K1 can be easily made larger than the coefficient k3.
  • FIG. 10 is a circuit diagram showing the configuration of the antenna coupling element 101 according to the second embodiment and the antenna device 201 including the antenna coupling element 101.
  • the circuit configuration of the antenna device 201 is the same as that of the antenna device 201 shown in FIG.
  • the conductor pattern E11 formed on the insulating base material S1 corresponds to the first end T11 of the first coil L1.
  • the conductor pattern E11 conducts to the second terminal T2 formed on the laminated body 1.
  • the conductor pattern E121 formed on the insulating base material S2 corresponds to the second end T12 of the first coil L1 and the first end T21 of the second coil L2.
  • the conductor pattern E121 conducts to the first terminal T1 formed on the laminated body 1.
  • the conductor pattern E22 formed on the insulating base material S7 corresponds to the second end T22 of the second coil L2.
  • the conductor pattern E22 conducts to the fourth terminal T4 formed on the laminated body 1.
  • the conductor pattern E32 formed on the insulating base material S8 corresponds to the second end T32 of the third coil L3. This conductor pattern E32 also conducts to the fourth terminal T4 formed in the laminated body 1.
  • the conductor pattern E31 formed on the insulating base material S10 corresponds to the first end T31 of the third coil L3. The conductor pattern E31 conducts to the third terminal T3 formed on the laminated body 1.
  • the winding direction of the first coil L1 from the first end T11 to the second end T12 and the winding direction of the second coil L2 from the first end T21 to the second end T22 are in the same direction (direction shown in FIG. 8). And counterclockwise). Further, in the present embodiment, the winding direction from the first end T31 to the second end T32 of the third coil L3 (clockwise in the direction shown in FIG. 8) and the first end T21 to the second of the second coil L2. The direction is opposite to the winding direction up to the end T22 (counterclockwise in the direction shown in FIG. 8).
  • the winding direction from the first end T31 to the second end T32 of the third coil L3 is opposite to the winding direction from the first end T11 to the second end T12 of the first coil L1.
  • the dot marks indicate the winding directions of each coil.
  • the antenna coupling element 101 of the circuit shown in FIG. 10 can be obtained.
  • the coil conductor patterns L21 to L26 forming the second coil L2 are the coil conductor patterns L11 and L12 forming the first coil L1 and the coil conductor patterns L31 to L33 forming the third coil L3. Since it is arranged between them, the unnecessary parasitic capacitance generated between the first coil L1 and the third coil L3 is small. Therefore, the adverse effect of the parasitic capacitance and the self-resonance of the parasitic resonance circuit composed of the first coil L1 and the third coil L3 is small.
  • the coil opening diameters of the coil conductor patterns formed on the insulating base materials S1 to S10 are alternately different depending on the stacking position.
  • the coil conductor patterns L11, L22, L24, L26, and L32 shown in FIG. 8 are large-diameter coil conductor patterns having a large coil opening diameter, and the coil conductor patterns L12, L23, L25, L31, and L33 are coil conductor patterns. It is a small diameter coil conductor pattern with a small diameter.
  • FIG. 9 is a diagram showing the difference in the coil opening diameter of the coil conductor pattern.
  • the pattern LB shows the collective shape of the large diameter coil
  • the pattern LS shows the collective shape of the small diameter coil.
  • the inner circumference of the large-diameter coil pattern LB overlaps between the outer circumference and the inner circumference of the small-diameter coil pattern LS.
  • the outer circumference of the small diameter coil pattern LS overlaps between the outer circumference and the inner circumference of the large diameter coil pattern LB.
  • the shape and arrangement of such a coil conductor pattern can be expressed as a "plover arrangement" in the radial direction.
  • the width of the overlap is preferably the maximum width of the stacking misalignment, and the line width is preferably twice the maximum width of the stacking misalignment.
  • the maximum width of stacking deviation is 35 ⁇ m
  • it is preferable that the line width of each coil conductor pattern is 70 ⁇ m, and the large diameter coil pattern LB and the small diameter coil pattern LS are overlapped by 35 ⁇ m in the line width direction.
  • the coil opening of the large-diameter coil and the coil opening of the small-diameter coil overlap even if the insulating base material is not stacked or the coil conductor pattern is formed in a different position with respect to the insulating base material. Since the area (the coil opening formed on the inner circumference of the small-diameter coil pattern LS) can be kept constant, it is possible to suppress variations in electrical characteristics due to the above deviation.
  • FIG. 11A is a circuit diagram of a portion including the antenna coupling element 101 and its connection path from the fourth terminal T4 to the ground.
  • FIG. 11B is a circuit diagram in which the transformer by the second coil L2 and the third coil L3 is replaced with an equivalent circuit.
  • the inductance Lp is a parasitic inductance generated in the connection path from the fourth terminal T4 of the antenna coupling element 101 to the ground of the circuit. Since the second coil L2 and the third coil L3 are coupled with opposite polarities, a negative mutual inductance ( ⁇ M) is generated as shown in FIG. 11 (B). Since this negative inductance is connected in series with the parasitic inductance Lp, the influence of the presence of the parasitic inductance Lp is suppressed.
  • the coil conductor patterns L21 to L26 forming the second coil L2 are the coil conductor patterns L11 and L12 forming the first coil L1 and the coil conductor patterns L31 to L33 forming the third coil L3. Since it is arranged between them, the coupling coefficient between the second coil L2 and the third coil L3 can also be effectively increased. Further, when the number of turns of the second coil L2 is larger than the number of turns of the first coil L1 and the third coil L3, the interlayer distance between the first coil L1 and the third coil L3 can be increased. As a result, the coupling coefficient k2 can be made larger than the coupling coefficient k3 shown in FIG. The larger the coupling coefficient k2, the larger the absolute value of the negative inductance ( ⁇ M), so that the effect of suppressing the parasitic inductance Lp is enhanced.
  • Third Embodiment an example of an antenna coupling element in which the polarity of coupling of the third coil L3 to the first coil L1 and the second coil L2 is different from the example shown in the second embodiment is shown.
  • FIG. 12 is an exploded plan view showing conductor patterns formed on a plurality of insulating base materials in the antenna coupling element according to the third embodiment.
  • the basic structure of the laminated body is as shown in the second embodiment.
  • the shapes of the coil conductor patterns L31, L32, and L33 formed on the insulating base materials S8, S9, and S10 are different from the example shown in FIG.
  • the coil conductor patterns L31, L32, and L33 of the antenna coupling element of the present embodiment are reversed from the coil conductor patterns L31, L32, and L33 shown in FIG. 8 in the left-right direction (direction parallel to the X-axis). is there.
  • FIG. 13 is a circuit diagram showing the configuration of the antenna coupling element 102 according to the present embodiment and the antenna device 202 including the antenna coupling element 102. Since the winding direction of the third coil L3 included in the antenna device 202 is opposite to the winding direction of the third coil L3 included in the antenna device 201, the first end T31 to the second end of the third coil L3 The winding direction up to T32 (counterclockwise in the direction shown in FIG. 12) and the winding direction from the first end T21 to the second end T22 of the second coil L2 (counterclockwise in the direction shown in FIG. 12) are the same. The direction.
  • the winding direction from the first end T31 to the second end T32 of the third coil L3 and the winding direction from the first end T11 to the second end T12 of the first coil L1 are the same direction.
  • the dot mark indicates the winding direction of each coil.
  • the antenna device 201 is designed to strengthen the magnetic field coupling and the electric field coupling. In this way, by making the polarity of the coupling of the third coil L3 to the first coil L1 and the second coil L2 the same, no power is supplied.
  • the polarity (phase) of the current induced in the radiating element 12 can be changed, and the coupling strength of the non-feeding radiating element 12 can be changed.
  • the feeding radiating element 11 and the non-feeding radiating element 12 have various coupling relationships with each other depending on the positional relationship between the two and the extending direction. There are strengths and weaknesses in the bond. In consideration of this coupling relationship, the polarity (phase) of the current induced in the passive repeater 12 is appropriately set.
  • the impedance locus becomes large, and it becomes difficult to match the impedance in the frequency band undertaken by the passive repeater. In that case, the impedance can be easily matched by reversing the polarities.
  • a coupling between the feeding radiation element and the non-feeding radiation element occurs.
  • the coupling and the size of the impedance locus on the Smith chart are related.
  • the inductor Even if the shunt is connected, the impedance is separated from 50 ⁇ (center of Smith chart). In such a case, the size of the coupling is weakened and the third quadrant (the real part of impedance is 1 or less and the imaginary part is negative) or the fourth quadrant (the real part of impedance is 1 or more and imaginary) on the Smith chart. You may want to set the impedance in the negative quadrant).
  • One of the methods is a method of reversing the polarity of the bond.
  • the magnetic field coupling is changed, the direction of the current is changed and the electric field coupling is weakened, and as a result, the coupling of the unfed radiation element can be weakened, resulting in a small impedance trajectory and matching.
  • the impedance can be easily adjusted.
  • Feeding circuit 10 ... Antenna coupling circuit 11 .
  • Feeding radiation element 12 ...
  • Non-feeding radiation element 101, 102 ...
  • Antenna coupling element 201, 202 ... Antenna device 301 ... Communication device

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PCT/JP2020/008501 2019-04-25 2020-02-28 アンテナ結合回路、アンテナ結合素子及びアンテナ装置 WO2020217708A1 (ja)

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Publication number Priority date Publication date Assignee Title
WO2022230371A1 (ja) * 2021-04-28 2022-11-03 株式会社村田製作所 アンテナ装置
JP7211576B1 (ja) * 2021-08-30 2023-01-24 株式会社村田製作所 コイル素子、アンテナ装置、および電子機器
WO2023032510A1 (ja) * 2021-08-30 2023-03-09 株式会社村田製作所 コイル素子、アンテナ装置、および電子機器

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WO2012153690A1 (ja) * 2011-05-09 2012-11-15 株式会社村田製作所 結合度調整回路、アンテナ装置および通信端末装置
JP2014053808A (ja) * 2012-09-07 2014-03-20 Murata Mfg Co Ltd 結合度調整素子、アンテナ装置および無線通信装置
WO2018101285A1 (ja) * 2016-11-29 2018-06-07 株式会社村田製作所 磁界結合素子、アンテナ装置および電子機器

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JP2014053808A (ja) * 2012-09-07 2014-03-20 Murata Mfg Co Ltd 結合度調整素子、アンテナ装置および無線通信装置
WO2018101285A1 (ja) * 2016-11-29 2018-06-07 株式会社村田製作所 磁界結合素子、アンテナ装置および電子機器

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Publication number Priority date Publication date Assignee Title
WO2022230371A1 (ja) * 2021-04-28 2022-11-03 株式会社村田製作所 アンテナ装置
JP7533777B2 (ja) 2021-04-28 2024-08-14 株式会社村田製作所 アンテナ装置
JP7211576B1 (ja) * 2021-08-30 2023-01-24 株式会社村田製作所 コイル素子、アンテナ装置、および電子機器
WO2023032510A1 (ja) * 2021-08-30 2023-03-09 株式会社村田製作所 コイル素子、アンテナ装置、および電子機器

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