WO2018126617A1 - 一种恒流恒压复合拓扑的无线充电电路 - Google Patents

一种恒流恒压复合拓扑的无线充电电路 Download PDF

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WO2018126617A1
WO2018126617A1 PCT/CN2017/090443 CN2017090443W WO2018126617A1 WO 2018126617 A1 WO2018126617 A1 WO 2018126617A1 CN 2017090443 W CN2017090443 W CN 2017090443W WO 2018126617 A1 WO2018126617 A1 WO 2018126617A1
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Prior art keywords
circuit
wireless charging
inductor
resonant capacitor
rectifier
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PCT/CN2017/090443
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English (en)
French (fr)
Inventor
雷艳婷
李建华
袁庆民
茹永刚
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西安特锐德智能充电科技有限公司
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Publication of WO2018126617A1 publication Critical patent/WO2018126617A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • B60L53/10—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles characterised by the energy transfer between the charging station and the vehicle
    • B60L53/12—Inductive energy transfer
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • B60L53/10—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles characterised by the energy transfer between the charging station and the vehicle
    • B60L53/12—Inductive energy transfer
    • B60L53/122—Circuits or methods for driving the primary coil, e.g. supplying electric power to the coil
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/02—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries for charging batteries from ac mains by converters
    • H02J7/04—Regulation of charging current or voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/70—Energy storage systems for electromobility, e.g. batteries
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/7072—Electromobility specific charging systems or methods for batteries, ultracapacitors, supercapacitors or double-layer capacitors
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02T90/10—Technologies relating to charging of electric vehicles
    • Y02T90/14—Plug-in electric vehicles

Definitions

  • the present invention relates to the field of wireless charging, and in particular to a wireless charging circuit of a constant current constant voltage composite topology.
  • Electric vehicle battery charging methods have traditional contact charging and non-contact charging. Compared with the traditional contact charging method, wireless charging can avoid the sparking hazard, reduce the wire loss, reduce the weight of the car body, has the advantages of high safety and reliability, and can be applied to some special occasions such as mines and seabeds.
  • the loosely coupled transformer is the core component of wireless charging.
  • the separated primary and secondary windings and the large distance make it have the disadvantages of large leakage inductance and small magnetizing inductance compared with the tight coupling transformer. Therefore, the compensation network becomes a wireless charging circuit.
  • the loosely coupled transformer must use a multi-element resonant converter to compensate for the leakage inductance and the magnetizing inductance separately, improve the voltage gain and power transmission capability, and reduce the circulating current loss.
  • the constant current and constant voltage phase is an important stage of charging.
  • the wireless charging system can work in a constant current and constant voltage state by performing parameter setting, topology switching and control on the compensation network.
  • the chopper control circuit is added to the secondary circuit of the wireless charging system, and the regulated output is realized by controlling the chopper circuit.
  • a first-order circuit is added to the entire topology circuit of the radio energy transmission, so that the transmission efficiency of the system is lowered.
  • the constant current and constant voltage output can be realized under two different parameters by changing the circuit parameters without increasing the control.
  • the self-inductance of the coil changes with the frequency change, and it is difficult for the control system to work at the resonance point.
  • Chinese patent CN 104753152A discloses a constant current-constant voltage composite topology inductive charging system, which enables the system to achieve constant current output in a series/string compensation (S/S) topology circuit, and A constant voltage output is implemented in a string compensation (P/S) topology circuit.
  • S/S series/string compensation
  • P/S string compensation
  • the hybrid topology circuit can be implemented as a constant current constant voltage charging of the battery, in practical applications, the switching of the primary side resonant capacitor is controlled according to the voltage across the secondary side battery, thereby increasing system cost and control difficulty.
  • the technical problem to be solved by the present invention is to provide a wireless charging circuit of a constant current and constant voltage composite topology for the defects of the above-mentioned conversion mechanism of the prior art, complicated control, large circuit volume, and complicated switching switches.
  • the technical solution adopted by the present invention to solve the technical problem thereof is to construct a wireless charging circuit of a constant current constant voltage composite topology, comprising a first rectifier circuit, a high frequency inverter circuit, a resonance compensation circuit and a second rectifier circuit which are sequentially connected.
  • the resonance compensation circuit includes a primary compensation module and a secondary compensation module, wherein
  • the primary compensation module includes a first inductor and a first resonant capacitor, and a first end of the first resonant capacitor is coupled to a first output end of the high frequency inverter circuit, and a first resonant capacitor The second end is connected to the first end of the first inductor, and the second end of the first inductor is connected to the second output end of the high frequency inverter circuit;
  • the secondary compensation module includes a second inductor, a second resonant capacitor, a third resonant capacitor, and a switch, and a first end of the second resonant capacitor is coupled to the first input end of the second rectifier circuit, a second end of the second resonant capacitor is coupled to the first end of the second inductor, a second end of the second inductor is coupled to a second input of the second rectifier circuit, the switch and the third resonant a capacitor is connected in series between the first end of the second resonant capacitor and the second end of the second inductor;
  • the switch is turned off when the voltage output by the second rectifier circuit does not reach the voltage target value, the wireless charging circuit is in a constant current operation mode, and the voltage output by the switch in the second rectifier circuit reaches a voltage When the target value is closed, the wireless charging circuit is in the constant voltage operating mode.
  • the high frequency inverter circuit is a forward conversion circuit, a flyback conversion circuit, a push-pull inverter circuit, a half bridge inverter circuit or a full bridge inverter circuit.
  • the first rectifier circuit is a PFC rectifier circuit.
  • the PFC rectifier circuit comprises a diode three-phase rectifier bridge, a first group of switching devices, a second group of switching devices, a third group of switching devices, a first electrolytic capacitor, a second electrolytic capacitor, and further, the diode three-phase
  • the three input ends of the rectifier bridge are respectively connected to a three-phase AC voltage
  • the positive bus terminal of the diode three-phase rectifier bridge is connected to the positive pole of the first electrolytic capacitor
  • the cathode of the first electrolytic capacitor is connected to the second electrolytic a cathode of the capacitor
  • a cathode of the second electrolytic capacitor is connected to a negative bus terminal of the diode three-phase rectifier bridge
  • a first end of the first group of switching devices is connected to a first input end of the diode three-phase rectifier bridge
  • a first end of the second set of switching devices is connected to a second input end of the diode three-phase rectifier bridge
  • the high frequency inverter circuit includes a first switch tube and a second switch tube, wherein a first end of the first switch tube is connected to a positive bus end of the first rectifier circuit, and the second switch The first end of the tube is connected to the negative of the first rectifier circuit a second end of the first switch tube and a second end of the second switch tube are respectively connected to a first end of the first resonant capacitor, and a second end of the first inductor is connected to the first end The negative end of an electrolytic capacitor.
  • an equivalent load circuit connected to the second rectifier circuit is further included.
  • the equivalent load circuit comprises a battery.
  • the equivalent load circuit further includes a power conversion circuit connected between the second rectifier circuit and the battery.
  • the resonant compensation circuit in the wireless charging circuit is easy to control at the resonance point regardless of the SS topology or the SSP topology, so that the wireless charging circuit has higher output power and transmission efficiency;
  • the resonant network of the wireless charging circuit works at a fixed voltage gain intersection, and the input impedance angle is zero. In this state, the switching loss is small, which is beneficial to improve wireless.
  • the efficiency of the charging circuit
  • SS/SSP topology switching requires only one switch to enable the wireless charging circuit to operate in constant current and constant voltage. Therefore, the SS/SSP topology has fewer switching devices, smaller circuit size, and constant current. Pressure switching control is simpler.
  • FIG. 1 is a circuit diagram of a first embodiment of a wireless charging circuit of a constant current constant voltage composite topology according to the present invention
  • FIG. 2 is a circuit diagram of the wireless charging circuit of FIG. 1 in a constant current charging mode
  • FIG. 3 is a current waveform diagram of a second rectifier circuit of the wireless charging circuit of FIG. 2 before and after a sudden change in load;
  • FIG. 4 is a circuit diagram of the wireless charging circuit of FIG. 1 in a constant voltage charging mode
  • FIG. 5 is a voltage waveform diagram of a second rectifier circuit of the wireless charging circuit of FIG. 4 before and after a sudden change in load;
  • FIG. 6 is a circuit diagram of a second embodiment of a wireless charging circuit of a constant current constant voltage composite topology according to the present invention.
  • FIG. 7 is a circuit diagram of a first embodiment of the first rectifier circuit of the wireless charging circuit of FIG. 6.
  • the electric circuit includes a first rectifying circuit 1, a high frequency inverter circuit 2, a resonance compensating circuit 3, a second rectifying circuit 4, and an equivalent load circuit 5 which are sequentially connected.
  • the first rectifying circuit 1 is configured to convert the single-phase mains into a DC voltage.
  • the first rectifying circuit 1 may be Three-phase rectifier circuit.
  • the first rectifier circuit 1 is a PFC rectifier circuit.
  • the high frequency inverter circuit 2 is a full bridge inverter circuit and is used to convert the direct current output from the first rectifier circuit into a high frequency alternating current signal.
  • the high frequency inverter circuit 2 may also be a forward conversion circuit, a flyback conversion circuit, a push-pull inverter circuit, a half bridge inverter circuit, or the like.
  • the resonance compensation circuit 3 includes a primary side compensation module 31 and a secondary side compensation module 32.
  • the primary compensation module 31 includes a first inductor L 1 and a first resonant capacitor C 1
  • the secondary compensation module 32 includes a second inductor L 2 , a second resonant capacitor C 2 , a third resonant capacitor C 3 , and a switch S 1 .
  • the first inductor L 1 and the second inductor L 2 are coupled to form a non-contact transformer.
  • a first resonant capacitor C 1 is connected to a first terminal of a first output terminal of the high-frequency inverter circuit 2
  • a first resonant capacitor C 1 is connected to a second terminal of the first inductance of L 1
  • the second end of the first inductor L 1 is connected to the second output end of the high frequency inverter circuit 2.
  • the first end of the second resonant capacitor C 2 is connected to the first input end of the second rectifier circuit 4, and the second end of the second resonant capacitor C 2 is connected to the first end of the second inductor L 2
  • the second end of the second inductor L 2 is connected to the second input end of the second rectifying circuit 4
  • the first end of the switch S 1 is connected to the first end of the second resonant capacitor C 2
  • the second end of the switch S 1 is passed
  • the three resonant capacitor C 3 is connected to the second end of the second inductor L 2 .
  • the positions of the switch S 1 and the third resonant capacitor C 3 are interchangeable.
  • the second rectifying circuit 4 is for converting the coupled high frequency alternating current signal into a direct current signal, and the second rectifying circuit 4 may include a rectifying and filtering circuit or the like matched thereto.
  • the equivalent load circuit 5 may specifically include a battery that is directly coupled to the output of the second rectifier circuit.
  • a power conversion circuit is further included, the power conversion circuit is connected between the second rectifier circuit and the battery, and is configured to convert the voltage current signal output by the second rectifier circuit into a battery Required voltage and current signals.
  • the switch S 1 is turned off when the voltage outputted by the second rectifying circuit 4 does not reach the voltage target value.
  • the wireless charging circuit is in the constant current operating mode, and the switch S 1 is in the second rectifying circuit 4 When the output voltage reaches the voltage target value, it is closed.
  • the wireless charging circuit is in the constant voltage operation mode.
  • the voltage target value is a voltage corresponding to the output of the second rectifier circuit when the battery reaches the rated voltage.
  • the resonance compensation circuit 3 is SS (primary side series secondary side series) / SSP (primary side)
  • SS primary side series secondary side series
  • SSP primary side
  • the series side-by-side series-parallel) composite topology switches between a constant current charging mode and a constant voltage charging mode.
  • the switch S1 When the voltage output by the second rectifier circuit does not reach the voltage target value, the switch S1 is turned off. At this time, the resonance compensation circuit 3 switches to the SS topology, and the wireless charging circuit enters the constant current charging mode. 2, the first inductor L 1 in the primary compensation module resonates with the first resonant capacitor C 1 , and the second inductor L 2 in the secondary compensation module resonates with the second resonant capacitor C 2 , and the resonant frequency Equivalent input impedance at this time Where M is the mutual inductance of the non-contact transformer, and Coupling coefficient Where n is the primary and secondary coil turns ratio of the non-contact transformer, and L M is the magnetizing inductance of the non-contact transformer.
  • the fundamental wave analysis method can calculate the current outputted by the second rectifier circuit of the constant current charging mode (when the battery is directly connected to the second rectifier circuit, the current is the battery charging current) I bat can be expressed as: Where D is the duty ratio of the input voltage U AB of the high frequency inverter circuit. It can be determined that when the SS topology satisfies the resonant frequency At the time, the battery charging current I bat is a load-independent output, that is, the wireless charging circuit can operate in the constant current mode of operation when the switch S 1 is turned off.
  • the switch S1 When the voltage output by the second rectifier circuit reaches the voltage target value, the switch S1 is closed. At this time, the resonance compensation circuit 3 switches to the SSP topology, and the wireless charging circuit enters the constant voltage charging mode. 4, the equivalent leakage inductance L l1 of the first inductor L 1 in the primary compensation module resonates with the first resonant capacitor C 1 , and the equivalent leakage inductance L l2 of the second inductor L 2 in the secondary compensation module Resonating with the second resonant capacitor C 2 , the exciting inductor L M resonating with the third resonant capacitor C 3 , the resonant frequency Equivalent input impedance at this time Where M is the mutual inductance of the non-contact transformer, and R eq is the equivalent load connected after the second rectifier circuit, Coupling coefficient n is the original secondary winding ratio of the non-contact transformer.
  • the fundamental wave analysis method can calculate the output voltage of the second rectifier circuit of the constant voltage charging mode (when the battery is directly connected to the second rectifier circuit, the voltage is the battery charging voltage) U bat can be expressed as Thus, it can be determined that when the SSP topology satisfies the resonant frequency At the time, the battery charging voltage U bat is a load-independent output, that is, the wireless charging circuit can operate in a constant voltage operating mode.
  • the SS topology only works in the constant current state, and only needs to ensure the resonance parameter of the SS in the constant current state, that is, only the first resonant capacitor needs to be resonant with the first inductor, and the second resonant capacitor and the second inductor resonate. Yes, there is no need to balance the constant pressure state.
  • the SSP topology only works in a constant voltage state, and at the voltage gain point, the circuit operates in a resonant state, so the circuit output constant voltage point is the circuit resonance point. That is to say, whether it is the SS topology or the SSP topology, it is easy to control at the resonance point, so that the wireless charging circuit has higher output power and transmission efficiency;
  • the resonant network of the wireless charging circuit works at a fixed voltage gain intersection, and the input impedance angle is zero. In this state, the switching loss is small, which is beneficial to improve the circuit. effectiveness;
  • SS/SSP topology switching requires only one switch to enable the wireless charging circuit to operate in both constant current and constant voltage.
  • the composite topology has fewer switching devices, small circuit size, and constant current constant voltage switching control.
  • FIG. 6 is a circuit diagram of a second embodiment of a wireless charging circuit of the constant current constant voltage composite topology of the present invention.
  • the first rectifier circuit is a PFC rectifier circuit.
  • the PFC rectifier circuit of the embodiment includes a diode three-phase rectifier bridge D 11 and a first group of switching devices Q 1 .
  • the second group of switching devices Q 2 , the third group of switching devices Q 3 , the first electrolytic capacitor C 11 , and the second electrolytic capacitor C 12 it should be noted that each group of switching devices is a combination of four switching tubes .
  • three-phase input of the diode rectifier bridge 11 are respectively connected D-phase AC voltage
  • the three-phase diode rectifier bridge D is connected to positive bus terminal 11 of the first positive electrode of the electrolytic capacitor C 11, C 11 of the first electrolytic capacitor a second negative electrolytic capacitor C connected to the positive electrode 12, a second electrolytic capacitor C connected to the negative-phase diode bridge rectifier D negative bus line 11 of the end 12,
  • a first set of the switching device Q 1 is connected to a first end of a three-phase diode bridge rectifier D a first input terminal 11,
  • a second set of a first switching device Q 2 is connected to a second input terminal of the diode bridge three-phase rectifier 11 D
  • the third set of the switching device Q is connected to a first end of the 3-phase diode bridge rectifier D the third input terminal 11, a first end of the second group of the switching device Q 1, a second group of a second switching device Q 2 terminal, the third terminal of the third switching device Q group 3 are connected to the negative electrode
  • the high frequency inverter circuit 2 includes a first switching transistor Q 4 and a second switching transistor Q 5 , wherein the first end of the first switching transistor Q 4 is connected to the positive bus terminal of the first rectifier circuit.
  • the first end of the second switch tube Q 5 is connected to the negative bus end of the first rectifier circuit, and the second end of the first switch tube Q 4 and the second end of the second switch tube Q 5 are respectively connected to the first resonant capacitor C 1
  • the first end of the first inductor L 1 is connected to the negative end of the first electrolytic capacitor C 11 .
  • the first switching transistor Q 4 and the second switching transistor Q 5 are alternately turned on. When the first switching transistor Q 4 is turned on, the positive bus bar provides energy; when the second switching transistor Q 5 is turned on, The negative bus provides energy.
  • the circuit can be operated in a constant current or constant voltage working state, the number of required switches is small, the circuit volume is small, the control is simple, and the circuit output power and transmission efficiency are high.

Abstract

一种恒流恒压复合拓扑的无线充电电路，在该无线充电电路中，原边补偿模块（31）包括第一电感（L 1）和第一谐振电容（C 1），第一谐振电容（C 1）的第一端连接高频逆变电路（2）的第一输出端，第一谐振电容（C 1）的第二端连接第一电感（L 1）的第一端，第一电感（L 1）的第二端连接高频逆变电路（2）的第二输出端；副边补偿模块（32）包括第二电感（L 2）、第二谐振电容（C 2）、第三谐振电容（C 3）及开关（S 1），第二谐振电容（C 2）的第一端连接第二整流电路（4）的第一输入端，第二谐振电容（C 2）的第二端连接第二电感（L 2）的第一端，第二电感（L 2）的第二端连接第二整流电路（4）的第二输入端，开关（S 1）和第三谐振电容（C 3）串联在第二谐振电容（C 2）的第一端与第二电感（L 2）的第二端之间。该恒流恒压复合拓扑的无线充电电路的开关数量少、电路体积小、控制简单，且输出功率及传输效率高。

Description

一种恒流恒压复合拓扑的无线充电电路 技术领域
本发明涉及无线充电领域，尤其涉及一种恒流恒压复合拓扑的无线充电电路。
背景技术
为减少环境污染和缓减能源短缺的危机，电动汽车的发展受到了世界的普遍关注，解决电动汽车电池充电的问题也成为社会研究的热点。电动汽车电池充电方法有传统的接触式充电和非接触式充电。与传统接触式充电方式相比，无线充电可避免电火花危险、减少导线损耗、降低车体重量、具有安全可靠性高等优点，并可应用于矿场、海底等一些特殊场合。
松耦合变压器是无线充电的核心元件，其分离的原、副边绕组及较大的距离使其相比紧耦合变压器具有漏感大、激磁电感小的缺点，故补偿网络成为无线充电电路的研究重点，松耦合变压器必须采用多元件谐振变换器，对漏感和激磁电感分别补偿，提高电压增益和功率传输能力，减小环流损耗。而在蓄电池充电过程中，恒流恒压阶段是充电的重要阶段，通过对补偿网络进行参数整定、拓扑切换和控制等方式可使无线充电系统工作在恒流恒压状态。
传统的在无线充电系统副边电路加入斩波控制环节，通过控制斩波电路，实现稳压输出。虽然达到电压独立负载输出，但在无线电能传输整个拓扑电路中多加了一级电路，使系统的传输效率降低。或者在串/串补偿(S/S)(或者其他单一补偿拓扑)拓扑下，在不增加控制的前提下，通过改变电路参数，在两种不同参数下实现恒流恒压输出。但是实际应用中线圈自感在频率变化时也随之变化，控制系统工作在谐振点处较困难。例如，中国专利CN 104753152A公开了一种恒流-恒压复合拓扑的感应式充电系统，该方式可使系统在串/串补偿(S/S)拓扑电路中实现恒流输出，而在并/串补偿(P/S)拓扑电路中实现恒压输出。虽然该混合拓扑电路可以实现为电池恒流恒压充电，但是在实际应用中要根据副边电池两端电压控制原边谐振电容的切换，因此增加了系统成本和控制难度。
综上可见，现有技术存在以下三个问题：
(1)额外增加功率变换电路以达到系统的恒压或恒流控制，增加了电路体积，传输效率较低；
(2)单一拓扑控制下，系统较难工作在谐振点处，影响系统功率和效率；
(3)SS/PS可实现电池恒流恒压充电，但两级控制系统成本高，难度大。
发明内容
本发明要解决的技术问题在于，针对现有技术的上述变换机构级联、控制复杂、电路体积大、切换开关繁杂的缺陷，提供一种恒流恒压复合拓扑的无线充电电路。
本发明解决其技术问题所采用的技术方案是：构造一种恒流恒压复合拓扑的无线充电电路，包括依次连接的第一整流电路、高频逆变电路、谐振补偿电路、第二整流电路，所述谐振补偿电路包括原边补偿模块和副边补偿模块，其中，
所述原边补偿模块包括第一电感和第一谐振电容，而且，所述第一谐振电容的第一端连接所述高频逆变电路的第一输出端，所述第一谐振电容的第二端连接所述第一电感的第一端，所述第一电感的第二端连接所述高频逆变电路的第二输出端；
所述副边补偿模块包括第二电感、第二谐振电容、第三谐振电容及开关，而且，所述第二谐振电容的第一端连接所述第二整流电路的第一输入端，所述第二谐振电容的第二端连接所述第二电感的第一端，所述第二电感的第二端连接所述第二整流电路的第二输入端，所述开关和所述第三谐振电容串联在所述第二谐振电容的第一端与所述第二电感的第二端之间；
而且，所述开关在所述第二整流电路所输出的电压未达到电压目标值时断开，无线充电电路处于恒流工作模式，所述开关在所述第二整流电路所输出的电压达到电压目标值时闭合，无线充电电路处于恒压工作模式。
优选地，所述高频逆变电路为正激变换电路、反激变换电路、推挽式逆变电路、半桥逆变电路或全桥逆变电路。
优选地，所述第一整流电路为PFC整流电路。
优选地，所述PFC整流电路包括二极管三相整流桥、第一组开关器件、第二组开关器件、第三组开关器件、第一电解电容、第二电解电容，而且，所述二极管三相整流桥的三个输入端分别接入三相交流电压，所述二极管三相整流桥的正母线端连接所述第一电解电容的正极，所述第一电解电容的负极连接所述第二电解电容的正极，所述第二电解电容的负极连接所述二极管三相整流桥的负母线端，所述第一组开关器件的第一端连接所述二极管三相整流桥的第一输入端，所述第二组开关器件的第一端连接所述二极管三相整流桥的第二输入端，所述第三组开关器件的第一端连接所述二极管三相整流桥的第三输入端，所述第一组开关器件的第二端、所述第二组开关器件的第二端、所述第三组开关器件的第二端分别连接所述第一电解电容的负极。
优选地，所述高频逆变电路包括第一开关管和第二开关管，其中，所述第一开关管的第一端连接所述第一整流电路的正母线端，所述第二开关管的第一端连接所述第一整流电路的负 母线端，所述第一开关管的第二端及所述第二开关管的第二端分别连接所述第一谐振电容的第一端，所述第一电感的第二端连接所述第一电解电容的负端。
优选地，还包括与所述第二整流电路相连接的等效负载电路。
优选地，所述等效负载电路包括蓄电池。
优选地，所述等效负载电路还包括连接在所述第二整流电路和所述蓄电池之间的功率转换电路。
实施本发明的技术方案，具有以下有益效果：
1.该无线充电电路中的谐振补偿电路不管是SS拓扑还是SSP拓扑，均易控制在谐振点处，使无线充电电路具备较高的输出功率和传输效率；
2.在恒流恒压充电模式的切换过程中，该无线充电电路的谐振网络均工作在固定的电压增益交点处，输入阻抗角为零的状态，此状态下开关损耗小，有益于提高无线充电电路的效率；
3.SS/SSP拓扑的切换仅需一个切换开关即可使该无线充电电路工作在恒流恒压两种工作状态，因此，该SS/SSP拓扑的开关器件少、电路体积小、恒流恒压切换控制较简单。
附图说明
为了更清楚地说明本发明实施例或现有技术中的技术方案，下面将对实施例或现有技术描述中所需要使用的附图作简单地介绍，显而易见地，下面描述中的附图仅仅是本发明的一些实施例，对于本领域普通技术人员来讲，在不付出创造性劳动的前提下，还可以根据这些附图获得其他的附图。附图中：
图1是本发明恒流恒压复合拓扑的无线充电电路实施例一的电路图；
图2是图1中的无线充电电路在恒流充电模式下的电路图；
图3是在负载突变前后图2中的无线充电电路的第二整流电路的电流波形图；
图4是图1中的无线充电电路在恒压充电模式下的电路图；
图5是在负载突变前后图4中的无线充电电路的第二整流电路的电压波形图；
图6是本发明恒流恒压复合拓扑的无线充电电路实施例二的电路图；
图7是图6中的无线充电电路的第一整流电路实施例一的电路图。
具体实施方式
图1是本发明恒流恒压复合拓扑的无线充电电路实施例一的电路图，该实施例的无线充 电电路包括依次连接的第一整流电路1、高频逆变电路2、谐振补偿电路3、第二整流电路4和等效负载电路5。
在该实施例中，第一整流电路1用于将单相市电变换成直流电压，当然，在其它实施例中，若输入电压为三相交流市电，则该第一整流电路1可为三相的整流电路。另外，优选地，该第一整流电路1为PFC整流电路。
在该实施例中，高频逆变电路2为全桥逆变电路，且用于将第一整流电路输出的直流电转换为高频交流信号。当然，在其它实施例中，该高频逆变电路2还可为正激变换电路、反激变换电路、推挽式逆变电路、半桥逆变电路等。
在该实施例中，谐振补偿电路3包括原边补偿模块31和副边补偿模块32。其中，原边补偿模块31包括第一电感L1和第一谐振电容C1，副边补偿模块32包括第二电感L2、第二谐振电容C2、第三谐振电容C3及开关S1，而且，第一电感L1和第二电感L2相耦合，以组成非接触变压器。其中，在原边补偿模块31中，第一谐振电容C1的第一端连接高频逆变电路2的第一输出端，第一谐振电容C1的第二端连接第一电感L1的第一端，第一电感L1的第二端连接高频逆变电路2的第二输出端。在副边补偿模块32中，第二谐振电容C2的第一端连接第二整流电路4的第一输入端，第二谐振电容C2的第二端连接第二电感L2的第一端，第二电感L2的第二端连接第二整流电路4的第二输入端，开关S1的第一端连接第二谐振电容C2的第一端，开关S1的第二端通过第三谐振电容C3连接第二电感L2的第二端。当然，在另一个实施例中，开关S1与第三谐振电容C3的位置可互换。
在该实施例中，第二整流电路4用于将所耦合的高频交流信号转换成直流信号，该第二整流电路4可包括与之匹配的整流和滤波电路等。
另外，关于等效负载电路5，在一个可选实施例中，其可具体包括蓄电池，该蓄电池直接与第二整流电路的输出端相连。当然，在另一个可选实施例中，还可进一步包括功率转换电路，该功率转换电路连接在第二整流电路和蓄电池之间，用于将第二整流电路输出的电压电流信号转换成蓄电池所需的电压电流信号。
在该实施例中，开关S1在第二整流电路4所输出的电压未达到电压目标值时断开，此时，该无线充电电路处于恒流工作模式，开关S1在第二整流电路4所输出的电压达到电压目标值时闭合，此时，无线充电电路处于恒压工作模式。其中，电压目标值为当蓄电池达到额定电压时，第二整流电路的输出所对应的电压。
在图1所示的无线充电电路中，谐振补偿电路3为SS(原边串联副边串联)/SSP(原边 串联副边串并联)复合拓扑，其可在恒流充电模式和恒压充电模式之间切换。
当第二整流电路所输出的电压未达到电压目标值时，开关S1断开，此时，谐振补偿电路3切换到SS拓扑，该无线充电电路进入恒流充电模式。结合图2，原边补偿模块中的第一电感L1与第一谐振电容C1发生谐振，副边补偿模块中的第二电感L2与第二谐振电容C2发生谐振，谐振频率
Figure PCTCN2017090443-appb-000001
此时的等效输入阻抗
Figure PCTCN2017090443-appb-000002
其中，M为非接触变压器的互感，且
Figure PCTCN2017090443-appb-000003
耦合系数
Figure PCTCN2017090443-appb-000004
其中n为非接触变压器原副边线圈匝比，LM为非接触变压器的激磁电感。另外，由基波分析法可推算出该恒流充电模式的第二整流电路输出的电流(当蓄电池直接与第二整流电路相连时，该电流为蓄电池充电电流)Ibat可表示为：
Figure PCTCN2017090443-appb-000005
其中，D为高频逆变电路的输入电压UAB的占空比。由此可确定，当该SS拓扑满足谐振频率
Figure PCTCN2017090443-appb-000006
时，蓄电池充电电流Ibat是一个与负载无关的输出量，即，无线充电电路在开关S1断开时可工作在恒流工作模式。
通过对图2中的第二整流电路的输出电流进行负载突变前后的仿真，仿真结果如图3所示，当在0.006s时突减负载，输出电流Ibat有波动，但该波动维持约1ms后趋于稳定，且负载突变前后电流幅值不变，即，该无线充电电路可工作在恒流工作状态。
当第二整流电路所输出的电压达到电压目标值时，开关S1闭合，此时，谐振补偿电路3切换到SSP拓扑，该无线充电电路进入恒压充电模式。结合图4，原边补偿模块中的第一电感L1的等效漏感Ll1与第一谐振电容C1发生谐振，副边补偿模块中的第二电感L2的等效漏感Ll2与第二谐振电容C2发生谐振，激磁电感LM与第三谐振电容C3发生谐振，谐振频率
Figure PCTCN2017090443-appb-000007
此时的等效输入阻抗
Figure PCTCN2017090443-appb-000008
其中M为非接触变压器的互感，Req为第二整流电路后所接的等效负载，
Figure PCTCN2017090443-appb-000009
耦合系数
Figure PCTCN2017090443-appb-000010
n为非接触变压器原副边线圈匝比。其中，第一电感L1、第二电感L2与等效漏感Ll1、Ll2的关系为：L1＝Ll1+LM，L2＝Ll2+n2LM。另外，由基波分析法可推算出该恒压充电模式的第二整流电路的输出电压(当 蓄电池直接与第二整流电路相连时，该电压为蓄电池充电电压)Ubat可表示为
Figure PCTCN2017090443-appb-000011
由此，可确定出当SSP拓扑满足谐振频率
Figure PCTCN2017090443-appb-000012
时，蓄电池充电电压Ubat是一个与负载无关的输出量，即，无线充电电路可工作在恒压工作模式。
通过对图4所示的第二整流电路的输出电压进行负载突变前后的仿真，仿真结果如图5所示，当在仿真时间0.005s时突减负载，输出电压Ubat有波动，但该波动维持约2ms后趋于稳定，且负载突变前后电压幅值不变，即，该无线充电电路工作在恒压工作状态。
通过实施上述实施例的技术方案，由于将SS拓扑和SSP拓扑两种谐振补偿拓扑结合到同一个无线充电电路中，并通过开关切换该无线充电电路工作在恒流或恒压工作模式，所以，具有以下效果：
1.SS拓扑只工作在恒流状态下，只需保证SS配置在恒流状态的谐振参数，即，只需要保证第一谐振电容与第一电感谐振，第二谐振电容与第二电感谐振即可，无需兼顾恒压状态。而SSP拓扑只工作在恒压状态下，而且，在电压增益点处，电路工作于谐振状态，故电路输出恒压点即为电路谐振点。也就是说，不管是SS拓扑还是SSP拓扑，均易控制在谐振点处，使无线充电电路具备较高的输出功率和传输效率；
2.在恒流恒压充电模式的切换过程中，该无线充电电路的谐振网络均工作在固定的电压增益交点处，输入阻抗角为零的状态，此状态下开关损耗小，有益于提高电路效率；
3.SS/SSP拓扑的切换仅需一个切换开关即可使该无线充电电路工作在恒流恒压两种工作状态。该复合拓扑的开关器件少、电路体积小、恒流恒压切换控制较简单。
图6是本发明恒流恒压复合拓扑的无线充电电路实施例二的电路图。该实施例中，第一整流电路为PFC整流电路。
图7是图6中的无线充电电路的第一整流电路实施例一的电路图，如图7所示，该实施例中PFC整流电路包括二极管三相整流桥D11、第一组开关器件Q1、第二组开关器件Q2、第三组开关器件Q3、第一电解电容C11、第二电解电容C12，此处需说明的是，每组开关器件均为四个开关管的组合。而且，二极管三相整流桥D11的三个输入端分别接入三相交流电压，二极管三相整流桥D11的正母线端连接第一电解电容C11的正极，第一电解电容C11的负极连接第二电解电容C12的正极，第二电解电容C12的负极连接二极管三相整流桥D11的负母线端，第一组开关器件Q1的第一端连接二极管三相整流桥D11的第一输入端，第二组开关器件Q2的 第一端连接二极管三相整流桥D11的第二输入端，第三组开关器件Q3的第一端连接二极管三相整流桥D11的第三输入端，第一组开关器件Q1的第二端、第二组开关器件Q2的第二端、第三组开关器件Q3的第三端分别连接第一电解电容的负极。
进一步地，当第一整流电路的电路结构为图7所示的结构时，由于第一整流电路输出为正负母线，因此高频逆变电路不需要采用全桥逆变，采用半桥逆变即可，结合图6，该高频逆变电路2包括第一开关管Q4和第二开关管Q5，其中，第一开关管Q4的第一端连接第一整流电路的正母线端，第二开关管Q5的第一端连接第一整流电路的负母线端，第一开关管Q4的第二端及第二开关管Q5的第二端分别连接第一谐振电容C1的第一端，第一电感L1的第二端连接第一电解电容C11的负端。在该实施例中，第一开关管Q4和第二开关管Q5交替导通，当第一开关管Q4导通时，正母线提供能量；当第二开关管Q5导通时，负母线提供能量。
采用本申请的上述实施例，可使电路工作在恒流或恒压工作状态，所需开关数量少、电路体积小、控制简单，电路输出功率和传输效率较高。
以上所述仅为本发明的优选实施例而已，并不用于限制本发明，对于本领域的技术人员来说，本发明可以有各种更改和变化。凡在本发明的精神和原则之内，所作的任何纂改、等同替换、改进等，均应包含在本发明的权利要求范围之内。

Claims (8)

  1. 一种恒流恒压复合拓扑的无线充电电路，包括依次连接的第一整流电路、高频逆变电路、谐振补偿电路、第二整流电路，其特征在于，所述谐振补偿电路包括原边补偿模块和副边补偿模块，其中，
    所述原边补偿模块包括第一电感和第一谐振电容，而且，所述第一谐振电容的第一端连接所述高频逆变电路的第一输出端，所述第一谐振电容的第二端连接所述第一电感的第一端，所述第一电感的第二端连接所述高频逆变电路的第二输出端；
    所述副边补偿模块包括第二电感、第二谐振电容、第三谐振电容及开关，而且，所述第二谐振电容的第一端连接所述第二整流电路的第一输入端，所述第二谐振电容的第二端连接所述第二电感的第一端，所述第二电感的第二端连接所述第二整流电路的第二输入端，所述开关和所述第三谐振电容串联在所述第二谐振电容的第一端与所述第二电感的第二端之间；
    而且，所述开关在所述第二整流电路所输出的电压未达到电压目标值时断开，无线充电电路处于恒流工作模式，所述开关在所述第二整流电路所输出的电压达到电压目标值时闭合，无线充电电路处于恒压工作模式。
  2. 根据权利要求1所述的恒流恒压复合拓扑的无线充电电路，其特征在于，所述高频逆变电路为正激变换电路、反激变换电路、推挽式逆变电路、半桥逆变电路或全桥逆变电路。
  3. 根据权利要求1所述的恒流恒压复合拓扑的无线充电电路，其特征在于，所述第一整流电路为PFC整流电路。
  4. 根据权利要求3所述的恒流恒压复合拓扑的无线充电电路，其特征在于，所述PFC整流电路包括二极管三相整流桥、第一组开关器件、第二组开关器件、第三组开关器件、第一电解电容、第二电解电容，而且，所述二极管三相整流桥的三个输入端分别接入三相交流电压，所述二极管三相整流桥的正母线端连接所述第一电解电容的正极，所述第一电解电容的负极连接所述第二电解电容的正极，所述第二电解电容的负极连接所述二极管三相整流桥的负母线端，所述第一组开关器件的第一端连接所述二极管三相整流桥的第一输入端，所述第二组开关器件的第一端连接所述二极管三相整流桥的第二输入端，所述第三组开关器件的第一端连接所述二极管三相整流桥的第三输入端，所述第一组开关器件的第二端、所述第二组开关器件的第二端、所述第三组开关器件的第二端分别连接所述第一电解电容的负极。
  5. 根据权利要求4所述的恒流恒压复合拓扑的无线充电电路，其特征在于，所述高频逆变电路包括第一开关管和第二开关管，其中，所述第一开关管的第一端连接所述第一整流电路的正母线端，所述第二开关管的第一端连接所述第一整流电路的负母线端，所述第一开关管的 第二端及所述第二开关管的第二端分别连接所述第一谐振电容的第一端，所述第一电感的第二端连接所述第一电解电容的负端。
  6. 根据权利要求1所述的恒流恒压复合拓扑的无线充电电路，其特征在于，还包括与所述第二整流电路相连接的等效负载电路。
  7. 根据权利要求6所述的恒流恒压复合拓扑的无线充电电路，其特征在于，所述等效负载电路包括蓄电池。
  8. 根据权利要求7所述的恒流恒压复合拓扑的无线充电电路，其特征在于，所述等效负载电路还包括连接在所述第二整流电路和所述蓄电池之间的功率转换电路。
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