WO2018066419A1 - アンテナ装置 - Google Patents

アンテナ装置 Download PDF

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Publication number
WO2018066419A1
WO2018066419A1 PCT/JP2017/034828 JP2017034828W WO2018066419A1 WO 2018066419 A1 WO2018066419 A1 WO 2018066419A1 JP 2017034828 W JP2017034828 W JP 2017034828W WO 2018066419 A1 WO2018066419 A1 WO 2018066419A1
Authority
WO
WIPO (PCT)
Prior art keywords
patch
antenna device
ground plane
additional conductor
area
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/JP2017/034828
Other languages
English (en)
French (fr)
Japanese (ja)
Inventor
杉本　勇次
小出　士朗
博之 泉
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Denso Corp
Original Assignee
Denso Corp
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Denso Corp filed Critical Denso Corp
Publication of WO2018066419A1 publication Critical patent/WO2018066419A1/ja
Priority to US16/373,675 priority Critical patent/US11005171B2/en
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/42—Housings not intimately mechanically associated with radiating elements, e.g. radome
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/48—Earthing means; Earth screens; Counterpoises
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/08—Radiating ends of two-conductor microwave transmission lines, e.g. of coaxial lines, of microstrip lines
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/10—Resonant slot antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/0006—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices
    • H01Q15/0086—Devices acting selectively as reflecting surface, as diffracting or as refracting device, e.g. frequency filtering or angular spatial filtering devices said selective devices having materials with a synthesized negative refractive index, e.g. metamaterials or left-handed materials
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna

Definitions

  • the present disclosure relates to an antenna device having a flat plate structure using zeroth-order resonance, which is an applied technology of metamaterials.
  • a flat metal conductor (hereinafter referred to as a ground plane) that is connected to an external conductor of a power feeding cable and functions as a ground, is disposed so as to face the ground plane, and is arbitrary.
  • an antenna device including a flat metal conductor (hereinafter referred to as a patch portion) provided with a feeding point at a position and a short-circuit portion that electrically connects the ground plane and the patch portion (for example, Patent Document 1).
  • parallel resonance is generated at a frequency corresponding to the capacitance and the inductance by the capacitance formed between the ground plane and the patch portion and the inductance provided in the short-circuit portion.
  • the capacitance formed between the ground plane and the patch part is determined according to the area of the patch part.
  • the antenna device having the above-described configuration adjusts the area of the patch part or adjusts the distance between the ground plane and the patch part, so that the frequency to be transmitted / received in the antenna device (hereinafter, the target frequency) is desired. It can be a frequency.
  • Patent Document 1 discloses a configuration in which a spiral pattern as a helical load is provided in a portion connected to the short-circuit portion on the ground plane.
  • the fact that the target frequency can be reduced while maintaining the area of the patch part means that the area of the patch part can be reduced when the same frequency is set as the target frequency.
  • the fact that the area of the patch portion can be reduced means that the area of the antenna device in the top view (hereinafter referred to as the antenna area) can be reduced. That is, the configuration of Patent Document 1 can also be used to reduce the antenna area.
  • the antenna device is desired to be further downsized.
  • an inductance is increased by providing a spiral pattern on the ground plane, and a reduction in antenna area is realized. Therefore, in order to further reduce the antenna area using the configuration of Patent Document 1, it is necessary to increase the number of turns (so-called number of turns) of the spiral pattern.
  • Patent Literature 1 increases the inductance while decreasing the capacitance.
  • the Q value indicating the sharpness of the resonance peak is increased, and the robustness as the antenna device is lowered. This is because the Q value increases as the inductance increases and the capacitance decreases as shown in the following formula.
  • R represents a pure resistance value
  • L represents an inductance
  • C represents a capacitance.
  • the present disclosure has been made based on this situation, and an object of the present disclosure is to provide an antenna device capable of reducing the antenna area while suppressing an increase in the Q value.
  • One aspect of the present disclosure for achieving the object includes a ground plate that is a plate-like conductor member, and a patch portion that is a plate-like conductor member disposed so as to face the ground plate with a predetermined interval therebetween.
  • a short-circuit portion that is a conductor member that electrically connects the patch portion and the ground plate, and a plate-like shape that is disposed on the side where the ground plate is not disposed with respect to the patch portion so as to face the patch portion at a predetermined interval
  • an additional conductor that is a conductor member of the antenna, and parallel resonance using an inductance provided in the short-circuit portion, a capacitance formed by the ground plane and the patch portion, and a capacitance formed by the patch portion and the additional conductor. It is characterized by.
  • the short-circuit part has a predetermined inductance corresponding to its length, and the patch part forms a capacitance according to its area with the ground plane.
  • the capacitance formed by the ground plane and the patch portion is connected in parallel with the inductance derived from the short-circuit portion.
  • the additional conductor forms a capacitance between the patch portion and the patch portion according to the distance from the patch portion and the area of the additional conductor.
  • the electrostatic capacitance derived from the patch portion and the additional conductor is connected in parallel to the electrostatic capacitance formed between the ground plane and the patch portion in the equivalent circuit of the antenna device.
  • the total value of the electrostatic capacitance derived from the ground plane and the patch portion and the electrostatic capacitance derived from the patch portion and the additional conductor is an electrostatic capacitance that causes parallel resonance at the inductance and target frequency of the short-circuit portion. It only needs to be capacity. That is, according to the said structure, the area of a patch part can be made small compared with the conventional structure which uses the same frequency as an object frequency. As described above, the reduction in the area of the patch portion leads to a reduction in the antenna area.
  • the conventional structure here refers to the structure which does not provide an additional conductor above a patch part.
  • the upper side of the patch part is the side where the ground plane does not exist for the patch part.
  • the reduction of the antenna area by the above configuration is achieved by increasing the capacitance, it is not necessary to increase the inductance. Therefore, the antenna area can be reduced while suppressing an increase in the Q value.
  • FIG. 1 is a schematic external perspective view of an antenna device 100.
  • FIG. FIG. 2 is a cross-sectional view of the antenna device 100 taken along line II-II shown in FIG. 2 is an equivalent circuit diagram of the antenna device 100.
  • FIG. It is the figure which showed the structure of the antenna apparatus 100X as a comparison structure.
  • 5 is a graph showing a relationship between an area ratio of an additional conductor 30 to a patch unit 20 and a parallel resonance frequency.
  • FIG. 11 is a diagram illustrating a schematic configuration of an antenna device 100 according to Modification 1.
  • FIG. 10 is a diagram illustrating a schematic configuration of an antenna device 100 according to Modification 2.
  • FIG. 11 is a diagram illustrating a schematic configuration of an antenna device 100 according to Modification 3.
  • FIG. 1 is an external perspective view showing an example of a schematic configuration of an antenna device 100 according to the present embodiment.
  • 2 is a cross-sectional view of antenna device 100 taken along the line II-II shown in FIG.
  • the antenna device 100 is configured to transmit and receive radio waves having a predetermined target frequency.
  • the antenna device 100 may be used for only one of transmission and reception.
  • the target frequency is 850 MHz as an example here.
  • the target frequency may be appropriately designed, and as another aspect, for example, 300 MHz, 760 MHz, 900 MHz, 5.9 GHz, or the like may be used.
  • the antenna device 100 can transmit and receive not only the target frequency but also a radio wave having a frequency within a predetermined range before and after the target frequency.
  • the frequency band in which the antenna device 100 can be transmitted and received is also referred to as an operation band.
  • the antenna device 100 is connected to a radio device (not shown) via, for example, a coaxial cable, and signals received by the antenna device 100 are sequentially output to the radio device.
  • the antenna device 100 converts an electric signal input from the wireless device into a radio wave and radiates it into space.
  • the wireless device uses a signal received by the antenna device 100 and supplies high-frequency power corresponding to the transmission signal to the antenna device 100.
  • the antenna device 100 and the wireless device are assumed to be connected by a coaxial cable.
  • other known communication cables such as a feeder line may be used for connection.
  • the antenna device 100 and the wireless device may be configured to be connected via a known matching circuit or filter circuit in addition to the coaxial cable.
  • the antenna device 100 includes a ground plane 10, a patch portion 20, an additional conductor 30, a first support portion 40, a second support portion 50, a short-circuit portion 60, and a feed line 70.
  • the side on which the patch part 20 and the additional conductor 30 are provided with respect to the ground plane 10 is the upper side for the antenna device 100.
  • the ground plane 10 is a plate-like (including foil) conductor member made of a conductor such as copper.
  • the ground plane 10 is electrically connected to the outer conductor of the coaxial cable, and provides a ground potential (in other words, a ground potential) in the antenna device 100.
  • the ground plane 10 should just be provided with the magnitude
  • the area of the ground plane 10 is preferably at least larger than the patch portion 20 and 1.5 times or more the area of the patch portion 20.
  • the ground plane 10 is assumed to have an area equivalent to 1.8 times the patch portion 20.
  • the shape of the main plate 10 viewed from the upper side may be appropriately designed.
  • the planar shape of the ground plane 10 is a square shape.
  • the planar shape of the ground plane 10 may be a rectangular shape or other polygonal shapes. Further, it may be circular (including an ellipse).
  • the shape which combined the linear part and the curved part may be sufficient.
  • the patch part 20 is a plate-like conductor member made of a conductor such as copper.
  • the patch unit 20 is disposed so as to face the ground plane 10 via the first support unit 40.
  • the planar shape of the patch portion 20 is a square, but may be a rectangle or a shape other than a rectangle (for example, a circle or an octagon).
  • the notch part and the slit may be provided in a part.
  • a notch as a degenerate separation element may be provided in a pair of diagonal portions.
  • the additional conductor 30 is a plate-like (including foil) conductor member made of a conductor such as copper.
  • the additional conductor 30 is disposed so as to face the patch portion 20 with a predetermined interval through the second support portion 50.
  • the additional conductor 30 is preferably larger than the patch portion 20 so as to cover the patch portion 20 in a top view.
  • the planar shape of the additional conductor 30 is a shape in which the patch portion 20 is similarly enlarged so that the area of the additional conductor 30 is 1.2 times the area of the patch portion 20.
  • the additional conductor 30 is arranged so that the center thereof overlaps with the center of the patch portion 20 (hereinafter referred to as patch center point) in a top view.
  • the center of the additional conductor 30 and the patch center point may be points corresponding to the center of gravity. Since the additional conductor 30 of this embodiment has a square shape, the center of the additional conductor 30 corresponds to the intersection of square diagonal lines. Moreover, since the patch part 20 of this embodiment is square shape, a patch center point is equivalent to the intersection of a square diagonal line.
  • the planar shape of the additional conductor 30 is a similar shape of the patch portion 20, but is not limited thereto.
  • the planar shape of the additional conductor 30 may be a quadrangle other than a square, or may be another polygonal shape. Moreover, circular shape may be sufficient. Further, the additional conductor 30 may be smaller than the patch portion 20 as will be described later as a first modification.
  • the 1st support part 40 is a member for arrange
  • the first support portion 40 may be realized using a dielectric such as resin.
  • the surface on which the patch portion 20 is disposed is referred to as a patch side surface
  • the surface on which the ground plane 10 is disposed is referred to as a ground plane side surface.
  • the first support portion 40 is a plate-like member having a thickness such that the distance between the base plate 10 and the patch portion 20 is H1.
  • the interval H1 only needs to be sufficiently small with respect to the wavelength of the radio wave of the target frequency (hereinafter referred to as the target wavelength), and a specific value may be appropriately determined by simulation or a test.
  • the 1st support part 40 should just fulfill
  • the first support portion 40 may be a plurality of pillars that support the base plate 10 and the patch portion 20 so as to face each other with a predetermined interval H1.
  • the structure with which resin as the 1st support part 40 was filled between the ground plane 10 and the patch part 20 in this embodiment is employ
  • the space between the base plate 10 and the patch portion 20 may be hollow or vacuum. Furthermore, the structures exemplified above may be combined.
  • the interval H1 functions as a parameter for adjusting the length of the short-circuit portion 60 (in other words, the inductance provided by the short-circuit portion 60) as will be described later.
  • the interval H1 also functions as a parameter for adjusting the capacitance formed when the ground plane 10 and the patch portion 20 face each other.
  • the interval H1 is preferably at least one-tenth of the target wavelength. For example, it may be set to 1/50 or 1/100 of the target wavelength.
  • the second support part 50 is a member for arranging the patch part 20 and the additional conductor 30 so as to face each other with a predetermined interval H2.
  • the second support 50 may be realized using a dielectric such as resin.
  • the second support portion 50 is a plate-like member having a thickness such that the distance between the patch portion 20 and the additional conductor 30 is H2. By adjusting the thickness of the second support portion 50, the distance H2 between the patch portion 20 and the additional conductor 30 can be adjusted.
  • the 2nd support part 50 should just fulfill
  • the second support portion 50 may be a plurality of pillars that support the patch portion 20 and the additional conductor 30 so as to face each other with a predetermined interval H2. Further, in the present embodiment, a configuration in which the resin as the second support portion 50 is filled between the patch portion 20 and the additional conductor 30 is employed, but is not limited thereto.
  • the patch 20 and the additional conductor 30 may be hollow or vacuum.
  • the interval H2 also functions as a parameter for adjusting the capacitance formed by the patch portion 20 and the additional conductor 30 facing each other.
  • the interval H2 only needs to be sufficiently small with respect to the target wavelength in the same manner as the interval H1, and a specific value may be appropriately determined by simulation or test.
  • the short-circuit portion 60 is a conductive member that electrically connects the ground plane 10 and the patch portion 20.
  • the short circuit part 60 should just be implement
  • a via provided in the printed wiring board may function as the short-circuit portion 60.
  • the short-circuit portion 60 is a linear member having one end electrically connected to the ground plane 10 and the other end electrically connected to the patch portion 20.
  • the short-circuit part 60 is provided so as to be located at the patch center point. Note that the short-circuit portion 60 is not necessarily arranged at the patch center point. If it is arranged at a position other than the patch center point, a directivity bias according to the amount of deviation from the patch center point occurs. In a range where the directivity deviation falls within a predetermined allowable range, the short-circuit portion 60 may be disposed at a position shifted from the patch center point.
  • the power supply line 70 is a microstrip line provided on the patch side surface of the first support part 40 in order to supply power to the patch part 20.
  • One end of the feed line 70 is electrically connected to the inner conductor of the coaxial cable, and the other end is electrically connected to the patch unit 20.
  • a connecting portion between the feeding line 70 and the patch unit 20 corresponds to a feeding point for the patch unit 20.
  • the connection part of the feed line 70 and the patch part 20 may be provided with a predetermined interval at which the feed line 70 and the patch part 20 are electromagnetically coupled at the target frequency.
  • the antenna device 100 described above is used in a moving body such as a vehicle, for example.
  • the ground plate 10 may be installed on the roof portion of the vehicle so that the ground plate 10 is substantially horizontal and the direction from the ground plate 10 toward the patch portion 20 is substantially coincident with the zenith direction. .
  • FIG. 3 shows an equivalent circuit of the antenna device 100.
  • the inductor L1 is an element derived from the patch unit 20 and includes an inductance corresponding to the shape of the patch unit 20.
  • the inductor L ⁇ b> 2 is an element derived from the short-circuit portion 60 and includes an inductance corresponding to the length of the short-circuit portion 60.
  • the capacitor C ⁇ b> 1 is an element corresponding to the capacitance formed by the ground plane 10 and the patch unit 20.
  • the capacitor C ⁇ b> 1 includes a capacitance according to the area of the patch unit 20 and the distance H ⁇ b> 1 between the ground plane 10 and the patch unit 20.
  • the capacitor C2 is an element corresponding to the capacitance formed by the patch unit 20 and the additional conductor 30.
  • the capacitor C ⁇ b> 2 has a capacitance according to the area of the additional conductor 30 and the distance H ⁇ b> 2 between the patch unit 20 and the additional conductor 30.
  • the capacitor C1 and the capacitor C2 can be regarded as one capacitor (hereinafter referred to as a composite capacitor) C12.
  • the capacitance of the composite capacitor C12 is the sum of the capacitance of the capacitor C1 and the capacitance of the capacitor C2.
  • the composite capacitor C12 is connected in parallel with the inductor L2. Therefore, the antenna device 100 resonates in parallel at a frequency (hereinafter referred to as a parallel resonance frequency) determined from the electrostatic capacitance included in the composite capacitor C12 and the inductance included in the inductor L2.
  • a parallel resonance frequency here corresponds to a frequency called a zeroth-order resonance frequency in the metamaterial antenna.
  • the antenna device 100 can be caused to resonate in parallel at the target frequency by adjusting the capacitance of the composite capacitor C12 and the inductance of the inductor L2 so that the parallel resonance frequency matches the target frequency. .
  • the target capacitance required for parallel resonance is calculated from the inductance included in the inductor L2 and the target frequency.
  • interval H1 of the ground plane 10 and the patch part 20 is made constant, the length of the short circuit part 60 also becomes a constant value. Therefore, the remaining parameters can be designed by setting the inductance of the inductor L2 to a constant value corresponding to the interval H1.
  • the capacitance that each of the capacitor C1 and the capacitor C2 should have is determined so that the capacitance of the composite capacitor C12 matches the target capacitance, and the shape and arrangement of the members corresponding to each capacitor are determined. do it.
  • the capacitance of the capacitor C1 can be adjusted by the area of the patch unit 20. Further, the capacitance of the capacitor C2 can be adjusted by the distance H2 and the area of the additional conductor 30.
  • each element such as the size of the patch unit 20, the size of the additional conductor 30, the distance H2 between the patch unit 20 and the additional conductor 30, and the like so that the antenna device 100 resonates in parallel at a predetermined target frequency. Adjust the arrangement accordingly.
  • the distance H1 between the ground plane 10 and the patch portion 20 may be handled as an adjustable parameter instead of a fixed value.
  • the value of the inductor L2 may be adjusted by introducing the configuration disclosed in Patent Document 1.
  • the additional conductor 30 is formed larger than the patch portion 20 (for example, the area ratio is 1.2 times) so as to cover the patch portion 20 in a top view.
  • an electric field perpendicular to the ground plane 10 is generated between the ground plane 10 and the additional conductor 30 (particularly between the ground plane 10 and the patch portion 20).
  • the vertical electric field propagates from the short-circuit portion 60 toward the outer edge portion of the patch portion 20 and the outer edge portion of the additional conductor 30.
  • the vertical electric field becomes a vertically polarized electric field and propagates through the space.
  • the antenna device 100 radiates vertically polarized waves at the outer edge portion of the additional conductor 30 in a direction orthogonal to the thickness direction of the antenna device 100 (hereinafter, centrifugal direction).
  • the antenna device 100 has the same gain in all directions from the patch center point toward the outer edge of the additional conductor 30. In particular, when the antenna device 100 is placed so that the ground plane 10 is horizontal, the antenna device 100 operates as a non-directional metamaterial antenna in the horizontal direction.
  • the antenna device 100X as a comparative configuration includes a ground plane 10X, a patch portion 20X, a support portion 40X, a short-circuit portion 60X, and a feed line 70X. That is, the antenna device 100X as a comparative configuration corresponds to a configuration in which the additional conductor 30 and the second support portion 50 are removed from the antenna device 100 of the present embodiment.
  • the patch section 20X has the same shape and the same area as the patch section 20 of the present embodiment, and the electrostatic capacity formed between the ground plane 10X and the patch section 20X is a static included in the capacitor C1 of the present embodiment. It is equal to the capacity.
  • the inductance provided by the short-circuit portion 60X is also equal to the inductance provided by the short-circuit portion 60.
  • the support part 40 ⁇ / b> X is a member corresponding to the first support part 40. In this comparative configuration, parallel resonance is caused by the electrostatic capacitance formed between the ground plane 10X and the patch portion 20X and the inductance provided in the short-circuit portion 60X.
  • the capacitor C2 derived from the additional conductor 30 is connected in parallel to the capacitor C1 formed by the ground plane 10 and the patch portion 20.
  • the capacitance that contributes to the occurrence of parallel resonance is the total value of the capacitor C2 and the capacitor C1.
  • the capacitance connected in parallel with the inductance provided by the short-circuit portion 60 of the present embodiment is larger than the capacitance connected in parallel with the inductance provided by the short-circuit portion 60X in the comparative configuration.
  • the parallel resonant frequency F becomes low, so that the inductance L is large and the electrostatic capacitance C is large, as represented by the following formula.
  • the parallel resonance frequency of the antenna device 100 of the present embodiment is lower than the parallel resonance frequency of the antenna device 100X of the comparative configuration. That is, according to said structure, a parallel resonant frequency can be reduced compared with the comparison structure provided with the patch part 20X of the same size.
  • FIG. 5 shows the area ratio of the additional conductor 30 to the patch section 20 and the parallel resonant frequency in the antenna device 100 in which the patch section 20 and the short-circuit section 60 are designed so that the resonance frequency Fx when the additional conductor 30 is not provided is 1300 MHz. It is a graph which shows the relationship. As shown in FIG. 5, it can be seen that the parallel resonant frequency is reduced by providing the additional conductor 30. In addition, by making the area of the additional conductor 30 larger than the area of the patch portion 20 (in other words, by making the area ratio larger than 1), the parallel resonance frequency can be reduced by 100 MHz or more. In particular, the effect of reducing the parallel resonance frequency can be enhanced by setting the area ratio to 1.2 or more.
  • the capacitance formed by the ground plane 10X and the patch portion 20X is the capacitance that resonates in parallel at the target frequency and the inductance that the short-circuit portion 60X has (that is, the target capacitance).
  • the area of the patch portion 20X needs to be an area corresponding to the target capacitance.
  • the target capacitance is achieved by the sum of the capacitance of the capacitor C1 formed by the patch unit 20 and the capacitor C2 provided by the additional conductor 30. Therefore, the capacitance of the capacitor C1 formed by the patch unit 20 does not need to match the target capacitance, and the area of the patch unit 20 can be made smaller than that of the patch unit 20X having the conventional configuration.
  • the antenna area when a certain predetermined frequency is set as the target frequency, the antenna area can be reduced as compared with the comparative configuration. For example, when the target frequency is 850 MHz, the antenna area can be reduced by about 37% compared to the comparative configuration by making the additional conductor 30 of the present embodiment the same size as the ground plane 10.
  • FIG. 7 conceptually represents such an aspect.
  • 10A in FIG. 7 represents the metal part of the housing that functions as the main plate 10.
  • casing which accommodates the antenna apparatus 100 shall be formed with the raw material (for example, resin) which does not prevent propagation of an electromagnetic wave.
  • FIG. 8 conceptually represents such an aspect. 8A represents a metal portion of the housing that functions as the additional conductor 30. Note that, similarly to the second modification, the side surface portion of the housing that houses the antenna device 100 is formed of a material (for example, resin) that does not hinder the propagation of radio waves.

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PCT/JP2017/034828 2016-10-05 2017-09-27 アンテナ装置 Ceased WO2018066419A1 (ja)

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US16/373,675 US11005171B2 (en) 2016-10-05 2019-04-03 Antenna device

Applications Claiming Priority (2)

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JP2016-197466 2016-10-05
JP2016197466A JP6658439B2 (ja) 2016-10-05 2016-10-05 アンテナ装置

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US16/373,675 Continuation US11005171B2 (en) 2016-10-05 2019-04-03 Antenna device

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CN113285228A (zh) * 2020-02-19 2021-08-20 株式会社电装 天线装置

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JP7028212B2 (ja) * 2019-03-26 2022-03-02 株式会社Soken アンテナ装置
JP6962346B2 (ja) * 2019-03-26 2021-11-05 株式会社Soken アンテナ装置
JP7298517B2 (ja) * 2020-03-05 2023-06-27 株式会社デンソー 電子装置
JP7400621B2 (ja) * 2020-05-15 2023-12-19 株式会社Soken アンテナ装置
JP7294248B2 (ja) 2020-06-17 2023-06-20 株式会社Soken アンテナ装置
JP7363719B2 (ja) 2020-08-26 2023-10-18 株式会社デンソー アンテナ装置
JP7567452B2 (ja) 2020-12-23 2024-10-16 株式会社Soken 無線通信装置
JP7463980B2 (ja) 2021-02-15 2024-04-09 株式会社デンソー 無線通信機

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