WO2018020797A1 - Dispositif de conversion de puissance - Google Patents

Dispositif de conversion de puissance Download PDF

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Publication number
WO2018020797A1
WO2018020797A1 PCT/JP2017/019112 JP2017019112W WO2018020797A1 WO 2018020797 A1 WO2018020797 A1 WO 2018020797A1 JP 2017019112 W JP2017019112 W JP 2017019112W WO 2018020797 A1 WO2018020797 A1 WO 2018020797A1
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Prior art keywords
limit threshold
threshold value
detection signal
load
control
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PCT/JP2017/019112
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English (en)
Japanese (ja)
Inventor
義章 石黒
友一 坂下
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三菱電機株式会社
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Priority to JP2018529379A priority Critical patent/JP6826119B2/ja
Publication of WO2018020797A1 publication Critical patent/WO2018020797A1/fr

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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60Q—ARRANGEMENT OF SIGNALLING OR LIGHTING DEVICES, THE MOUNTING OR SUPPORTING THEREOF OR CIRCUITS THEREFOR, FOR VEHICLES IN GENERAL
    • B60Q1/00—Arrangement of optical signalling or lighting devices, the mounting or supporting thereof or circuits therefor
    • B60Q1/02—Arrangement of optical signalling or lighting devices, the mounting or supporting thereof or circuits therefor the devices being primarily intended to illuminate the way ahead or to illuminate other areas of way or environments
    • B60Q1/04—Arrangement of optical signalling or lighting devices, the mounting or supporting thereof or circuits therefor the devices being primarily intended to illuminate the way ahead or to illuminate other areas of way or environments the devices being headlights
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only

Definitions

  • the present invention relates to a power converter, and more particularly to output control of a power converter to which hysteresis control is applied.
  • a hysteresis control method is used as one aspect of output feedback control of the power converter.
  • Patent Document 1 Japanese Patent Laying-Open No. 2001-103739 (Patent Document 1) describes a power converter to which hysteresis control is applied.
  • the output of the power conversion device is compared with an upper limit threshold value and a lower limit threshold value, and on / off of the power semiconductor switching element (hereinafter also simply referred to as “switching element”) is controlled.
  • the switching frequency can be controlled by adjusting the hysteresis width corresponding to the difference between the threshold value and the lower limit threshold value.
  • the ON / OFF cycle (switching frequency) of the power semiconductor switching element is controlled by adjusting the hysteresis width in the hysteresis control.
  • digital PLL Phase Locked Loop
  • the DAC Digital to Analog Converter
  • the hysteresis width cannot be set below the minimum width restricted by the resolution of the DAC. That is, when the hysteresis width is reduced to the minimum width, the switching frequency cannot be further increased.
  • the output range (voltage range or current range) is widened, so the setting range of the upper threshold and lower threshold in hysteresis control is also widened.
  • the output range corresponding to one DAC gradation is also widened, so the hysteresis width is finely adjusted to a level sufficient to maintain the switching frequency at a predetermined level.
  • the switching frequency of the switching element to which the hysteresis control is applied fluctuates to a range where noise and electromagnetic noise are generated.
  • the present disclosure has been made to solve such a problem, and an object of the present disclosure is to appropriately control the switching frequency in the power conversion device to which hysteresis control is applied.
  • the power conversion device includes a power conversion circuit connected between the DC power supply and the load device, a detection unit, and a power supply control unit.
  • the power conversion circuit includes a switching element that increases or decreases the output to the load device according to on / off.
  • the detection unit is configured to output a first detection signal corresponding to the output from the power conversion circuit to the load device.
  • the power supply control unit is configured to control on / off of the switching element using the first detection signal.
  • the power supply control unit includes first and second hysteresis control units, an AC signal extraction unit, a control unit, and a selection unit.
  • the first hysteresis control unit generates a first control signal for controlling on / off of the switching element according to a result of comparing the first detection signal with the first upper limit threshold and the first lower limit threshold.
  • the AC component extraction unit is configured to output a second detection signal obtained by extracting an AC component of the first detection signal.
  • the second hysteresis control unit generates a second control signal for controlling on / off of the switching element according to a result of comparing the second detection signal with the second upper limit threshold and the second lower limit threshold. Configured as follows.
  • the control unit changes the first upper limit threshold and the first lower limit threshold in accordance with a change in the operating state of the load device, and the second upper limit threshold in accordance with the switching frequency at which the switching element is turned on / off. It is configured to adjust the difference between the value and the second lower threshold.
  • the selection unit is configured to output one of the first and second control signals to the switching element according to the selection by the control unit.
  • FIG. 5 is a signal waveform diagram for explaining the operation of the hysteresis control unit shown in FIG. 4.
  • FIG. 7 is a signal waveform diagram for explaining the operation of the hysteresis control unit shown in FIG. 6.
  • FIG. 1st waveform diagram for demonstrating operation
  • 2nd waveform diagram for demonstrating operation
  • 3rd wave form diagram for demonstrating operation
  • wave form diagram explaining the setting of the upper limit threshold value and the lower limit threshold value in the hysteresis control part for controlling a direct current.
  • FIG. 1 is a block diagram illustrating a configuration of a power conversion device according to an embodiment of the present disclosure.
  • power conversion device 100 according to the embodiment of the present disclosure supplies DC power to load device 200 connected to power lines PL and NL.
  • the power conversion device 100 includes a power supply main circuit unit 110 and a power supply control unit 150.
  • the power supply main circuit unit 110 includes a DC power supply 120, a power conversion circuit 130, and a current detection unit 140.
  • the DC power source 120 outputs a DC voltage Vin.
  • the DC power supply 120 can be configured by a storage element such as a secondary battery or a DC power supply circuit that rectifies and smoothes an AC voltage from a commercial AC power supply.
  • the power conversion circuit 130 includes a switching element 132, a reactor 135, a diode 137, and a smoothing capacitor 138.
  • Smoothing capacitor 138 is connected between power lines PL and NL.
  • the voltage across the terminals of the smoothing capacitor 138 is also referred to as the output voltage Vo of the power conversion circuit 130.
  • L be the inductance value of the reactor 135.
  • an IGBT Insulated Gate Bipolar Transistor
  • a power MOS Metal Oxide Semiconductor
  • a power bipolar transistor or the like
  • the switching element 132 is turned on or off by a pulsed control signal Sg from the power supply control unit 150 for controlling the output of the power conversion circuit 130.
  • switching element 132 is turned on corresponding to a logic high level (hereinafter also simply referred to as “H level”) period, while corresponding to a logic low level (hereinafter also simply referred to as “L level”) period. Turned off.
  • a current supply path from the DC power source 120 to the load device 200 is formed via the switching element 132, the reactor 135, and the power lines PL and NL.
  • a current path that passes through reactor 135, power lines PL and NL, and load device 200 is formed by diode 137.
  • the output (output current Io and / or output voltage Vo) from the power conversion circuit 130 to the load device 200 increases during the ON period of the switching element 132, but decreases during the OFF period of the switching element 132.
  • the output current Io increases with a slope of (Vin ⁇ Vo) / L during the ON period of the switching element 132.
  • the output current Io decreases with a slope of ⁇ Vo / L.
  • the power conversion circuit 130 controls the load device.
  • the output to 200 output voltage Vo and output current Io
  • the load device 200 has n (n: a natural number of 2 or more) load units connected in parallel between the power lines PL and NL.
  • Each load unit has a load 210 and a load switch 220 connected in series between power lines PL and NL.
  • n loads 210 (1) to 210 (n) and load switches 220 (1) to 220 (n) are arranged.
  • the load switches 220 (1) to 220 (n) are controlled by load control signals LS (1) to LS (n), respectively.
  • Load 210 in which corresponding load switch 220 is turned on in accordance with load control signals LS (1) to LS (n) is connected between power lines PL and NL and operates by receiving a current supply.
  • the operating voltages of the loads 210 (1) to 210 (n) are common, and the output voltage Vo of the power conversion circuit 130 needs to be controlled according to the target voltage Vo * corresponding to the operating voltage.
  • the power consumption (current) during operation of the loads 210 (1) to 210 (n) may be common or different, but in the following, in order to simplify the description, the load 210 (1) It is assumed that the power consumption (current) during operation of ⁇ 210 (n) is the same. For this reason, in the following description, the power consumption (current) in the load device 200 is the number of operating loads 210 out of the loads 210 (1) to 210 (n) (hereinafter simply referred to as “the number of loads”). Will depend on.
  • the load device 200 generates power by operating part or all of the n loads 210 (1) to 210 (n) according to the load control signals LS (1) to LS (n). Consume. For this reason, the power (current) supplied to the load device 200 by the power conversion circuit 130 varies depending on the operating state (for example, the number of loads) of the load device 200.
  • the power conversion circuit 130 it is necessary for the power conversion circuit 130 to supply the load device 200 with the output current Io corresponding to the operating state of the load device 200 while maintaining the output voltage Vo at the target voltage Vo *. As a result, the output current range of the power conversion circuit 130 is relatively wide.
  • the current detector 140 is arranged on the path of the output current Io.
  • the current detection unit 140 outputs a detection signal Vdet having a voltage corresponding to the output current Io using a resistance element, an operational amplifier, or the like.
  • the power supplied to the load device 200 can be controlled by controlling on / off of the switching element 132.
  • the power supply control unit 150 generates a control signal Sg for the switching element 132 based on the load selection signal LDS indicating the operation state of the load device 200 and the detection signal Vdet from the current detection unit 140.
  • the power supply control unit 150 includes a control device 160, a hysteresis control unit 170 for controlling DC current, an AC component extraction unit 180, a hysteresis control unit 190 for controlling switching frequency, a selection unit 197, a signal And a buffer 198.
  • the control device 160 executes a predetermined control calculation for generating the control signal Sg.
  • the control device 160 may be configured by a general digital control circuit (including a circuit using software having the same function) that does not use an IC (Integrated Circuit), and only a part of the components are digitally controlled. It may be a circuit.
  • the control device 160 is configured by a microcomputer. That is, the output signal from the control device 160 is a digital signal.
  • the control device 160 corresponds to an example of a “control unit”.
  • the control device 160 receives a load selection signal LDS indicating the operating state of the load device 200.
  • the load selection signal LDS instructs to activate / stop the loads 210 (1) to 210 (n) in the load device 200. Therefore, the control device 160 generates the load control signals LS (1) to LS (n) so as to turn on the load switch 220 corresponding to the load 210 instructed to operate in response to the load selection signal LDS. That is, when the operation command of the load device 200 changes, the operation state of the load device 200 changes by switching the load control signals LS (1) to LS (n) according to the change of the load selection signal LDS. To do.
  • control device 160 can detect the number of operating loads 210 in the load device 200 based on the load selection signal LDS. Thereby, the target level of the output current Io can be set by predicting the current consumption in the load device 200.
  • the load control signals LS (1) to LS (n) are input from the power supply control unit 150 in the configuration example of FIG. 1, but may be input directly from the outside of the power conversion device 100 to the load device 200. In this case, in order to set the target level of the output current Io, information (for example, load control signals LS (1) to LS (n)) for detecting the number of operating loads in the load device 200 is used. Input to the control device 160 is required.
  • the controller 160 further outputs a plurality of bits of digital signals S1 and S2 indicating the upper threshold value V1h and the lower threshold value V1l used in the hysteresis control unit 170. Further, control device 160 outputs digital signals S3 and S4 having a plurality of bits indicating upper threshold value V2h and lower threshold value V21 used in hysteresis control unit 190. Each of upper threshold values V1h and V2h and lower threshold values V1l and V2l has a voltage value defined by a plurality of bits of digital data.
  • control device 160 outputs the control signal Sel of the selection unit 197.
  • the selection unit 197 is connected between the hysteresis control units 170 and 190 and the signal buffer 198.
  • the selection unit 197 switches the path between the hysteresis control units 170 and 190 and the signal buffer 198 according to the control signal Sel.
  • one of the control signal Sh1 from the hysteresis control unit 170 and the control signal Sh2 from the hysteresis control unit 190 is selectively input to the signal buffer 198.
  • the signal buffer 198 generates the control signal Sg output to the control electrode (for example, the gate of the MOS transistor) of the switching element 132 according to the control signal Sh1 or Sh2 transmitted from the selection unit 197.
  • the output current Io of the power conversion circuit 130 a ripple current that increases or decreases depending on whether the switching element 132 is on or off is generated. Therefore, the output current Io is represented by the sum of a direct current (DC component) corresponding to the average value and an alternating current (AC component) corresponding to the ripple current.
  • DC component direct current
  • AC component alternating current
  • the frequency of the alternating current (alternating current component) is equal to the switching frequency of the switching element 132.
  • the detection signal Vdet output from the current detection unit 140 has a voltage value proportional to the output current Io.
  • the AC component extraction unit 180 includes a DC component removal unit 182 and an amplification unit 185.
  • the DC component removal unit 182 is configured to extract an AC component from the detection signal Vdet.
  • the DC component removing unit 182 can be configured by a capacitor that allows the AC component of the detection signal Vdet to pass therethrough.
  • the DC component removal unit 182 may be configured as a differential circuit including a capacitor and a resistor, or a high-pass filter having a differential element by an operational amplifier or the like. Note that the DC component removal unit 182 is desired to have a sharp frequency characteristic while appropriately setting the cutoff frequency in order to reliably remove the low-frequency component.
  • the direct current component removing unit 182 can be configured by a subtracting unit 184.
  • Subtraction unit 184 outputs a signal obtained by subtracting DC voltage Vd * from control device 160 from detection signal Vdet from current detection unit 140. That is, the output signal from the subtracting unit 184 has a voltage value of (Vdet ⁇ Vd *).
  • the control device 160 can set the DC voltage Vd * according to the load selection signal LDS.
  • the amplifying unit 185 amplifies the output signal of the direct current component removing unit 182 and outputs the detection signal Vdet #.
  • Detection signal Vdet # has a voltage value corresponding to the AC component of detection signal Vdet, that is, the AC component of output current Io.
  • the detection signal Vdet corresponds to the “first detection signal”
  • the detection signal Vdet # corresponds to the “second detection signal”.
  • FIG. 3 is a conceptual diagram for explaining the extraction process of the AC component from the detection signal.
  • detection signal Vdet output from current detection unit 140 has a DC component that changes according to the number of loads in load device 200 as shown in (a) to (c).
  • the detection signal Vdet is within the range of the power supply voltage used in the power supply control unit 150, that is, the control power supply voltage Vc (for example, 3.3V or 5V) that is the operation power supply of the control device 160 to the ground voltage GND (0V).
  • the voltage changes according to the output current Io.
  • the detection gain K1 in the current detection unit 140 is such that K1 ⁇ Iomax ⁇ Vc with respect to the maximum current consumption Iomax when all the loads 210 (1) to 210 (n) are operated in the load device 200. It is necessary to design to.
  • the functions of the direct current component removing unit 182 and the amplifying unit 185 in FIG. 1 are integrally configured using a differential amplifier circuit using an operational amplifier, so that the output current Io can be reduced without requiring a negative power supply.
  • a detection signal Vdet # indicating an AC component can be generated. Although the generation of a negative voltage is necessary in principle, the detection signal Vdet # is generated only by removing the DC component from the detection signal Vdet by the DC component removal unit 182 without adding the offset voltage Vof. Is also possible.
  • FIG. 4 is a block diagram illustrating the configuration of the hysteresis control unit 170 for controlling the direct current shown in FIG.
  • hysteresis control unit 170 includes digital / analog converters (DACs) 171 and 172, comparison units 174 and 175, and signal generator 176.
  • the DAC 171 outputs an upper limit threshold value V1h by converting the digital signal S1 from the control device 160 into an analog voltage.
  • the DAC 172 outputs the lower threshold value V1l by converting the digital signal S2 from the control device 160 into an analog voltage.
  • Each of the comparison units 174 and 175 can be configured by a comparator using an operational amplifier.
  • the comparison unit 174 outputs a one-shot pulse each time Vdet ⁇ V1h becomes Vdet> V1h by comparing the detection signal Vdet from the current detection unit 140 with the upper threshold value V1h from the DAC 171. .
  • the comparison unit 175 outputs a one-shot pulse each time Vdet ⁇ V1l from the state of Vdet> V1l by comparing the detection signal Vdet from the current detection unit 140 with the lower limit threshold value V1l from the DAC 172. .
  • the signal generator 176 generates the control signal Sh1 according to the outputs of the comparison units 174 and 175.
  • FIG. 5 shows a signal waveform diagram for explaining the operation of the hysteresis control unit 170 shown in FIG.
  • comparison unit 174 when detection signal Vdet rises from the state of Vdet ⁇ V1h and becomes higher than upper limit threshold value V1h, comparison unit 174 outputs a one-shot pulse. In response to this, the signal generator 176 changes the control signal Sh1 from the H level to the L level in order to turn off the switching element 132. Thereby, further increase in the detection signal Vdet (that is, the output current Io) can be avoided.
  • the comparison unit 175 outputs a one-shot pulse.
  • the signal generator 176 changes the control signal Sh1 from the L level to the H level in order to turn on the switching element 132. As a result, a further decrease in the detection signal Vdet (that is, the output current Io) can be avoided.
  • the detection signal Vdet is maintained within the range of V1l to V1h by generating the control signal Sh1 based on the comparison result between the detection signal Vdet and the upper limit threshold value V1h and the lower limit threshold value V1l.
  • the switching element 132 can be controlled on and off. This makes it possible to control the direct current so as to maintain the output current Io within a certain range.
  • the hysteresis control unit 170 corresponds to an example of the “first hysteresis control unit”, and the control signal Sh1 corresponds to the “first control signal”. Further, the upper limit threshold value V1h corresponds to a “first upper limit threshold value”, and the lower limit threshold value V1l corresponds to a “first lower limit threshold value”.
  • FIG. 6 is a block diagram illustrating the configuration of the hysteresis control unit 190 for controlling the switching frequency shown in FIG.
  • the hysteresis control unit 190 includes digital / analog converters (DACs) 191, 192, comparison units 194, 195, and a signal generator 196.
  • the DAC 191 outputs the upper limit threshold V2h by converting the digital signal S3 from the control device 160 into an analog voltage.
  • the DAC 192 outputs the lower threshold value V21 by converting the digital signal S4 from the control device 160 into an analog voltage.
  • Each of the comparison units 194 and 195 can be configured by a comparator using an operational amplifier, like the comparison units 174 and 175.
  • the comparison unit 194 compares the detection signal Vdet # from the amplification unit 185 with the upper limit threshold value V2h from the DAC 191 and outputs a one-shot pulse every time Vdet # ⁇ V2h from Vdet # ⁇ V2h. Output.
  • the comparison unit 195 outputs a one-shot pulse each time Vdet # ⁇ V2l from the state of Vdet #> V2l by comparing the detection signal Vdet # with the lower limit threshold value V2l from the DAC 192.
  • the signal generator 196 generates a control signal Sh2 according to the outputs of the comparison units 194 and 195.
  • FIG. 7 is a signal waveform diagram for explaining the operation of the hysteresis control unit 190 shown in FIG.
  • comparison unit 194 when detection signal Vdet # rises from the state of Vdet # ⁇ V2h and becomes higher than upper threshold value V2h, comparison unit 194 outputs a one-shot pulse. In response to this, the signal generator 196 changes the control signal Sh2 from the H level to the L level in order to turn off the switching element 132.
  • the comparison unit 195 outputs a one-shot pulse.
  • the signal generator 196 changes the control signal Sh2 from the L level to the H level in order to turn on the switching element 132.
  • control signal Sh2 is generated based on the result of comparison of the detection signal Vdet # with the upper limit threshold value V2h and the lower limit threshold value V21, so that the ON / OFF cycle of the switching element 132 is set to the upper limit threshold value. It can be adjusted by V2h and the lower threshold value V21. That is, the switching frequency of the switching element 132 can be increased by setting the difference between the upper limit threshold value V2h and the lower limit threshold value V2l so as to reduce the AC component of the output current Io.
  • the hysteresis control unit 190 corresponds to an example of the “second hysteresis control unit”
  • the control signal Sh2 corresponds to the “second control signal”.
  • upper limit threshold value V2h corresponds to “second upper limit threshold value”
  • lower limit threshold value V2l corresponds to “second lower limit threshold value”.
  • the current detection unit 140 amplifies a voltage difference (that is, a voltage drop amount due to Io) generated between both ends of the current detection resistor 142 and the current detection resistor 142 arranged to pass the output current Io.
  • Amplifier 145 The amplifier 145 outputs the detection signal Vdet.
  • the full scale of the DAC corresponding to the control power supply voltage Vc can be used effectively.
  • G 100
  • the design of the current detection unit 140 for example, the design of the resistance value R of the current detection resistor 142 and the gain G of the amplifier 145 is determined by the current detection resistor 142 in the case where the supply current to the load device 200 is maximum. Power loss, current control accuracy (resolution of upper threshold and lower threshold in hysteresis control), current ripple, and the like.
  • the detection signal Vdet indicated by the solid line is controlled within the range of the upper limit threshold value V1l to the lower limit threshold value V1h. Yes.
  • FIG. 12 is a conceptual waveform diagram for explaining a method of setting the upper limit threshold value V1h and the lower limit threshold value V1l in the hysteresis control unit 170.
  • the on period of the switching period T of the switching element 132 is assumed to be ton.
  • the following equation (1) is established from a voltage conversion ratio in a so-called step-down chopper.
  • the current ripple ⁇ Io is expressed by the following equation (3). That is, since the current ripple ⁇ Io is a function of the inductance value L, the input voltage Vin, the output voltage Vo, and the switching frequency f, the inductance value L is designed in consideration of the allowable current width (current ripple ⁇ Io).
  • the target value of the switching frequency at the time of hysteresis control by the hysteresis controller 170 can be determined.
  • the detection signal Vdet has a voltage width of K1 ⁇ ⁇ Io corresponding to the current ripple ⁇ Io (current width).
  • the upper limit threshold V1h and the lower limit are set so that the output current Io falls within a certain range centered on the direct current Iodc depending on the operating state (number of loads) of the load device 200. It is necessary to set the threshold value V1l.
  • the upper threshold value V1h and the lower threshold value V1l can be set according to the following equations (4) and (5). That is, upper limit threshold value V1h is set corresponding to a current value obtained by adding 1/2 of current width ⁇ Io to DC current Iodc, and lower limit threshold value V1l and DC current Iodc are set to 1/2 of current width ⁇ Io. Set according to the subtracted current value.
  • the upper limit threshold value V1h and the lower limit threshold value for setting the desired switching frequency f according to the inductance value L of the reactor 135, the input voltage Vin and the output voltage Vo of the DC power supply 120 V1l can be calculated.
  • the calculation of the upper limit threshold value V1h and the lower limit threshold value V1l according to the equations (6) and (7) may be performed at regular intervals, and the direct current is changed depending on the change in the operating state (the number of loads) of the load device 200. It may be executed every time the current Iodc changes. It is understood from equations (6) and (7) that the difference (hysteresis width) between upper limit threshold value V1h and lower limit threshold value V1l is constant even if DC current Iodc changes.
  • a table reflecting formulas (6) and (7) for setting the upper limit threshold value V1h and the lower limit threshold value V1l corresponding to the operating state (the number of loads) of the load device 200 is created in advance. Is also possible. In this case, when the power conversion device 100 is operated, the table is referred to according to the operating state of the load device 200 acquired by the load selection signal LDS, and the equations (6) and (7) are followed.
  • the upper limit threshold value V1h and the lower limit threshold value V1l can be easily set without executing the calculation each time.
  • the upper limit threshold value V1h is set to a margin so as to be set smaller than the calculated value according to the equation (6).
  • a margin so that the lower limit threshold value V1l is set larger than the calculated value according to the equation (7).
  • the same effect can be obtained even when the upper limit threshold value V1h and the lower limit threshold value V1l are set by setting the switching frequency f in the equations (6) and (7) higher than the actual desired frequency. Can do.
  • the output current Io is reduced to Iodc ⁇ ( ⁇ Io / 2 ) ⁇ Io ⁇ Iodc + ( ⁇ Io / 2).
  • FIG. 13 is a conceptual waveform diagram for explaining a method of setting upper limit threshold value V2h and lower limit threshold value V2l in hysteresis control unit 190.
  • the AC component (Io ⁇ Iodc) of the output current Io is multiplied by the detection gain K1 by the current detection unit 140 and the gain K2 of the amplification unit 185, and appears in the detection signal Vdet #.
  • Upper limit threshold value V2h and lower limit threshold value V2l may be set to have a difference of K1, K2, and ⁇ Io with offset voltage Vof as the center, similar to upper limit threshold value V1h and lower limit threshold value V1l. it can.
  • the upper threshold value V2h and the lower threshold value V2l can be calculated according to the following equations (8) and (9).
  • upper limit threshold value V2h and lower limit threshold value V2l are changed from the initial values set according to equations (8) and (9) for the purpose of adjusting the switching frequency. .
  • the expressions (8) and (9) do not include the Iodc term unlike the expressions (6) and (7). That is, the upper limit threshold value V2h and the lower limit threshold value V2l are updated in accordance with the operating state of the load device 200 (the number of operations of the load 210), unlike the upper limit threshold value V1h and the lower limit threshold value V1l. It is understood that there is no need.
  • FIG. 14 is a flowchart illustrating a control process for direct current control using the hysteresis control unit 170.
  • control device 160 selects so as to select a path through which control signal Sh1 from hysteresis control unit 170 is transmitted to signal buffer 198 in step S100.
  • the control signal Sel of the unit 197 is generated.
  • control device 160 sets an upper limit threshold value V1h and a lower limit threshold value V1l according to the operating state (number of loads) of the load device 200 in step S105.
  • upper limit threshold value V1h and lower limit threshold value V1l can be set according to equations (6) and (7) using DC current Iodc set in accordance with load selection signal LDS. .
  • the hysteresis controller 170 as shown in FIG. 5 based on the detection signal Vdet from the current detector 140 and the upper and lower thresholds V1h and V1l set in step S105.
  • the control signal Sh1 is generated.
  • the signal buffer 198 generates the control signal Sg of the switching element 132 according to the control signal Sh1 transmitted from the selection unit 197. Thereby, on / off of the switching element 132 is controlled so that the hysteresis control shown in FIG. 12 is executed.
  • control device 160 executes the convergence determination in step S110.
  • step S110 whether or not the output current Io has converged in the vicinity of the direct current Iodc can be determined based on whether or not the detection signal Vdet is within the range of V1l ⁇ Vdet ⁇ V1h. That is, if V1l ⁇ Vdet ⁇ V1h is detected, step S110 is determined as YES.
  • step S110 determines whether or not the output current Io has converged to the target level based on the elapsed time from the start of the hysteresis control using the upper limit threshold value V1h and the lower limit threshold value V1l (S105). It is. In this case, until the elapsed time exceeds the determination value T *, step S110 is determined as NO, and when the elapsed time reaches the determination value T *, step S110 is determined as YES.
  • the determination value T * it is preferable to set the determination value T * so as to ensure a time during which the vibration of the detection signal Vdet # that occurs when the direct current Iodc changes is sufficiently attenuated.
  • the judgment value T * can be determined in advance according to the result of simulation or actual machine experiment.
  • the control device 160 continues the hysteresis control using the upper limit threshold value V1h and the lower limit threshold value V1l (S105) in step S120 when NO is determined in step S110.
  • the convergence determination in step S110 is repeatedly executed until the determination in step S110 is YES. Therefore, ON / OFF of switching element 132 is controlled by hysteresis control (S120) using upper limit threshold value V1h and lower limit threshold value V1l until output current Io converges in the vicinity of DC current Iodc.
  • step S110 it waits until predetermined time passes from the start of hysteresis control, and you may make it perform the 1st determination after progress of the said predetermined time.
  • step S110 determines whether the determination in step S110 is YES. If the determination in step S110 is YES, the control device 160 detects that the output current Io has converged in the vicinity of the direct current Iodc, and proceeds to step S130. In step S ⁇ b> 130, the control device 160 ends the direct current control by the hysteresis control unit 170 and shifts to the switching frequency control by the hysteresis control unit 190.
  • FIG. 15 shows a conceptual waveform diagram for explaining an example of changes in the upper threshold value and the lower threshold value depending on the operating state of the load device.
  • load 210 (2) to load 210 (4) are further sequentially operated from the state in which only load 210 (1) is activated.
  • the operation (ON) / stop (OFF) of each of the loads 210 (2) to 210 (4) is designated by the load selection signal LDS.
  • the upper limit threshold value V1h and the lower limit threshold value V1l are newly set by executing the control process according to the flowchart of FIG. 14 (S105).
  • the upper limit threshold value V1h and the lower limit threshold value V1l can be increased stepwise as the DC current Iodc is increased stepwise as the operating load increases. .
  • the power conversion apparatus 100 generates the output current Io corresponding to the consumption current required for the load apparatus 200 by hysteresis control (DC current control) using the upper limit threshold value V1h and the lower limit threshold value V1l that are sequentially updated. Can be supplied.
  • hysteresis control DC current control
  • FIG. 16 is a flowchart for explaining a control process of switching frequency control by hysteresis control.
  • control device 160 selects so as to select a path through which control signal Sh2 from hysteresis control unit 190 is transmitted to signal buffer 198 in step S200.
  • the control signal Sel of the unit 197 is generated.
  • control device 160 sets initial values of upper limit threshold value V2h and lower limit threshold value V2l according to equations (8) and (9).
  • the hysteresis control unit 190 performs control as shown in FIG. 7 based on the detection signal Vdet # corresponding to the AC component of the output current Io and the upper and lower thresholds V2h and V2l.
  • a signal Sh2 is generated.
  • the signal buffer 198 generates the control signal Sg of the switching element 132 according to the control signal Sh2 transmitted from the selection unit 197. Thereby, on / off of the switching element 132 is controlled so that the hysteresis control shown in FIG. 13 is executed.
  • the output current Io is controlled so that the AC component falls within a certain range according to the upper limit threshold value V2h and the lower limit threshold value V21, starting from the state controlled by the DC current control.
  • control device 160 measures the current switching frequency fo of the switching element 132 in step S210.
  • the switching frequency fo can be measured by measuring the period of the control signal Sh2 transmitted from the selection unit 197 to the signal buffer 198 using a timer (not shown) built in the control device 160. .
  • control device 160 compares switching frequency fo measured in step S210 with a predetermined lower limit frequency ft.
  • the lower limit frequency ft can be set corresponding to the lower limit frequency at which generation of electromagnetic noise and noise can be avoided.
  • control device 160 When measured switching frequency fo is higher than lower limit frequency ft (when YES in S220), control device 160 maintains the current upper limit threshold value V2h and lower limit threshold value V2l in step S240 to perform hysteresis control. Execute.
  • control device 160 proceeds to step S230 to process upper limit threshold value V2h and lower limit threshold value. Adjust V2l. Then, in step S240, control device 160 executes hysteresis control using upper limit threshold value V2h and lower limit threshold value V21 after adjustment in step S230.
  • step S230 in order to increase the switching frequency, the upper limit threshold value V2h and the lower limit threshold value V2l are adjusted so that the difference between the upper limit threshold value V2h and the lower limit threshold value V2l decreases.
  • FIG. 17 is a conceptual waveform diagram for explaining an adjustment example of the upper and lower thresholds in the switching frequency control.
  • initial values of upper limit threshold value V2h and lower limit threshold value V2l are set symmetrically with offset voltage Vof as the center value.
  • the upper limit threshold value V2h is lowered by a predetermined unit voltage Vu and is reduced to a lower limit.
  • the threshold value V21 is increased by the unit voltage Vu.
  • the unit voltage can be set in advance corresponding to the resolution in the DACs 191 and 192, that is, the voltage change of one gradation.
  • the switching frequency fo under hysteresis control using the upper limit threshold value V2h and the lower limit threshold value V21 after adjustment is measured again, and the adjustment in step S230 is executed according to the comparison result with the lower limit frequency ft. Is done.
  • the upper limit threshold V2h and the lower limit threshold V2l are adjusted until the difference is such that fo> ft can be secured.
  • the lowering of the upper limit threshold value V2h and the lowering of the lower limit threshold value V2l are simultaneously executed in step S230. Only one of the increase of the threshold value V2l may be executed alternately.
  • the unit voltage can also be set arbitrarily.
  • the unit voltage Vu can be set in correspondence with a voltage change for m gradations (m: a natural number of 2 or more) in the DACs 191 and 192.
  • control device 160 determines whether the operating state (number of loads) of load device 200 has been switched based on load selection signal LDS. Control device 160 repeatedly executes the processes of steps S210 to S240 until the operation state of load device 200 is switched (when NO is determined in S250). Thereby, ON / OFF of the switching element 132 is controlled by the hysteresis control unit 190 so that the state where the switching frequency fo is higher than the lower limit frequency ft is maintained.
  • control device 160 proceeds to step S260 and ends switching frequency control by hysteresis control unit 190. Instruct the transition to DC current control by the hysteresis controller 170. In response to this, the control device 160 activates the control process shown in FIG.
  • the upper limit threshold value V2h and the lower limit threshold value V2l used in the hysteresis control unit 190 do not need to be updated even when the operating state (the number of loads) of the load device 200 changes. Therefore, for upper limit threshold value V2h and lower limit threshold value V21, default values are set according to equations (8) and (9), and switching frequency control is terminated after operation of power converter 100 is started. (S260), the current upper limit threshold value V2h and lower limit threshold value V2l are stored, and when the switching frequency control is activated next time, the stored value is read out, whereby the upper limit threshold value V2h and the lower limit threshold value are read. It is also possible to set the initial value of V2l (S205).
  • control for limiting the lower limit frequency of the switching frequency fo is illustrated, but it is also possible to perform control for limiting the upper limit frequency of the switching frequency fo.
  • the upper limit threshold V2h and the lower limit are increased so that the difference between the upper limit threshold V2h and the lower limit threshold V2l is expanded in step S230.
  • the threshold value V2l can be adjusted. Specifically, in step S230, the upper limit threshold value V2h can be increased and / or the lower limit threshold value V2l can be decreased.
  • both the upper limit frequency and the lower limit frequency and control the switching frequency to fall within the range from the lower limit frequency to the upper limit frequency.
  • the difference between the upper limit threshold value V2h and the lower limit threshold value V2l is reduced and the measured switching frequency fo is set to the upper limit value as in FIG.
  • the control process for adjusting the upper limit threshold value V2h and the lower limit threshold value V2l can be changed so as to increase the difference between the upper limit threshold value V2h and the lower limit threshold value V2l.
  • FIG. 18 shows a state transition diagram of DC current control (hysteresis control unit 170) and frequency control (hysteresis control unit 190) in the power converter according to the present embodiment.
  • DC current control is executed.
  • the hysteresis control based on the detection signal Vdet is executed so that the DC current Iodc set according to the operating state of the load device 200 (the number of operating loads 210) is supplied.
  • the hysteresis control is switched from the direct current control to the switching frequency control.
  • the hysteresis control based on the detection signal Vdet # is executed starting from the state in which the output current Io is controlled to the current level according to the operating state of the load device 200. Therefore, on / off of switching element 132 is controlled such that the AC component of output current Io is maintained within a certain range defined by the difference between upper limit threshold value V2h and lower limit threshold value V2l. As a result, the switching frequency can be controlled by adjusting the difference between the upper limit threshold value V2h and the lower limit threshold value V21 according to the actually measured switching frequency fo.
  • hysteresis control is applied to the power conversion device in which output current Io varies over a wide range by combining hysteresis control for controlling DC current and switching frequency control. Even in this case, it is possible to appropriately control the switching frequency.
  • FIG. 19 is an electric circuit diagram illustrating a configuration example of the load device shown in FIG. Referring to FIG. 19, each of loads 210 (1) to 210 (n) constituting load device 200 can be constituted by an LED module that is an assembly of a predetermined number of light emitting diodes (LEDs) 240. By connecting the LED modules in parallel as loads 210 (1) to 210 (n), a matrix LED for a vehicle headlight can be realized.
  • LEDs light emitting diodes
  • the LED module By turning on / off the load switches 220 (1) to 220 (n), the LED module can be turned on and off for each load 210 (1) to 210 (n). Note that a plurality of LED modules can be connected in series and parallel to form a matrix LED. Moreover, also about each LED module, it is also possible to connect LED240 in parallel or series-parallel.
  • ADB Adaptive Driving Beam
  • a so-called matrix control system has been developed in which LEDs are assigned to each irradiation range and the illuminance of the LED for each irradiation range is controlled in accordance with detection of an oncoming vehicle or the like.
  • the matrix control method has an advantage that light can be efficiently irradiated as compared with the mechanical ADB method that shields light by a mechanical mechanism.
  • the output current Io of the power conversion device 100 varies in a wide range according to the number of LED modules that are turned on. For this reason, hysteresis control that is excellent in response speed to load fluctuations is often applied.
  • the switching frequency range of the power conversion device 100 is limited.
  • the switching frequency needs to avoid the range of 500 kHz to 1.6 MHz.
  • power converter 100 when high frequency is directed from the viewpoint of miniaturization of reactor 135, it is necessary to stably maintain the switching frequency in a high frequency band of 1.6 MHz or higher.
  • the output current Io is controlled corresponding to the number of lighting of the LED module by a combination of two types of hysteresis control, and the switching frequency is higher than the AM radio band. (Fo> 1.6 MHz) can be stably maintained.
  • the power conversion device according to the present embodiment is suitable for supplying power to the LED module constituting the LED headlight having the ADB function illustrated in FIG.
  • the hysteresis control in the case where the output current Io is controlled over a wide range as the output of the power conversion device while the target level of the output voltage Vo is substantially constant has been described.
  • the power conversion device according to the present embodiment can also be applied to applications in which the output voltage Vo is controlled over a wide range according to the operating state of the load device 200.
  • the same hysteresis control can be executed by calculating the detection signals Vdet and Vdet # according to the detection value of the output voltage Vo.
  • the output voltage Vo in the equations (6) to (9) is treated as a variable according to the operating state of the load device 200, and the upper limit threshold values V1h and V2h and the lower limit threshold values V1l and V2l are set. Can be calculated. Further, when both target levels of the output voltage Vo and the output current Io change according to the operating state of the load device 200, both the output voltage Vo and the output current Io in the equations (6) to (9). As a variable according to the target level, the same hysteresis control can be executed.
  • circuit configuration of the power conversion circuit 130 in FIG. 1 is merely an example, and any configuration can be applied as long as the circuit configuration has a DC voltage conversion function.
  • 100 power converter 110 power supply main circuit part, 120 DC power supply, 130 power conversion circuit, 132 power semiconductor switching element, 135 reactor, 137 diode, 138 smoothing capacitor, 140 current detection part, 142 current detection resistor, 145 amplifier, 150 power supply control unit, 160 control device, 170, 190 hysteresis control unit, 171, 172, 191, 192 DAC, 174, 175, 194, 195 comparison unit, 176, 196 signal generator, 180 AC component extraction unit, 182 DC Component removal unit, 184 subtraction unit, 185 amplification unit, 197 selection unit, 198 signal buffer, 200 load device, 210 (1) -210 (n) load, 220 (1) -220 (n) load switch, Io output current , Io goal Bell, Iodc DC current (load consumption current), L inductance value, LDS load selection signal, LS (1) to LS (n) load control signal, NL, PL power line, Sel control signal (selection unit), Sg control signal ( Switching element), Sh

Abstract

Selon la présente invention, un circuit de conversion de puissance (130) comprend un élément de commutation (132) permettant d'augmenter et de diminuer un courant de sortie (Io) circulant vers un dispositif de charge (200). Une unité de détection de courant (140) émet un premier signal de détection (Vdet) correspondant au courant de sortie (Io). Un second signal de détection (Vdet#) est généré par extraction de composantes de courant alternatif du premier signal de détection. Une première unité de commande d'hystérèse (170) génère un premier signal de commande (Sh1) en fonction d'une comparaison entre le premier signal de détection (Vdet) et les premières valeurs seuil (V1h, Vll). Une seconde unité de commande d'hystérèse (190) génère un second signal de commande (Sh2) en fonction d'une comparaison entre le second signal de détection et les secondes valeurs seuil (V2h, V2l). Une unité de sélection (197) sélectionne le premier ou le second signal de commande et transmet le signal sélectionné à l'élément de commutation (132). La première valeur seuil change en fonction des changements de l'état de fonctionnement du dispositif de charge, et la différence entre les première et seconde valeurs seuil est ajustée en fonction de la fréquence de commutation.
PCT/JP2017/019112 2016-07-27 2017-05-23 Dispositif de conversion de puissance WO2018020797A1 (fr)

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Cited By (1)

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JP2022007241A (ja) * 2020-06-26 2022-01-13 Ｎｅｃプラットフォームズ株式会社 制御回路、装置、制御方法及びプログラム

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Publication number Priority date Publication date Assignee Title
JP2005341712A (ja) * 2004-05-27 2005-12-08 Taiyo Yuden Co Ltd 電源装置
JP2013093214A (ja) * 2011-10-26 2013-05-16 Koito Mfg Co Ltd 半導体光源点灯回路
JP2014216600A (ja) * 2013-04-30 2014-11-17 株式会社小糸製作所 制御装置および車両用灯具
JP2015532085A (ja) * 2012-08-22 2015-11-05 アレグロ・マイクロシステムズ・エルエルシー ヒステリシス制御を使用するｄｃ／ｄｃコンバータおよび関連する方法

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2005341712A (ja) * 2004-05-27 2005-12-08 Taiyo Yuden Co Ltd 電源装置
JP2013093214A (ja) * 2011-10-26 2013-05-16 Koito Mfg Co Ltd 半導体光源点灯回路
JP2015532085A (ja) * 2012-08-22 2015-11-05 アレグロ・マイクロシステムズ・エルエルシー ヒステリシス制御を使用するｄｃ／ｄｃコンバータおよび関連する方法
JP2014216600A (ja) * 2013-04-30 2014-11-17 株式会社小糸製作所 制御装置および車両用灯具

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2022007241A (ja) * 2020-06-26 2022-01-13 Ｎｅｃプラットフォームズ株式会社 制御回路、装置、制御方法及びプログラム
JP7056881B2 (ja) 2020-06-26 2022-04-19 Ｎｅｃプラットフォームズ株式会社 制御回路、装置、制御方法及びプログラム

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