WO2015081627A1 - 反激式开关电源电路及应用该电路的背光源驱动装置 - Google Patents

反激式开关电源电路及应用该电路的背光源驱动装置 Download PDF

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Publication number
WO2015081627A1
WO2015081627A1 PCT/CN2014/070840 CN2014070840W WO2015081627A1 WO 2015081627 A1 WO2015081627 A1 WO 2015081627A1 CN 2014070840 W CN2014070840 W CN 2014070840W WO 2015081627 A1 WO2015081627 A1 WO 2015081627A1
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WIPO (PCT)
Prior art keywords
switching transistor
voltage
power supply
supply circuit
transistor
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
PCT/CN2014/070840
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English (en)
French (fr)
Inventor
王照
曹丹
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
TCL China Star Optoelectronics Technology Co Ltd
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Shenzhen China Star Optoelectronics Technology Co Ltd
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Application filed by Shenzhen China Star Optoelectronics Technology Co Ltd filed Critical Shenzhen China Star Optoelectronics Technology Co Ltd
Priority to US14/241,415 priority Critical patent/US9160239B2/en
Priority to JP2016536836A priority patent/JP6580044B2/ja
Priority to GB1609794.1A priority patent/GB2535115B/en
Priority to RU2016121671A priority patent/RU2637773C9/ru
Priority to KR1020167017286A priority patent/KR101847321B1/ko
Publication of WO2015081627A1 publication Critical patent/WO2015081627A1/zh
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33523—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/337—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters
    • H05B41/288—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters with semiconductor devices and specially adapted for lamps without preheating electrodes, e.g. for high-intensity discharge lamps, high-pressure mercury or sodium lamps or low-pressure sodium lamps
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/385—Switched mode power supply [SMPS] using flyback topology
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B47/00—Circuit arrangements for operating light sources in general, i.e. where the type of light source is not relevant
    • H05B47/10—Controlling the light source
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B20/00—Energy efficient lighting technologies, e.g. halogen lamps or gas discharge lamps
    • Y02B20/30—Semiconductor lamps, e.g. solid state lamps [SSL] light emitting diodes [LED] or organic LED [OLED]
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to the field of power supply technologies, and in particular, to a flyback switching power supply circuit and a back: light source driving device using the same. Background technique
  • the flyback power supply circuit has many advantages such as simple circuit and high efficiency in providing DC output, and is particularly suitable for, for example, home appliances, battery chargers, and many other switching power supplies of low power design.
  • the flyback switching power supply refers to the switching power supply of the flyback high frequency transformer isolated input and output circuit.
  • FLY BACK specifically refers to the output line when the input is high (the switch is turned on) and the inductor connected in series is discharged. When the input is high, the switch is disconnected. The inductance in the state is the state of charge.
  • Figure: I shows a schematic diagram of a flyback switching power supply circuit that should be on a liquid crystal display in the prior art. As shown in Figure 1, the switching power supply circuit mainly includes: a voltage input terminal, a control IC, and a power MOS transistor. , a transformer, a rectifier diode and an output capacitor.
  • the MOS transistor is controlled by the control IC to close or turn on the MOS transistor by controlling the pulse width adjustment signal generated by the IC.
  • the power MOS transistor When the power MOS transistor is turned on, the inductor winding current of the transformer begins to rise. At this time, due to the relationship of the secondary winding, the rectifier diode is turned off, and the transformer stores energy.
  • the power MOS transistor When the power MOS transistor is turned off, the inductance induced voltage of the primary winding of the transformer is reversed, and the rectifier diode is turned on, and the energy in the transformer is supplied to the load via the rectifying diode.
  • the control IC is used to directly control the on/off of the MOS switch. Due to the parasitic capacitance effect inside the transformer, after the MOS transistor is turned off, the potential of the drain (D pole) is not immediately stabilized, but tends to be stable according to the damping vibration (as shown in Fig. 2). Since the damping vibration effect is not considered in this process, a high switching loss of the MOS transistor is generated.
  • One of the technical problems to be solved by the present invention is to provide a flyback switching power supply circuit which can effectively reduce the switching loss of a MOS transistor.
  • a backlight driving device to which the circuit is applied is also provided.
  • the present invention provides a flyback switching power supply circuit comprising: a transformer including a primary winding, a secondary winding, and a auxiliary winding disposed on one side of the primary winding; An output rectifier having a secondary winding of the transformer coupled to an output of the flyback switching power supply circuit; a switching transistor for controlling a voltage across the primary winding, wherein a drain of the switching transistor Connecting to one end of the primary winding; a controller for providing a pulse width modulation signal to drive a pole of the switching transistor, wherein the controller includes a GATE terminal connecting a gate of the switching transistor; a clamp delay circuit for clamping a » terminal potential of the switching transistor to a low potential such that the switching transistor is turned on at a valley of a drain potential damping vibration thereof, wherein the clamp delay circuit is The auxiliary winding is connected to the gate of the switching transistor.
  • the clamp delay circuit further includes: a voltage stabilizing capacitor that charges according to a voltage generated by the auxiliary winding, the stabilizing capacitor and The auxiliary windings are connected in parallel, and one end of the voltage stabilizing capacitor is connected to a ground reference together with the first terminal of the auxiliary winding;
  • a diode having a second terminal of the auxiliary winding connected to the other end of the stabilizing capacitor; a voltage dividing circuit for dividing a voltage stored in the stabilizing capacitor, the voltage dividing circuit Connected in parallel with the stabilizing capacitor;
  • the voltage dividing circuit has a collector connected to a gate of the switching transistor.
  • the voltage dividing circuit comprises a first-part voltage dividing resistor and a second voltage dividing resistor connected in series, the triode The base is connected between the first voltage dividing resistor and the second voltage dividing resistor.
  • the switching transistor when the controller outputs a low potential, the switching transistor is turned off, and the auxiliary winding is turned to The stabilizing capacitor is charged and passed the The first voltage dividing resistor and the second voltage dividing resistor are divided to turn on: the triode, the triode clamps the gate potential of the switching transistor to a low potential, so that the switching transistor is at its drain potential The valley of the damped vibration is turned on.
  • the switching transistor when the controller outputs a high potential, the switching transistor is turned on, and the clamp delay circuit does not jobs.
  • a backlight driving apparatus comprising the flyback switching power supply circuit as described above.
  • the present invention provides a clamp delay circuit in a flyback switching power supply circuit, and an auxiliary winding is added to the transformer, The circuit clamps the gate potential of the MOS transistor to low when the MOS transistor is turned off from the off state, and controls the MOS transistor to be turned on at the valley of the drain potential damping vibration thereof, which causes the voltage accumulation of the MOS transistor to be turned on. Small, avoid voltage spikes, lower! Switching loss of the V10S tube.
  • FIG. 1 is a schematic diagram of a flyback switching power supply circuit in the prior art
  • 2 is a schematic diagram of damped vibration of a drain (D-pole) potential of a MOS transistor in a flyback switching power supply circuit
  • FIG. 3 is a schematic diagram of a flyback switching power supply circuit according to an embodiment of the present invention.
  • FIG. 3 shows a flyback power switch circuit according to an embodiment of the present invention.
  • the flyback power supply circuit can reduce the switching loss of the switching transistor through its internal clamp delay circuit, thereby improving circuit efficiency.
  • the flyback power switch circuit mainly includes a voltage input terminal Viii, a transformer 200, a rectifier diode D2, an output capacitor C2, a voltage output terminal Vo, an N-channel field effect transistor (referred to as a MOS transistor) Ql, and a control IC. 100 and clamp delay circuit 300.
  • FIG. 3 shows an illustration of a switching transistor composed of an N-channel field effect transistor, and it is obvious that the switching transistor is not limited to the above device.
  • the transformer 200 includes a primary winding, a secondary winding, and an auxiliary winding disposed on one side of the primary winding. It is easy to understand that the number of turns of the auxiliary winding can be designed by the needs of the actual transformer. According to the same principle of the phase of the same name, the auxiliary winding is identical to the secondary winding, and the output is started when the MOS transistor Q1 is turned off.
  • the output diode D2 has a secondary winding of the transformer 200 connected to the voltage output terminal Vo of the flyback switching power supply circuit. As shown in Fig. 3, the anode of the output diode 1) 2 is connected to the second terminal (terminal No. 3) of the secondary winding, and the cathode of the output diode D2 is connected to the voltage output terminal Vo of the flyback power supply circuit.
  • the output capacitor C2 is used to filter the output voltage.
  • the output capacitor C2 is connected to the output of the flyback switching power supply circuit and the other end is connected to a ground reference.
  • the MOS transistor Q1 is for controlling the voltage on the primary winding of the transformer 200, wherein a drain of the MOS transistor Q1 is connected to the second terminal (terminal No. 2) of the primary winding. A source of the MOS transistor Q1 is connected to a ground reference via a resistor R. When the pulse width modulated signal is turned off, a flyback voltage is reflected by the secondary winding to the primary winding and the auxiliary winding.
  • the VCC ffl of the control IC 100 is provided with a pulse width modulation signal for driving the gate of the MOS transistor Q1, wherein the control IC 100 includes a VCC input terminal for receiving a voltage, a GATE terminal for connecting the gate of the MOS transistor Q1, and a ground reference for connection. GND ground.
  • the control IC is when the voltage received by the control IC 100 exceeds the startup threshold voltage 100 will generate a pulse width adjustment signal and transmit it from a GATE terminal connected to the cabinet of the MOS transistor Q1.
  • the pulse width adjustment signal will drive a gate (G pole) of the MOSFET Q1 for pulse width adjustment control.
  • the clamp delay circuit 300 is configured to clamp the gate potential of the MOS transistor to a low potential such that the MOS transistor Qi is turned on at a valley of its drain potential damped vibration, wherein the clamp delay circuit 300 is connected from the auxiliary winding to the MOS transistor Q1.
  • the cabinet is very.
  • the clamp delay circuit 300 includes a diode T1, a first voltage dividing resistor R l , a second voltage dividing resistor R2, a voltage stabilizing capacitor C1 and a diode D1.
  • the stabilizing capacitor C1 is charged according to the voltage generated by the auxiliary winding, and the stabilizing capacitor C1 is connected in parallel with the auxiliary winding of the transformer 200, and one end of the stabilizing capacitor Ci is combined with the first terminal (terminal No. 6) of the auxiliary winding. Connect to a ground reference.
  • the diode D1 is connected from the second terminal (terminal No. 5) of the auxiliary winding of the transformer 200 to the other end of the voltage stabilizing capacitor C i .
  • the anode of the diode D1 is connected to the second terminal of the auxiliary winding of the transformer 200, and the cathode is connected to one end of the stabilizing capacitor C1.
  • the first voltage dividing resistor R1 and the second voltage dividing resistor R2 resistors are connected in series to form a voltage dividing circuit, and the voltage dividing circuit is connected in parallel with the voltage stabilizing capacitor C1.
  • the voltage dividing circuit is used for dividing the voltage stored in the voltage stabilizing capacitor Ci, that is, the first voltage dividing resistor R1 and the second voltage dividing resistor R2 are divided by the voltage stored therein.
  • the above voltage dividing circuit is only a preferred indication f, and those skilled in the art can reasonably adjust the size of the voltage dividing resistor according to the actual situation, thereby achieving the best effect.
  • the transistor T1 is used to clamp the gate potential of the MOS transistor Q1 to a low level during the on period, so that the MOS transistor Q1 is turned on at the valley of its drain potential damping vibration.
  • the base of the transistor T1 is connected to a voltage dividing circuit (between the first voltage dividing resistor R1 and the second voltage dividing resistor R2), and the collector of the transistor T1 is connected to the gate of the MOS transistor Q1.
  • the flyback switching power supply circuit further includes a first resistor R3, and the GATE terminal of the bundle control IC 100 is connected to the drain of the MOS transistor Q1 to perform a current limiting function, thereby controlling the conduction of the MOS transistor Q1.
  • a second resistor R4 is connected from the source of the MOS transistor Q1 to a ground reference, and the second resistor R4 also acts as a current limiter in the circuit.
  • the control IC 100 detects whether the voltage at the VCC input exceeds the startup threshold voltage. If the detection is YES, the control IC i00 will generate a pulse width modulation signal and a gate from the MOS transistor Qi. Connect to the GATE terminal to launch.
  • the MOSFET Q1 When the iC 100 is controlled to output a high potential to the gate of the MOSFET Q1, the MOSFET Q1 is turned on. At this time, the first end of the primary winding of the transformer 200 is at a high potential, and the auxiliary winding 6 of the transformer 600 is also at a high potential end, then two The pole tube D1 is turned off, and the clamp delay circuit 300 is not fraudulent.
  • the MOS transistor Q1 When the control IC 100 outputs a low potential to the gate of the MOS transistor Q1, the MOS transistor Q1 is turned off. When the MOS transistor Q1 is turned off, the i-terminal of the primary winding of the transformer 200 is at a low potential, and the fifth winding of the auxiliary winding is at a high potential end, and the voltage waveform thereof is similar to that shown in Fig. 2 as damping vibration.
  • the diode D2 is turned on, and the clamp delay circuit 300 starts operating. Specifically, since the first voltage dividing resistor Ri, the second voltage dividing resistor R2, and the voltage stabilizing capacitor Ci are appropriately set, the auxiliary winding of the transformer 200 is charged to C1 and passes through the first voltage dividing resistor Ri and the second voltage dividing unit.
  • the resistor R2 divides the voltage to turn on the transistor T1, so that the drain of the MOS transistor Q1 is clamped to a low potential, and the control MOS transistor Q1 is delayed in conduction at the valley of
  • the present invention provides a clamp delay circuit in a flyback power supply circuit, and an auxiliary winding is added to the transformer.
  • the clamp delay circuit By using the clamp delay circuit, the switching loss of the switching transistor can be reduced, thereby improving circuit efficiency. .

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Dc-Dc Converters (AREA)
  • Liquid Crystal (AREA)

Abstract

一种反激式开关电源电路及应用该电路的背光源驱动装置。该反激式开关电源电路包括：变压器（200），其包括一初级绕组、一次级绕组和置于该初级绕组一侧的一辅助绕组；输出整流器（D2），其从变压器的次级绕组连接至该反激式开关电源电路的输出端；开关晶体管（Q1），其用于控制初级绕组上的电压；控制器（100），其用于提供脉冲宽度调制信号以驱动开关晶体管的栅极；钳位延迟电路（300），其用于将开关晶体管的栅极电位钳制为低电位，使得该开关晶体管在其漏极电位阻尼振动的波谷处导通。通过在该开关电源电路中设置钳位延迟电路，并在变压器中增设辅助绕组，使得开关晶体管在其漏极电位阻尼振动的波谷处导通，降低开关晶体管的开关损耗。

Description

反激式开关电源电路及应用该电路的背光源驱动装置 技术领域
本发明涉及一种电源技术领域， 尤其涉及一种反激式开关电源电路及应用该电路的 背:光源驱动装置。 背景技术
近年来， 随着电源技术的飞速发展， 开关稳压电源正朝着小型化、 高频化、 集成化 的方向发展， 高效率的开关电源已经得到越来越广泛的应用。 反激式电源电路以其电路 简单、 可以高效提供直流输出等许多优点、 特别适合例如家用电器、 电池充电器和很多 其他设计小功率的开关电源。
反激式开关电源是指反激高频变压器隔离输入输出回路的开关电源。 "反激 ( FLY BACK) "具体所指是当输入为高电平 （开关管接通） 时输出线路中串联的电感为放电状 态， 相反输入为高电平 开关管断开）时， 输出线路中的电感为充电状态。 图 : I显示为现 有技术中应 在液晶显示器上的反激式开关电源电路的示意图， 如图 1 所示， 该开关电 源电路主要包括： 一电压输入端、 一控制 IC、 一功率 MOS管、 一变压器、 一整流二极 管和一输出电容。
具体地， MOS管由控制 IC来控制， 通过控制 IC产生的脉冲宽度调节信号来闭合或 导通 MOS管。 在功率 MOS管导通时， 变压器的初级绕组电感电流开始上升， 此时由于 次级绕组的关系， 整流二极管截止， 变压器储存能量。 在功率 MOS管截止时， 变压器的 初级绕组的电感感应电压反向， 此时整流二极管导通， 变压器中的能量经 ώ该整流二极 管向负载供电。
然而， 上述的反激式幵关电源拓 ί卜线路设 if中， 使用控制 IC来直接控制 MOS开关 管的通断。 由于变压器内部的寄生电容效应， 在 MOS管关断后， 其漏极（D极） 的电位 不会立即稳定， 而会按照阻尼振动趋于稳定（如图 2所示）。 由于在此过程中未考虑其阻 尼振动效应， 则会产生较高的 MOS管的开关损耗。 因此， 如何解决上述 1¾]题， 以降低反激式幵关电源中 MOS管的开关损耗， 乃业界所 致力的课题之 发明内容 本发明所要解决的技术问题之一是需要提供一种反激式开关电源电路， 该电路能够 有效降低 MOS管的开关损耗。 另外， 还提供了应用该电路的背光源驱动装置。
1 ) 为了解决上述技术问题， 本发明提供了一种反激式开关电源电路， 包括： 一变压 器， 其包括一初级绕组、 一次级绕组和置于该初级绕组一侧的一辅劭绕组； 一输出整流 器， 其丛所述变压器的次级绕组连接至所述反激式开关电源电路的输出端； 一开关晶体 管， 其用于控制所述初级绕组上的电压， 其中所述开关晶体管的漏极连接至所述初级绕 组的一端； 一控制器， 其 ^于提供脉冲宽度调制信号以驱动所述开关晶体管的極极， 其 中所述控制器包括连接所述开关晶体管的栅极的 GATE端； 一钳位延迟电路， 其用于将 所述开关晶体管的 »极电位钳制为低电位， 使得所述幵关晶体管在其漏极电位阻尼振动 的波谷处导通， 其中所述钳位延迟电路从所述辅助绕组连接至所述幵关晶体管的栅极。
2) 在本发明的第 1 ) 项的一个优选实施方式中， 所述钳位延迟电路进一步包括： 一稳压电容， 其根据所述辅助绕组所产生的电压进行充电， 所述稳压电容与所述辅 助绕组并联连接， 并旦所述稳压电容的一端与所述辅助绕组的第一端子一并连接至一接 地参考；
一二极管， 其 所述辅助绕组的第二端子连接至所述稳压电容的另一端； 一分压电路， 其用于对所述稳压电容内部存储的电压进行分压， 所述分压电路与所 述稳压电容并联连接；
一三极管， 其在导通期间 于将所述开关晶体管的栅极电位钳制为低电位， 使得所 述开关晶体管在其漏极电位阻尼振动的波谷处导通， 其中所述三极管的基极连接至所述 分压电路， 所述三极管的集电极连接至所述开关晶体管的栅极。
3 )在本发明的第 1 )项或第 2)项中的一个优选实施方式中， 所述分压电路由一第-一 分压电阻和一第二分压电阻串联连接组成， 所述三极管的基极连接至所述第一分压电阻 和第二分压电阻之间。
4) 在本发明的第 1 ) 项-第 3 ) 项中任一项的 ·个优选实施方式中， 在所述控制器输 出低电位时， 所述幵关晶体管截止， 进而所述辅助绕组向所述稳压电容充电并通过所述 第一分压电阻和第二分压电阻分压来导通所述:三极管， 所述:三极管将所述开关晶体管的 栅极电位钳制为低电位， 使得所述幵关晶体管在其漏极电位阻尼振动的波谷处导通。
5 ) 在本发明的第 1 ) 项-第 4) 项中任一项的一个优选实施方式中， 在所述控制器输 出高电位时， 所述开关晶体管导通， 所述钳位延迟电路不工作。
6) 在本发明的第 1 ) 项-第 5 ) 项中任一项的一个优选实施方式中， 还包括： 一第一 电阻， 其^所述控制器的 GATE端连接至所述开关晶体管的檝极。
7) 在本发明的第 ) 项-第 6) 项中任一项的一个优选实施方式中， 还包括： 一第二 电阻， 其从所述开关晶体管的源极连接至一接地参考。
8) 在本发明的第 1 ) 项-第 7) 项中任一项的一个优选实施方式中， 还包括： ·输出 电容， 其用于对输出电压进行滤波， 所述输出电容一端与所述反激式幵关电源电路的输 出端连接， 另一端连接至 ·接地参考。
9) 在本发明的第】） 项-第 8) 项中任一项的一个优选实施方式中， 所述输出整流器 为一整流二极管。
10)根据本发明的另一方面， 还提供了一种背光源驱动装置， 包括如上所述的反激式 开关电源电路。 与现有技术相比， 本发明的一个或多个实施例可以具有如下优点- 本发明通过在反激式开关电源电路中设置了钳位延迟电路， 并在变压器中增设了辅 助绕组， 通过上述电路在 MOS 管从截止到再次导通时将 MOS 管的栅极电位钳制为 低， 控制 MOS管在其漏极电位阻尼振动的波谷处导通， 这样会使得 MOS管导通时的电 压累积减小， 避免电压峰值， 降低！ V10S管的开关损耗。
本发明的其它特征和优点将在随后的说明书中阐述， 并且， 部分地从说明书中变得 显而易见， 或者通过实施本发明而了解。 本发明的目的和其他优点可通过在说明书、 权 利要求书以及 i 图中所特别指出的结构来实现和获得。 图锐明
ϋ图用来提供对本发明的进一步理解， 并 构成说明书的一部分， 与本发明的实施 倒共同 ^于解释本发明， 并不构成对本发明的限制。 在 ^图中：
图 1是一现有技术中反激式开关电源电路的示意图； 图 2是反激式开关电源电路中 MOS管漏极 （D极） 电位的阻尼振动示意图； 图 3是根据本发明一实施例的反激式开关电源电路的示意图。 具体实施方式
为使本发明的目的、 技术方案和优点更加清楚， 以下结合跗图对本发明诈进一步地 详细说明。
请参考图 3 , 图 3显示根据本发明一实施例的反激式电源开关电路， 该反激式电源电 路通过其内部的锘位延迟电路， 能够降低开关晶体管的开关损耗， 进而提升电路效率。
如图 3所示， 该反激式电源开关电路主要包括电压输入端 Viii、 变压器 200、 整流二 极管 D2、 输出电容 C2、 电压输出端 Vo、 N沟道场效应晶体管 （简称 MOS管） Ql、 控 制 IC 100及钳位延迟电路 300。
容易理解， 图 3 示出了 N沟道场效应晶体管构成的开关晶体管的一个示倒， 很明 显， 开关晶体管不限于上面的设备。
其中， 变压器 200 包括 ·初级绕组、 一次级绕组和置于该初级绕组一侧的一辅助绕 组。 容易理解的是， 该辅助绕组的匝数可由实际变压器的需要来设计。 根据同名端相位 相同的原理， 该辅助绕组与次级绕组一致， 在 MOS管 Q1截止时开始输出。
输出二极管 D2, 其 变压器 200的次级绕组连接至该反激式开关电源电路的电压输 出端 Vo。 如图 3所示， 该输出二极管 1)2的阳极连接次级绕组的第二端子（3号端）， 该 输出二极管 D2的阴极连接该反激式幵关电源电路的电压输出端 Vo。
输出电容 C2, 其用于对输出电压进行滤波， 该输出电容 C2 —端与反激式开关电源 电路的输出端连接， 另一端连接至一接地参考。
MOS管 Q1 , 其用于控制该变压器 200的初级绕组上的电压， 其中该 MOS管 Q1的 一漏极连接至初级绕组的第二端子（2号端）。 该 MOS管 Q1的一源极通过一电阻 R 连 接至一接地参考。 在脉冲宽度调制信号关闭时， 一反激电压将被^次级绕组反射至初级 绕组和辅助绕组。
控制 IC 100的 VCC ffl于提供脉冲宽度调制信号以驱动 MOS管 Q1的栅极， 其中控 制 IC 100包括用于接收电压的 VCC输入端、 连接 MOS管 Q1的栅极的 GATE端和连接 接地参考的 GND接地端。 当控制 IC 100所接收的电压超过启动阈值电压时， 该控制 IC 100就将产生一脉冲宽度调节信号， 并从与 MOS管 Q 1的一櫥极连接 GATE端发射出去。 该脉 宽度调节信号将驱动 M0S管 Q1的一栅极 （G极） ， 以用于脉冲宽度调节控制。
钳位延迟电路 300用于将 M0S管 的栅极电位钳制为低电位， 使得 MOS管 Qi在 其漏极电位阻尼振动的波谷处导通， 其中钳位延迟电路 300从辅助绕组连接至 MOS 管 Q1 的櫥极。 该钳位延迟电路 300包括一 极管 Tl、 一第一分压电阻 R l、 一第二分压电 阻 R2、 一稳压电容 C1和一二极管 Dl。 稳压电容 C1根据辅助绕组所产生的电压进行充电， 该稳压电容 C1与变压器 200的 辅助绕组并联连接， 并 该稳压电容 Ci的一端与辅助绕组的第一端子 （6号端） 一并连 接至一接地参考。
二极管 D1从变压器 200的辅助绕组的第二端子 （5号端） 连接至稳压电容 C i的另 一端。 如图所示， 二极管 D1的阳极连接至该变压器 200的辅助绕组的第二端子， 阴极连 接该稳压电容 C1的一端。 第一分压电阻 R1和第二分压电阻 R2电阻串联连接组成了分压 电路， 该分压电路与稳压电容 C 1并联。 该分压电路用于对稳压电容 Ci 内部存储的电压 进行分压， 即利 ^第一分压电阻 R1和第二分压电阻 R2迸行其内部存储的电压的分压。 当然， 上述分压电路仅为一优选示 f , 本领域技术人员可以根据实际情况来合理调整分 压电阻的大小， 从而达到最好的效果。
三极管 T1在导通期间用于将 MOS管 Q1 的栅极电位钳制为低电位， 使得 MOS管 Q1在其漏极电位阻尼振动的波谷处导通。 该三极管 T1 的基极连接至分压电路 （第一分 压电阻 R1和第二分压电阻 R2之间） ， 并且该三极管 T1的集电极连接至 MOS管 Q1的 栅极。
另外， 该反激式开关电源电路还包括一第一电阻 R3 , 其丛控制 IC 100的 GATE端连 接至 MOS管 Q1的檝极， 起到限流作用，迸而控制 MOS管 Q1的导通和截止的速度。 一 第二电阻 R4, 其从 MOS管 Q1的源极连接至一接地参考， 该第二电阻 R4在电路中也起 到限流作用。 接着， 说明该反激式电源开关电路的详细操作。 参阅图 3， 首先， 控制 IC 100检测 其 VCC输入端的电压是否超过启动阈值电压， 若检测为是时， 则该控制 IC i00将产生一 脉冲宽度调制信号， 并从与 M0S管 Qi的一栅极连接 GATE端发射出去。
当控制 iC 100输出高电位至 M0S管 Q1的栅极时， M0S管 Q1导通。 此时， 变压器 200的初级绕组的 1号端为高电位， 且变压器 600的辅助绕组 6号端也为高电位端， 则二 极管 Dl截止， 钳位延迟电路 300不工诈。
当控制 IC 100输出低电位至 MOS管 Q1的栅极时， MOS管 Q1截止。 MOS管 Q1 截止时， 变压器 200的初级绕组的 i号端为低电位， 辅助绕组 5号端为高电位端， 其电压 波形同样类似图 2所示为阻尼振动。 此^二极管 D2导通， 钳位延迟电路 300开始工作。 具体地， 由于合理的设置第一分压电阻 Ri、 第二分压电阻 R2和稳压电容 Ci 的大 小， 使得变压器 200的辅助绕组向 C1充电并通过第一分压电阻 Ri和第二分压电阻 R2 分压来导通三极管 T1 , 进而使得 MOS管 Q1的檝极钳位为低电位， 控制 MOS管 Q1在 其漏极电位阻尼振动的波谷处延迟导通。
这主要考虑到， 由于变压器 200内部的寄生电容效应， MOS管 Q1关断后， 其漏极 的电位不会立即稳定， 而会按照阻尼振动趋于稳定， 通过上述电路在 MOS 管从截止到 再次导通时将 MOS 管的栅极电位钳制为低， 控制 MOS管在其漏极电位阻尼振动的波谷 处导通， 这样会使得 MOS管导通时的电压累积减小， 避免电压峰值， 降低 MOS管的开 关损耗。 这是因为， 开关损耗近似等于 Δν*ΔΙ/4, 在波谷处 ΔΥ最小， 从而可以降低幵关 损耗。
另外， 还涉及一种背光源驱动装置， 其包括上述的反激式开关电源电路。
综上， 本发明通过在反激式幵关电源电路中设置了钳位延迟电路， 并在变压器中增 设了辅助绕组， 通过利用该钳位延迟电路能够降低开关晶体管的开关损耗， 进而提升电 路效率。
以上所述， 仅为本发明较佳的具体实施方式， 但本发明的保护范围并不局限于此， 任何熟悉该技术的人员在本发明所揭露的技术范围内， 可轻易想到的变化或替换， 都应 涵盖在本发明的保护范圈之内。 因此， 本发明的保护范围应该以权利要求的保护范围为 准。

Claims

权利要求书
1、 ·种反激式幵关电源电路， 包括-
-变压器， 其包括 ·初级绕组、 一次级绕组和置于该初级绕组一侧的一辅助绕组； 一输出整流器， 其从所述变压器的次级绕组连接至所述反激式开关电源电路的输出 端；
一开关晶体管，其用于控制所述初级绕组上的电压，其中所述开关晶体管的漏极连接 至所述初级绕组的一端；
一控制器，其用于提供脉冲宽度调制信号以驱动所述幵关晶体管的栅极，其中所述控 制器包括连接所述开关晶体管的栅极的 GATE端；
一钳位延迟电路，其用于将所述幵关晶体管的極极电位钳制为低电位，使得所述开关 晶体管在其漏极电位阻尼振动的波谷处导通,其中所述钳位延迟电路从所述辅助绕组连接 至所述开关晶体管的櫥极。
2、 根据权利要求 1所述的反激式开关电源电路， 其中， 所述钳位延迟电路进一步包 括- 一稳压电容，其根据所述辅助绕组所产生的电压进行充电，所述稳压电容与所述辅劭 绕组并联连接，并且所述稳压电容的一端与所述辅助绕组的第一端子一并连接至一接地参 -ΐί；
一二极管， 其从所述辅助绕组的第二端子连接至所述稳压电容的另一端； 一分压电路，其用于对所述稳压电容內部存储的电压进行分压，所述分压电路与所述 稳压电容并联连接；
一三极管，其在导通期间用于将所述开关晶体管的檝极电位钳制为低电位，使得所述 开关晶体管在其漏极电位阻尼振动的波谷处导通，其中所述 极管的基极连接至所述分压 电路， 所述三极管的集电极连接至所述开关晶体管的栅极。
3、 根据权利要求 2所述的反激式幵关电源电路， 其中，
所述分压电路由一第一分压电阻和一第二分压电阻串联连接组成，所述 极管的基极 连接至所述第一分压电阻和第二分压电阻之间。
4、 根据权利要求 3所述的反激式开关电源电路， 其中，
在所述控制器输出低电位^，所述开关晶体管截止，进而所述辅劭绕组向所述稳压电 容充电并通过所述第一分压电阻和第二分压电阻分压来导通所述 极管，所述:三极管将所 述幵关晶体管的櫥极电位钳制为低电位,使得所述幵关晶体管在其漏极电位阻尼振动的波 谷处导通。
5、 根据权利要求 4所述的反激式开关电源电路， 其中，
在所述控制器输出高电位时， 所述开关晶体管导通， 所述钳位延迟电路不工作。
6、 根据权利要求〗所述的反激式开关电源电路， 其中， 还包括- 一第一电阻， 其从所述控制器的 GATE端连接至所述幵关晶体管的栅极。
7、 根据权利要求 6所述的反激式开关电源电路， 其中， 还包括- 一第二电阻， 其从所述开关晶体管的源极连接至一接地参考。
8、 根据权利要求 7所述的反激式开关电源电路， 其中， 还包括：
一输出电容，其用于对输出电压进行滤波，所述输出电容一端与所述反激式开关电源 电路的输出端连接， 另一端连接至一接地参考。
9、 根据权利要求 8所述的反激式开关电源电路， 其中， 所述输出整流器为一整流二 极管。
10、 一种背光源驱动装置， 包括反激式开关电源电路，
所述反激式开关电源电路， 包括：
一变压器， 其包括一初级绕组、 一次级绕组和置于该初级绕组一侧的一辅助绕组： 一输出整流器， 其 A所述变压器的次级绕组连接至所述反激式开关电源电路的输出
¾ :
一开关晶体管，其用于控制所述初级绕组上的电压，其中所述开关晶体管的漏极连接 至所述初级绕组的一端；
一控制器，其用于提供脉冲宽度调制信号以驱动所述开关晶体管的栅极，其中所述控 制器包括连接所述幵关晶体管的栅极的 GATE端；
一钳位延迟电路，其用于将所述开关晶体管的極极电位钳制为低电位，使得所述开关 晶体管在其漏极电位阻尼振动的波谷处导通，其中所述钳位延迟电路从所述辅助绕组连接 至所述开关晶体管的栅极。
11、根据权利要求 10所述的背光源驱动装置， 其中， 所述钳位延迟电路进一歩包括: 一稳压电容，其根据所述辅助绕组所产生的电压迸行充电，所述稳压电容与所述辅助 绕组并联连接，并且所述稳压电容的一端与所述辅助绕组的第一端子一并连接至一接地参 考：
一二极管， 其 所述辅助绕组的第二端子连接至所述稳压电容的另一端；
一分压电路，其用于对所述稳压电容内部存储的电压进行分压，所述分压电路与所述 稳压电容并联连接； 一-三极管，其在导通期间用于将所述开关晶体管的樋极电位钳制为低电位，使得所述 开关晶体管在其漏极电位阻尼振动的波谷处导通，其中所述三极管的基极连接至所述分压 电路， 所述:三极管的集电极连接至所述开关晶体管的栅极。
12、 根据权利要求 11所述的背光源驱动装置， 其中，
所述分压电路由一第一分压电阻和一第二分压电阻串联连接组成，所述≡极管的基极 连接至所述第一分压电阻和第二分压电阻之间。
13、 根据权利要求 12所述的背光源驱动装置， 其中，
在所述控制器输出低电位 所述开关晶体管截止，进而所述辅助绕组向所述稳压电 容充电并通过所述第一分压电阻和第二分压电阻分压来导通所述三极管，所述三极管将所 述开关晶体管的栅极电位钳制为低电位，使得所述开关晶体管在其漏极电位阻尼振动的波 谷处导通。
14、 根据权利要求 13所述的背光源驱动装置， 其中，
在所述控制器输出高电位^, 所述开关晶体管导通， 所述钳位延迟电路不工作。
15、 根据权利要求 10所述的背光源驱动装置， 其中， 还包括：
一第一电阻， 其从所述控制器的 GATE端连接至所述开关晶体管的栅极。
16、 根据权利要求 15所述的背光源驱动装置， 其中， 还包括：
一第二电阻， 其从所述开关晶体管的源极连接至一接地参考。
17、 根据权利要求 16所述的背光源驱动装置， 其中， 还包括：
•输出电容，其用于对输出电压进行滤波，所述输出电容一端与所述反激式幵关电源 电路的输出端连接， 另一端连接至一接地参考。
18、 根据权利要求 17所述的背光源驱动装置， 其中， 所述输出整流器为一整流二极
PCT/CN2014/070840 2013-12-06 2014-01-17 反激式开关电源电路及应用该电路的背光源驱动装置 Ceased WO2015081627A1 (zh)

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RU2016121671A RU2637773C9 (ru) 2013-12-06 2014-01-17 Схема обратноходового импульсного источника питания и драйвер подсветки, в котором она используется
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