WO2015052838A1 - Circuit de découplage - Google Patents

Circuit de découplage Download PDF

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Publication number
WO2015052838A1
WO2015052838A1 PCT/JP2013/077792 JP2013077792W WO2015052838A1 WO 2015052838 A1 WO2015052838 A1 WO 2015052838A1 JP 2013077792 W JP2013077792 W JP 2013077792W WO 2015052838 A1 WO2015052838 A1 WO 2015052838A1
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WIPO (PCT)
Prior art keywords
input
output terminal
signal
distribution
circuit
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PCT/JP2013/077792
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English (en)
Japanese (ja)
Inventor
英俊 牧村
西本　研悟
深沢　徹
良和 吉田
和宜 大塚
Original Assignee
三菱電機株式会社
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
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Application filed by 三菱電機株式会社 filed Critical 三菱電機株式会社
Priority to JP2015541406A priority Critical patent/JPWO2015052838A1/ja
Priority to PCT/JP2013/077792 priority patent/WO2015052838A1/fr
Publication of WO2015052838A1 publication Critical patent/WO2015052838A1/fr

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/18—Phase-shifters
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H01Q1/521—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/18—Networks for phase shifting
    • H03H7/185—Networks for phase shifting comprising distributed impedance elements together with lumped impedance elements
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/01—Frequency selective two-port networks
    • H03H7/06—Frequency selective two-port networks including resistors
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/01—Frequency selective two-port networks
    • H03H7/17—Structural details of sub-circuits of frequency selective networks
    • H03H7/1741—Comprising typical LC combinations, irrespective of presence and location of additional resistors
    • H03H7/175—Series LC in series path
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/01—Frequency selective two-port networks
    • H03H7/17—Structural details of sub-circuits of frequency selective networks
    • H03H7/1741—Comprising typical LC combinations, irrespective of presence and location of additional resistors
    • H03H7/1775—Parallel LC in shunt or branch path
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B7/00—Radio transmission systems, i.e. using radiation field
    • H04B7/14—Relay systems
    • H04B7/15—Active relay systems
    • H04B7/155—Ground-based stations
    • H04B7/15528—Control of operation parameters of a relay station to exploit the physical medium
    • H04B7/1555—Selecting relay station antenna mode, e.g. selecting omnidirectional -, directional beams, selecting polarizations

Definitions

  • the present invention relates to, for example, a decoupling circuit that connects a plurality of antennas mounted on a wireless communication device or the like, and more particularly, to a decoupling circuit that reduces coupling between two antennas.
  • Non-Patent Document 1 discloses a decoupling circuit composed of two transmission lines and a reactance element that connects the two transmission lines. The mutual coupling is reduced.
  • Patent Document 1 discloses a method of reducing coupling between antennas by connecting antennas with a connection circuit.
  • the conventional decoupling circuit is configured as described above, in principle, the coupling is reduced at one frequency. For this reason, when the frequency band to be used is wide, there existed a subject which cannot reduce coupling in the whole use frequency band. In particular, when the coupling phase between the antennas greatly changes within the used frequency band, there is a problem that the coupling cannot be reduced over the entire used frequency band.
  • the present invention has been made to solve the above-described problems, and provides a decoupling circuit capable of reducing the coupling in the entire used frequency band even when the coupling phase greatly changes in the used frequency band. For the purpose.
  • the decoupling circuit according to the present invention has a first signal distribution means for distributing a signal input from the first input / output terminal to the second and third input / output terminals, and a signal input from the fourth input / output terminal.
  • the second signal distribution means for distributing the received signal to the fifth and sixth input / output terminals, and the third signal input means or the sixth input / output terminal.
  • Amplitude and phase adjusting means for adjusting the amplitude and phase of the signal distributed by the second signal distributing means, from the first input / output terminal to the fourth input / output terminal through the second and fifth input / output terminals.
  • the amplitude phase adjustment means the coupling phase of the first signal path to the second signal path from the first input / output terminal to the fourth input / output terminal through the amplitude phase adjustment means is opposite in phase.
  • the phase adjustment amount is set.
  • the phase adjustment amount in the amplitude phase adjustment means is set so that the coupling phase of the first signal path and the second signal path is opposite, the frequency used Even when the coupling phase changes greatly within the band, there is an effect that the coupling can be reduced over the entire use frequency band.
  • FIG. 6 is an explanatory diagram showing the effect of the decoupling circuit according to the first embodiment.
  • FIG. 1 is a block diagram showing a decoupling circuit according to Embodiment 1 of the present invention.
  • FIG. 1 is a block diagram showing a decoupling circuit according to Embodiment 1 of the present invention.
  • a distribution circuit 1 serving as a first signal distribution unit includes an input / output terminal 11 (first input / output terminal) for high-frequency signals, an input / output terminal 12 (second input / output terminal) serving as a connection point, and Connected to the input / output terminal 13 (third input / output terminal), the high frequency signal input from the input / output terminal 11 is divided into two, and one high frequency signal after distribution is output to the input / output terminal 12, The other high-frequency signal after distribution is output to the input / output terminal 13.
  • An antenna 3 (first antenna) is connected to the input / output terminal 12.
  • the distribution circuit 2 as the second signal distribution means includes an input / output terminal 21 (fourth input / output terminal) for high-frequency signals, an input / output terminal 22 (fifth input / output terminal) as connection points, and an input / output terminal 23. (Sixth input / output terminal), the high frequency signal input from the input / output terminal 21 is divided into two, the one high frequency signal after distribution is output to the input / output terminal 22, and the other after distribution Is output to the input / output terminal 23.
  • An antenna 4 (second antenna) is connected to the input / output terminal 22.
  • the amplitude / phase adjustment circuit 5 is connected between the input / output terminal 13 and the input / output terminal 23, and performs processing for adjusting the amplitude and phase of the high-frequency signal distributed by the distribution circuit 1 or the distribution circuit 2.
  • the amplitude phase adjustment circuit 5 constitutes an amplitude phase adjustment means.
  • Route is referred to as A route
  • the signal path (second signal path) of the input / output terminal 11 to the distribution circuit 1 to the input / output terminal 13 to the amplitude / phase adjustment circuit 5 to the input / output terminal 22 to the distribution circuit 2 to the input / output terminal 21 ) Is called the B route.
  • the signal distribution ratio in the distribution circuits 1 and 2 and the amplitude adjustment amount in the amplitude phase adjustment circuit 5 are set so that the combined amplitudes of the A route and the B route are equal, and the A route and the B route.
  • the phase adjustment amount in the amplitude and phase adjustment circuit 5 is set so that the coupling phase with the phase is reversed.
  • FIG. 2 is a block diagram showing an amplitude phase adjustment circuit 5 of the decoupling circuit according to the first embodiment of the present invention.
  • the amplitude / phase adjustment circuit 5 includes a transmission line 31 and a parallel resonant circuit 32 connected to the transmission line 31 in a shunt, and one end of the transmission line 31 is connected to the input / output terminal 13. The other end is connected to the input / output terminal 23.
  • the parallel resonance circuit 32 includes a capacitor 32a and an inductor 32b, which are lumped constant elements.
  • the distribution circuit 1 distributes the high frequency signal into two, outputs one high frequency signal after distribution to the input / output terminal 12, and outputs the other high frequency signal after distribution. Is output to the input / output terminal 13.
  • the high frequency signal output from the distribution circuit 1 to the input / output terminal 12 is supplied to the antenna 3, and electromagnetic waves generated by the high frequency signal are radiated from the antenna 3 to the space. At this time, a part of the electromagnetic wave radiated from the antenna 3 to the space is received by the antenna 4, and a high-frequency signal related to the electromagnetic wave is input to the distribution circuit 2 via the input / output terminal 22.
  • the high frequency signal output from the distribution circuit 1 to the input / output terminal 13 passes through the amplitude / phase adjustment circuit 5 and is input to the distribution circuit 2 via the input / output terminal 23.
  • the distribution circuit 2 has a high frequency signal (high frequency signal passing through the A route) input from the antenna 4 via the input / output terminal 22 and a high frequency signal (B) input from the amplitude / phase adjustment circuit 5 via the input / output terminal 23. High-frequency signal passing through the route) and the combined high-frequency signal is output to the input / output terminal 21.
  • FIG. 3 is an explanatory diagram showing an example of frequency characteristics of the coupling amplitude between the input / output terminal 11 and the input / output terminal 21 when the high-frequency signal passes through the A route (characteristics of the antenna alone).
  • FIG. 4 is an explanatory diagram showing an example of the frequency characteristic of the coupling phase between the input / output terminal 11 and the input / output terminal 21 when the high-frequency signal passes through the A route (characteristic of the antenna alone).
  • the coupling of the A route varies depending on the characteristics of the antennas 3 and 4, the arrangement, and the surrounding space conditions.
  • the combination A A (f) of the A route is defined as the following formula (1).
  • Equation (1) f is the frequency, s A (f) is the amplitude of coupling at the frequency f of the A route, and ⁇ A (f) is the phase of coupling at the frequency f of the A route.
  • the unit of phase is (°).
  • the coupling of the B route varies depending on the design value of the amplitude / phase adjustment circuit 5.
  • the combination S B (f) of the B route is defined as the following equation (2).
  • S B (f) s B (f) exp (j ⁇ B (f)) (2)
  • f the frequency
  • s B (f) the amplitude of coupling at the frequency f of the B route
  • ⁇ B (f) the phase of coupling at the frequency f of the B route.
  • FIG. 2 shows a configuration example of the amplitude / phase adjustment circuit 5, but it is known that the parallel resonance circuit 32 connected to the transmission line 31 in a shunt acts as a band-pass filter.
  • the capacitance of the capacitor 32a of the parallel resonance circuit 32 is Cp (F) and the inductance of the inductor 32b is Lp (H)
  • Lp the relationship between the resonance frequency fr of the parallel resonance circuit 32 and Cp
  • the Q value representing the sharpness of resonance is represented by the following equation (6), where R is the characteristic impedance of the transmission line 31.
  • the coupling of the A route via the antennas 3 and 4 and the space generally has bandpass characteristics. Therefore, if the resonant frequency fr and Q value of the parallel resonant circuit 32 are appropriately set, the coupling of the A route S A (f ) And the B route combination S B (f) can be made substantially the same.
  • the resonance frequency fr of the parallel resonance circuit 32 is set to a frequency f Amax at which the coupling A A (f) of the A route becomes maximum within the use frequency band. It is also conceivable that the resonance frequency fr of the parallel resonance circuit 32 is set to the center frequency of the used frequency band.
  • the coupling amplitude difference ⁇ s (f) is defined as in the following equation (7), where the upper limit of the use frequency band is f H and the lower limit is f L.
  • ⁇ s (f) s (fr) ⁇ s (f) (7)
  • a method of searching for the Q value at which the change of the pass amplitude characteristic s LPF (f) of the parallel resonance circuit 32 is closest to s A (f) can be considered by the least square method or the like.
  • the designer may appropriately select the values of Lp and Cp in consideration of other requirements such as the ease of configuration of the parallel resonant circuit 32 and the distribution of s A (f).
  • FIG. 5 is an explanatory diagram showing an example of the pass characteristics of the parallel resonant circuit 32 connected to the transmission line 31 in a shunt.
  • the resonance frequency fr of the parallel resonance circuit 32 is made to coincide with the maximum frequency f Amax within the use frequency band, and the Q value is set to 59.7.
  • the characteristic impedance R of the transmission line 31 is 50 ⁇ . From FIG. 5, it is confirmed that the way of changing the pass amplitude characteristic s LPF (f) within the used frequency band is close to the way of changing the coupling A A (f) of the A route shown in FIG. .
  • the absolute value of the pass amplitude characteristic s LPF (f) and the absolute value of the coupling A A (f) of the A route may be adjusted according to the characteristics of the distribution circuits 1 and 2. Only the way of change needs to be matched.
  • the passing phase characteristic ⁇ LPF (f) when the parallel resonant circuit 32 is connected to the transmission line 31 in a shunt is as shown in FIG.
  • the passing amplitude from the input / output terminal 11 to the input / output terminal 13 is P 1 (dB)
  • the passing amplitude from the input / output terminal 11 to the input / output terminal 12 is P 2 (dB).
  • the passing amplitude from the input / output terminal 21 to the input / output terminal 23 be P 1 (dB)
  • the passing amplitude from the input / output terminal 21 to the input / output terminal 22 be P 2 (dB).
  • the pass characteristics between the terminals in the distribution circuits 1 and 2 are symmetrical.
  • the pass amplitude from the input / output terminal 13 to the input / output terminal 11 is also P 1 (dB).
  • the passing amplitude to the output terminal 21 is also P 1 (dB).
  • the B route coupling S B (f) is determined from the distribution ratio of the distribution circuits 1 and 2 and the pass amplitude characteristics of the parallel resonant circuit 32 connected to the transmission line 31 in a shunt.
  • ⁇ 11-13 (f) which is a passing phase characteristic from input / output terminal 11 to input / output terminal 13
  • input / output terminal 23 is connected to input / output terminal 21.
  • ⁇ 23-21 (f) which is the passing phase characteristic
  • the amplitude phase adjustment circuit 5 may be designed so as to satisfy the following expression (11).
  • the electrical length ⁇ of the transmission line 31 is set so as to satisfy the following conditions (1) and (2).
  • (1) at the maximum frequency f Amax in the used frequency band, A route combined phase phi A and (f Amax), combined phase phi B of Route B (f Amax) is substantially opposite phase.
  • ⁇ LPF ⁇ ( ⁇ LPF (f H ) ⁇ LPF (f L ))
  • FIG. 7 shows an amplitude and phase adjustment circuit when a parallel resonant circuit 32 having the characteristics shown in FIG. 5 is connected to a shunt with respect to a transmission line 31 having an electrical length of 444 ° at the maximum frequency f Amax within the used frequency band.
  • FIG. 5 is an explanatory diagram showing a pass phase characteristic ⁇ p (f) of FIG. Compared with the combined phase ⁇ A (f) of the A route shown in FIG. 4, the passing phase characteristic ⁇ p (f) of the amplitude phase adjustment circuit 5 has a phase of almost 180 ° over the entire use frequency band. You can see that they are different.
  • FIG. 8 is an explanatory diagram showing the effect of the decoupling circuit according to the first embodiment.
  • the worst value of the coupling between the input and output terminals within the used frequency band is about ⁇ 20 dB (1/100) compared to the case without the decoupling circuit. The effect of the present invention to reduce the coupling over the entire use frequency band is confirmed.
  • the signal distribution ratio in the distribution circuits 1 and 2 and the amplitude adjustment amount in the amplitude phase adjustment circuit 5 are set so that the coupling amplitudes of the A route and the B route become equal.
  • the phase adjustment amount in the amplitude phase adjustment circuit 5 is set so that the coupling phase of the A route and the B route is opposite to each other. Even when the coupling amplitude and the coupling phase change greatly, the coupling between the input / output terminal 11 and the input / output terminal 21 can be reduced over the entire use frequency band. It is not particularly difficult to manufacture all of the distribution circuits 1 and 2 and the amplitude / phase adjustment circuit 5 on the same substrate.
  • the amplitude phase adjustment circuit 5 is mounted with a resonance circuit and the change in the passing amplitude and the passing phase difference becomes large, the circuit can be miniaturized.
  • the amplitude phase adjustment circuit 5 in which one parallel resonance circuit is connected to the transmission line 31 in a shunt is shown, but the amplitude adjustment amount and the phase adjustment amount in the amplitude phase adjustment circuit 5 are appropriately designed. If so, the amplitude / phase adjustment circuit 5 may have another configuration. For example, in order to configure the amplitude phase adjustment circuit 5 in which the change of the passing amplitude and the phase difference is extremely steep, a resonance circuit having an extremely high Q value is required. Although it is difficult to realize a resonance circuit having an extremely high Q value, an amplitude / phase adjustment circuit 5 having similar pass characteristics can be configured by combining a plurality of resonance circuits.
  • an amplitude phase adjustment circuit 5 in which a series resonance circuit 35 is connected in series to the transmission lines 33 and 34 may be used.
  • the series resonance circuit 35 is configured by connecting an inductor 35a and a capacitor 35b in series.
  • the amplitude / phase adjustment circuit 5 may include both the parallel resonance circuit 32 and the series resonance circuit 35.
  • FIG. 10 is a block diagram showing a decoupling circuit according to Embodiment 2 of the present invention.
  • a directional coupler 6 (first directional coupler) which is a first signal distribution means is connected to the input / output terminal 11, the input / output terminal 12, the input / output terminal 13 and the input / output terminal 14.
  • the high-frequency signal input from the terminal 11 is divided into two, one high-frequency signal after distribution is output to the input / output terminal 12, and the other high-frequency signal after distribution is output to the input-output terminal 13.
  • the input / output terminal 14 is connected to the GND conductor 43 via a termination resistor 41.
  • the directional coupler 7 (second directional coupler) as the second signal distribution means is connected to the input / output terminal 21, the input / output terminal 22, the input / output terminal 23, and the input / output terminal 24.
  • the high-frequency signal input from the terminal 21 is divided into two, one high-frequency signal after distribution is output to the input / output terminal 22, and the other high-frequency signal after distribution is output to the input-output terminal 23.
  • the input / output terminal 24 is connected to the GND conductor 43 via a termination resistor 42.
  • the distribution circuits 1 and 2 distribute the high-frequency signal input from the input / output terminals 11 and 21 and output one of the distributed high-frequency signals to the input / output terminals 12 and 22 for distribution.
  • the other high-frequency signal is output to the input / output terminals 13 and 23.
  • the directional couplers 6 and 7 receive the high-frequency signal input from the input / output terminals 11 and 21, respectively.
  • the divided high frequency signal may be output to the input / output terminals 12 and 22, and the other high frequency signal after distribution may be output to the input / output terminals 13 and 23.
  • the coupling amount between the input / output terminal 11 and the input / output terminal 14 is very small, and the coupling amount between the input / output terminal 12 and the input / output terminal 13 is very small.
  • the coupling amount between the input / output terminal 21 and the input / output terminal 24 is very small, and the coupling amount between the input / output terminal 22 and the input / output terminal 23 is very small. Therefore, in the directional coupler 6, isolation between the input / output terminal 12 and the input / output terminal 13 is ensured, and in the directional coupler 7, isolation between the input / output terminal 22 and the input / output terminal 23 is ensured.
  • the resistance values of the termination resistors 41 and 42 are generally the same as the standardized impedance for designing the directional couplers 6 and 7 (for example, 50 ⁇ ), but the resistance values are not limited to this. .
  • the input / output terminals over the entire use frequency band. 11 and the input / output terminal 21 can be reduced.
  • the Q value of the parallel resonant circuit 32 is set so that the coupling S A (f) of the A route matches the coupling S B (f) of the B route.
  • the Q value of the parallel resonance circuit 32 may be set so that the passing phase characteristic ⁇ p (f) of the amplitude phase adjustment circuit 5 is equal to the coupling phase ⁇ A (f) of the A route.
  • the electrical length ⁇ (f) of the transmission line 31 is determined by the following equation (15), for example. Is done.
  • ⁇ A (fr) + 180 ° and ⁇ B (fr) are matched, but the reference frequency is not limited to the resonance frequency fr.
  • the range of ⁇ A (f) is [ ⁇ 180 °, 180 °]
  • the range of ⁇ (f) is [0 °, 360 °].
  • the Q value of the parallel resonance circuit 32 is set so that the passing phase characteristic ⁇ p (f) of the amplitude phase adjustment circuit 5 is equal to the coupling phase ⁇ A (f) of the A route.
  • the electrical length ⁇ (f) of the transmission line 31 can be 360 ° at the maximum. As a result, it is possible to reduce the coupling between the antennas over a wide band and to obtain an effect of obtaining a small decoupling circuit.
  • FIG. 11 is a block diagram showing an amplitude / phase adjustment circuit 5 of a decoupling circuit according to Embodiment 4 of the present invention.
  • the short stub 36 is a distributed constant line connected to the transmission line 31 in a shunt, and realizes a parallel resonance circuit for the transmission line 31.
  • the short stub 36 is realized by a triplate line formed in the inner layer of the multilayer substrate.
  • the method of manufacturing the short stub 36 is not limited to this. For example, it may be realized by a microstrip line on a substrate.
  • the Q value of the parallel resonance circuit 32 is set so that the coupling S A (f) of the A route matches the coupling S B (f) of the B route.
  • the parallel resonant circuit 32 is formed by the capacitor 32a and the inductor 32b which are lumped elements. It is expected to be difficult to construct.
  • a stub structure constituted by distributed constant lines can be used as a resonance circuit.
  • the amplitude / phase adjusting circuit 5 is configured by connecting the short stub 36 to the shunt with respect to the transmission line 31.
  • the short stub 36 serves as a parallel resonant circuit, so that the Q value can be freely determined without being restricted by the value of the lumped element. Therefore, effects that can be matched coupling S A of Route A a (f) and B root of binding S B (f) more precisely can be obtained.
  • the method for producing the short stub 36 is not particularly limited. However, when realized with a triplate line, the characteristic impedance of the stub can be lowered as compared with the case of realizing with a microstrip line.
  • the parallel resonant circuit can be made.
  • a plurality of stubs can be arranged in an overlapping manner, so that the circuit area can be reduced.
  • the short stub 36 is connected to the shunt with respect to the transmission line 31, but an open stub may be used instead of the short stub 36.
  • an open stub may be used instead of the short stub 36.
  • some or all of the resonance circuits may be realized by stubs.
  • the stub structure constituted by the distributed constant line is used as the parallel resonant circuit 32.
  • the stub structure constituted by the distributed constant line is used as the series resonant circuit 35. It may be.
  • FIG. FIG. 12 is a block diagram showing the amplitude phase adjustment circuit 5 of the decoupling circuit according to the fifth embodiment of the present invention.
  • the meander line 37 is a transmission line having one end connected to the input / output terminal 13 and the other end connected to the input / output terminal 23.
  • the input / output terminal 13 and the input / output terminal 23 are connected by the transmission line 31.
  • the transmission line 31 is configured by a meander line 37 as shown in FIG. May be. By configuring the transmission line 31 with the meander line 37, the transmission line can be downsized.
  • the transmission line 31 in the amplitude / phase adjustment circuit 5 of FIG. 2 is configured by the meander line 37, but the transmission lines 33 and 34 in the amplitude / phase adjustment circuit 5 of FIG. 9 are configured by the meander line 37.
  • the transmission line 31 in the amplitude / phase adjustment circuit 5 of FIG. 11 may be configured by the meander line 37.
  • FIG. 13 is a block diagram showing the amplitude phase adjustment circuit 5 of the decoupling circuit according to the sixth embodiment of the present invention.
  • a plurality of lumped constant elements 51 for example, capacitors and inductors
  • a plurality of lumped constant elements 52 for example, capacitors and inductors
  • T-type phase shift circuit To form a T-type phase shift circuit, and a plurality of phase shift circuits carry transmission lines.
  • the amount of phase shift can be increased by combining a plurality of phase shift circuits.
  • the phase shift circuit is configured only by the lumped constant elements 51 and 52, the circuit can be reduced in size.
  • a T-type phase shift circuit is shown in FIG. 13, it may be a saddle type phase shift circuit.
  • the antennas 4 and 5 are connected to the input / output terminals 12 and 22, and the example in which the coupling between the antennas is reduced has been described.
  • the coupling exists between the input / output terminal 11 and the input / output terminal 21 through some propagation medium, the coupling can be reduced by applying the present invention.
  • the decoupling circuit according to the present invention is suitable, for example, for a circuit that has a high need for enabling sufficient effects of diversity and MIMO by reducing the coupling between two antennas.
  • 1 distribution circuit (first signal distribution means), 2 distribution circuit (second signal distribution means), 3 antenna (first antenna), 4 antenna (second antenna), 5 amplitude phase adjustment circuit (amplitude phase) Adjustment means), 6 directional coupler (first directional coupler, first signal distribution means), 7 directional coupler (second directional coupler, second signal distribution means), 11 input Output terminal (first input / output terminal), 12 Input / output terminal (second input / output terminal), 13 Input / output terminal (third input / output terminal), 14 Input / output terminal, 21 Input / output terminal (fourth Input / output terminal), 22 input / output terminal (fifth input / output terminal), 23 input / output terminal (sixth input / output terminal), 24 input / output terminal, 31 transmission line, 32 parallel resonant circuit, 32a capacitor, 32b inductor 33, 34 Transmission line, 35 Series resonant circuit, 35a inductors, 35b capacitor 36 short stub, 37 meander line, 41 terminating resistor, 43 GND conductor,

Abstract

L'invention porte sur un circuit de découplage qui est configuré de telle sorte que des taux de distribution de signal dans des circuits de distribution (1, 2) et une quantité de réglage d'amplitude, dans un circuit de réglage de phase d'amplitude (5), sont réglés de telle sorte que des amplitudes de couplage dans une route A et une route B deviennent égales et une quantité de réglage de phase dans le circuit de réglage de phase d'amplitude (5) est réglée de telle sorte que des phases de couplage dans la route A et la route B deviennent opposées l'une à l'autre. Par conséquent, même si l'amplitude de couplage et la phase de couplage entre des antennes changent fortement dans une bande de fréquences utilisable, le couplage entre une borne d'entrée/sortie (11) et une borne d'entrée/sortie (21) peut être réduit sur la totalité de la bande de fréquences utilisable.
PCT/JP2013/077792 2013-10-11 2013-10-11 Circuit de découplage WO2015052838A1 (fr)

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JP2015541406A JPWO2015052838A1 (ja) 2013-10-11 2013-10-11 減結合回路
PCT/JP2013/077792 WO2015052838A1 (fr) 2013-10-11 2013-10-11 Circuit de découplage

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PCT/JP2013/077792 WO2015052838A1 (fr) 2013-10-11 2013-10-11 Circuit de découplage

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WO2015052838A1 true WO2015052838A1 (fr) 2015-04-16

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Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN105655709A (zh) * 2016-01-29 2016-06-08 深圳微迎智科技有限公司 干扰消除电路和天线阵列
JP6272584B1 (ja) * 2017-02-08 2018-01-31 三菱電機株式会社 減結合回路
CN112997359A (zh) * 2018-12-17 2021-06-18 华为技术有限公司 一种天线阵列电磁去耦的方法及结构
CN113659337A (zh) * 2020-05-12 2021-11-16 西安电子科技大学 天线装置、电子设备和用于天线装置的去耦方法
CN113764888A (zh) * 2021-08-09 2021-12-07 荣耀终端有限公司 天线组合系统及终端设备

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CN105655709A (zh) * 2016-01-29 2016-06-08 深圳微迎智科技有限公司 干扰消除电路和天线阵列
JP6272584B1 (ja) * 2017-02-08 2018-01-31 三菱電機株式会社 減結合回路
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CN112997359A (zh) * 2018-12-17 2021-06-18 华为技术有限公司 一种天线阵列电磁去耦的方法及结构
CN112997359B (zh) * 2018-12-17 2022-07-26 华为技术有限公司 一种天线阵列去耦结构及天线阵列
CN113659337A (zh) * 2020-05-12 2021-11-16 西安电子科技大学 天线装置、电子设备和用于天线装置的去耦方法
WO2021227808A1 (fr) * 2020-05-12 2021-11-18 西安电子科技大学 Appareil d'antenne, dispositif électronique et procédé de découplage pour appareil d'antenne
CN113764888A (zh) * 2021-08-09 2021-12-07 荣耀终端有限公司 天线组合系统及终端设备

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