WO2008087143A1 - Procédé et dispositif de traitement de signaux - Google Patents

Procédé et dispositif de traitement de signaux Download PDF

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Publication number
WO2008087143A1
WO2008087143A1 PCT/EP2008/050405 EP2008050405W WO2008087143A1 WO 2008087143 A1 WO2008087143 A1 WO 2008087143A1 EP 2008050405 W EP2008050405 W EP 2008050405W WO 2008087143 A1 WO2008087143 A1 WO 2008087143A1
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WO
WIPO (PCT)
Prior art keywords
signal
frequency
radio
signals
intermediate frequency
Prior art date
Application number
PCT/EP2008/050405
Other languages
German (de)
English (en)
Inventor
Bernd Burchardt
Original Assignee
Cinterion Wireless Modules Gmbh
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Cinterion Wireless Modules Gmbh filed Critical Cinterion Wireless Modules Gmbh
Priority to EP08707903A priority Critical patent/EP2127104A1/fr
Publication of WO2008087143A1 publication Critical patent/WO2008087143A1/fr

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06—Receivers
    • H04B1/16—Circuits
    • H04B1/26—Circuits for superheterodyne receivers
    • H04B1/28—Circuits for superheterodyne receivers the receiver comprising at least one semiconductor device having three or more electrodes

Definitions

  • the invention relates to a method and apparatus for signal processing of simultaneously on at least two different frequencies Hochfrequenzskafre ⁇ radio signals received.
  • a conventional radio receiver known as a superheterodyne receiver which finds application in mobile radio technology, filters and amplifies the first through an antenna are received, ⁇ genes modulated high-frequency radio signal. Then, in a mixer, the received high-frequency radio signal is mixed with the signal of a local oscillator.
  • the local oscillator ⁇ frequency is set according to a fixed rule. With the so-called "Direct Conversion Receiver", the mixing or local oscillator frequency is set to the expected or fixed reception frequency.
  • the setting of the local oscillator frequency is frequency-offset in receivers with an intermediate frequency, so that the desired intermediate frequency results from the mixing process.
  • the frequency of reception is to be understood as the frequency range which a component of the radio receiver transmits or to which the component is tuned.
  • the output signal of the mixer is the mixed product of radio signal and local oscillator signal.
  • intermediate frequency The aforementioned difference frequencies from control and reverse are referred to below as intermediate frequency. It is important in this context that the information or modulation impressed on the radio-frequency radio signal is also contained in the intermediate-frequency signal.
  • the output signal of the mixer is in turn further filtered (intermediate frequency bandpass filter) and amplified.
  • the actual message content of the radio signal is separated from the carrier signal in a demodulator.
  • the message content for to the delegation ⁇ supply is embedded in a frame structure of the data stream, data elements for error correction in the transfer direction (forward error correction / forward error correction FEC) or to generate a repeat request provided, with opening extended / end labeling of certain data groups or contains synchronization indicator also known as Midambeln.
  • Sophisticated algorithms resort to the recovery of the message content during the separation of the payload data from the data stream within the program flow in the digital signal processor.
  • These described corrective measures or synchronization information depend on the radio standard used and are specified in a specification for the respective transmission standard.
  • multiple receiver trains consisting of the previously mentioned modules for each receiver path are set up today and multiple analog / digital converters with corresponding algorithms running side by side in the digital signal processor are processed further.
  • these receive paths formed in parallel can also be combined at specific points via a multiplexer and further processed and evaluated in a sequential method with temporal resolution.
  • the object is related to the method according to the invention by a method for signal processing of a first radio signal, which is formed by modulation of a first signal, wel ⁇ ches a previously known first parameter to a first high frequency carrier, and a second radio signal, which by modulating a second signal which comprises a previously known second parameter is formed on a second high-frequency carrier , wherein both radio signals have a different Hochfrequenzong ⁇ frequency and are received simultaneously, with the aid of a common local oscillator both Funkksigna- Ie be converted into a common intermediate frequency and first and second signal components in the intermediate frequency at least partially overlap and thus bil ⁇ a signal, wherein by a subsequent signal evaluation using the previously known first and second parameters in the sum signal two of each other un dependent partial signals are obtained, which are then fed to a further separate signal processing.
  • the inventive method and the device according to the invention is with less circuit complexity in a simultaneous reception of several high-frequency
  • Radio signals to be received increases the total data rate, that is, it can be dispensed with separate reception paths in the device respect ⁇ Lich of the two received radio signals, thereby reducing the construction cost of the apparatus.
  • the first and second preparatory known parameters respectively to a predetermined bit pattern in a bit stream ⁇ nercher are traceable.
  • the method for signal processing in radio receivers operating in accordance with agreed radio standards can be applied by using training, adjustment, start or stop sequences contained in bursts as parameters.
  • the first and the second previously known parameter is a previously known phase, frequency, amplitude, quadrature amplitude and / or spread spectrum modulation.
  • the signal evaluation is achieved by different sampling rates. This can the method known to those skilled in the digitization and
  • the mixing process with the first and second radio signal is mapped into a common rule Zvi ⁇ frequency takes place by means of a harmonic mixer.
  • the intermediate frequency initially achieved is again subjected to a frequency conversion before a signal evaluation. This allows gradual, even when more than two radio signals are received, all received radio signals to a plurality of frequency conversions are superimposed in the intermediate frequency, wherein the sum signal formed in the intermediate frequency, then a signal is subjected ⁇ evaluation.
  • FIG. 1 shows an inventive device FE and the inventive method for signal processing, with which the data rate to be received is increased.
  • the OF INVENTION ⁇ to the invention method of radio signals received in the device FE be processed simultaneously on at least two radio frequency carrier frequencies.
  • the device FE comprises the following essential components of the invention: An antenna A, to which the high-frequency received signals are fed, a high-frequency filter and amplifier HFFUV connected to the antenna A.
  • a mixer M connected to the high frequency filter and amplifier HFFUV, which in turn is connected to a local oscillator LO.
  • An intermediate frequency filter and amplifier ZFFUV connected to the mixer M.
  • An evaluation unit AE comprising the following components: An analog / digital converter ADC connected to the intermediate frequency filter and amplifier ZFFUV and a digital signal processor DSP connected to the analog / digital converter ADC.
  • a first radio signal FS1 is received via the antenna A and supplied to the high-frequency filter and amplifier HFFUV.
  • the first radio signal is a FSL from a transmitter (not constitute ⁇ provided) derived first signal Sl, which comprises a post ⁇ directed content, aeration generally is characterized as a useful signal, wherein the first signal Sl in the transmitter to a ERS radio frequency carrier HFT1 is modulated.
  • the first radio signal FS1 comprises a first parameter P1 previously known to the device FE, whose evaluation in the device FE will be described below.
  • the first radio signal fSL is represented by a dotted rectangle are maintained as components of the first radio frequency carrier HfTL, the first signal Sl and the prior art first parameter Pl ent ⁇ in what is represented by the clamp.
  • a second radio signal FS2 is simultaneously with the first
  • the second radio signal FS2 is a from a transmitter (not Darge ⁇ asserted) derived second signal S2, which also includes a message content, generally referred to as the useful signal, the second signal S2 is modulated in the transmitter on a second RF carrier HFT2, whose high-frequency carrier frequency however, different from that of the first radio frequency carrier HFT1.
  • the second radio signal FS2 comprises a second parameter P2, previously known to the device FE, whose evaluation in the device FE will be described below.
  • the second radio signal FS2 is represented by a dashed rectangle in which the second radio frequency carrier HFT2, the second signal S2 and the previously known second parameter P2 are contained as components, which is represented by the bracket. Since the first and the second radio signal FSL, FS2 have different Frequen ⁇ zen, they do not influence each other as they pass through high frequency filter and amplifier HFFUV. This is represented by the selected representation with non-overlapping dotted and dashed rectangles. Depending on the frequency spacing of the radio signals FS1, FS2, it may be necessary to provide separate high-frequency filters and amplifiers for the respective radio signals.
  • both radio signals FSL, FS2 the mixer M will now be supplied and converted to another Fre ⁇ frequency range by means of the local oscillator signal.
  • the oscillator frequency of the local oscillator LO is chosen such that the mixing results of different input frequencies do not overlap, the erfindungsommetli ⁇ che point that the oscillator frequency of the local oscillator LO is chosen exactly so that the mixing results from the radio signals FSL and FS2 at least partially überla ⁇ like.
  • This choice of local oscillator frequency is contrary to the prior art in which signal overlays are avoided. In the context of the invention, however, this choice is deliberately made in order to reduce bandwidth in the intermediate frequency, or to ⁇ come out without multiple trained receiver trains and at the same time to increase the total transmission data rate.
  • the local oscillator LO is set exactly in the middle between the two radio signals FSL, FS2.
  • both conversion results would then fall by the local oscillator LO and mixers M in a fully overlapping Swissfre acid sequence in which one from the control location and the two ⁇ te comes from the inverted position.
  • the respective data streams could be separated again by the band differentiations, since the radio signal originating from the Kehrlage is konju ⁇ giert complex present in the intermediate frequency.
  • the combination of the high-frequency carrier frequencies of the first and second radio signals FS1, FS2 with the Oscilloscope generates Gate frequency of the local oscillator LO sum and Differenzfre ⁇ frequencies.
  • the high-frequency carrier frequency of the first radio signal FSl 955.6 MHz and that of the second Funkksig ⁇ nals FS2 955.0 MHz amount.
  • the radio signal definitions of the GSM radio technology are borrowed.
  • Each radio signal FS1, FS2 has a signal band width of 0.2 MHz.
  • the oscillator frequency of the local oscillator LO is selected to be 955.35 MHz.
  • a first difference frequency of 0.25 MHz is now formed.
  • a second difference frequency of -0.35 MHz now arises. Since there are no non-ferrous gativen frequencies, the minus sign is deleted and thus taken into account that the obtained frequenzkonver ⁇ formatted signal after the conversion is complex conjugate before ⁇ .
  • the receivers in the case of further mixed products are designed in such a way that no signal power is taken off at these mixing frequencies.
  • the first signal component SAl is again drawn as dotted rectangle and the second signal component SA2 as ge ⁇ stricheltes rectangle.
  • the two signal components SA1, SA2 overlap, which is represented by a dashed / dotted rectangle in FIG.
  • the sum signal SS which is symbolized in the upper part by the gepunk ⁇ chain line, in the middle part by the dashed polka dot ⁇ th line and in the lower part by the dashed line, further the known first and second parameters comprises the message content Pl, P2, what is shown in the figure 1 by the bracket in the label.
  • the sum signal SS is then fed to the evaluation unit AE.
  • the evaluation unit AE then two independent sub-signals TSl, TS2 can be obtained again based on the previously known first and second parameters Pl, P2, which are then fed to a further separate signal processing.
  • a digital arithmetic unit such as the digital signal processor DSP
  • further amplifiers or filters are located within the intermediate frequency stages, which process the signal before conversion.
  • Procedures and algorithms run in the digital signal processor DSP and, knowing the previously known parameters P1 and P2, recover the respective transmitted data streams from the sampled values.
  • the signal components SA1 and SA2 interfere with their center frequencies at 0.25 MHz and 0.35 MHz. Since the radio signals fsl and FS2 are attached to a fixed channel spacing according to the used radio standard, and the oscillation frequency of the local oscillator LO within the radio receiver FE is known, the Mittenfrequen ⁇ zen of the signal components SAl and calculated SA2 can.
  • the separation into two independent sub-signals TS1, TS2 can be carried out in addition to the previously mentioned phase and amplitude modulation also for all other known modulation methods.
  • the quadrature amplitude, frequency and / or spread spectrum modulation are additionally mentioned here.
  • the partially overlapping partial signals TS1, TS2 are supplied to the analog / digital converter ADC.
  • the separation take place (not shown) due to different Ab ⁇ gating rates.
  • Partial signals TS1, TS2 due to existing in the supplied overlapping ⁇ penden signal predetermined bit patterns, which represent the previously known first and second parameters Pl, P2.
  • the type of separation is particularly advantageously applicable in standardized mobile radio systems, such as GSM, in which fixed bit patterns (training sequences, midambles), eg for error detection or synchronization, are present within a signal sequence (burst). Based on this specified bit pattern the superimposed signal can be decomposed in TS2 comprises two independent partial signals TSI, what is shown in Fi gur ⁇ 1 by a dotted rectangle separated from the dashed rectangle. Since the previously known first and second parameters P1, P2 have already been evaluated, they are no longer shown in FIG. 1 in the digital signal processor DSP.
  • both these known parameters Pl, P2 are available to the entire system of the radio receiver FE still available and can be used later again for a further stabilization of the process or amaschinesop ⁇ optimization.
  • DSP digital signal processor
  • Kom ⁇ components of the apparatus FE align themselves, for example via a bus system to, in which the partial signals TSl, TS2 are supplied to a further separate signal processing, for example, is performed there, the conversion in audio ⁇ or image data.
  • the inventive method and the inventive ago ⁇ direction FE are also applicable if more than the initially described two radio signals FSL received FS2 simultaneously. If, for example, four radio signals are received simultaneously on four different radio frequency carriers, the oscillator frequency of the local oscillator LO can be selected such that it lies between the second highest radio frequency carrier and the third highest radio frequency carrier relative to the height of the radio frequency carrier. In this choice of oscillator frequency arise in the intermediate frequency sum signals in which superimpose the two of the local oscillator frequency ⁇ closer radio signals in the intermediate frequency to a first combination of signal components (first sum signal) and the two of the local oscillator frequency farther away radio signals are also in the Intermediate frequency superimpose to a second combination of signal components (second sum signal).
  • the invention is not limited to the specific embodiment, but includes other not explicitly evidenced ⁇ te modifications, as long as the core of the invention, namely to use a method of frequency conversion, in which at least two radio frequency carrier frequencies received radio signals converted into an overlapping intermediate frequency be and then separated in the evaluation unit AE in different data streams.
  • This selection causes the intermediate frequency in a lower band width is occupied ⁇ compared to a choice of non-overlapping frequency components between or the sum of bandwidths operating in parallel receiving systems.
  • the signal components SAI, SA2 in the intermediate frequency can therefore already be the result of frequency conversion of a harmonious reception mixer which converts the radio signals FSL, FS2 over different harmonic a local oscillator signal ⁇ .
  • frequency transformations can also take place in other frequency ranges.
  • the intermediate frequency can be scanned directly or subharmonically or mixed again. It would also be possible to carry out the evaluation via a 6-port receiver.
  • the named components may have different names or be grouped into larger components. In particular, the transfer to software algorithms and their evaluation should be included in the invention.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Superheterodyne Receivers (AREA)

Abstract

L'invention concerne un procédé et un dispositif (FE) destiné au traitement de signaux d'un premier signal radio (FS1), qui est formé par modulation d'un premier signal (S1), comprenant un premier paramètre connu (P1), sur une première porteuse haute fréquence (HFT1), et d'un second signal radio (FS2), qui est formé par modulation d'un second signal (S2), comprenant un second paramètre connu (P2), sur une seconde porteuse haute fréquence (HFT2). Les deux signaux radio (FS1, FS2) présentent une fréquence porteuse haute fréquence différente et sont reçus simultanément, les deux signaux radio (FS1, FS2) étant convertis en une fréquence intermédiaire commune (ZF) au moyen d'un oscillateur local commun (LO) et des première et seconde composantes de signal (SA1, SA2) se superposant au moins partiellement dans la fréquence intermédiaire (ZF) et formant ainsi un signal cumulé (SS). Grâce à une évaluation de signal ultérieure à l'aide des premier et second paramètres connus (P1, P2) dans le signal cumulé (SS), deux signaux partiels indépendants l'un de l'autre (TS1, TS2) sont obtenus, lesquels sont transmis ensuite à un autre traitement de signaux séparé. Grâce à ce procédé ou ce système (FE), le débit de transfert de données à recevoir peut être augmenté avec de plus faibles besoins en termes de technique de montage et ainsi une optimisation des coûts.
PCT/EP2008/050405 2007-01-19 2008-01-15 Procédé et dispositif de traitement de signaux WO2008087143A1 (fr)

Priority Applications (1)

Application Number Priority Date Filing Date Title
EP08707903A EP2127104A1 (fr) 2007-01-19 2008-01-15 Procédé et dispositif de traitement de signaux

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102007003629 2007-01-19
DE102007003629.0 2007-01-19

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WO2008087143A1 true WO2008087143A1 (fr) 2008-07-24

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WO (1) WO2008087143A1 (fr)

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO1997005705A1 (fr) * 1995-07-26 1997-02-13 Telefonaktiebolaget Lm Ericsson (Publ) Recepteur superheterodine unique en bande a pour service telephonique mobile evolue
DE19838244A1 (de) * 1998-08-22 2000-02-24 Daimler Chrysler Ag Verfahren zum Empfang verschiedenartiger Funkstandards
WO2002037706A1 (fr) * 2000-11-03 2002-05-10 Aryya Communications, Inc. Systeme emetteur-recepteur radio sans fil a bande large multi-protocole
US20060045126A1 (en) * 2004-08-30 2006-03-02 Interdigital Technology Corporation Method and apparatus for adaptively selecting sampling frequency for analog-to-digital conversion
US20060141969A1 (en) * 2000-12-07 2006-06-29 Dubash Noshir B L1/L2 GPS receiver

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO1997005705A1 (fr) * 1995-07-26 1997-02-13 Telefonaktiebolaget Lm Ericsson (Publ) Recepteur superheterodine unique en bande a pour service telephonique mobile evolue
DE19838244A1 (de) * 1998-08-22 2000-02-24 Daimler Chrysler Ag Verfahren zum Empfang verschiedenartiger Funkstandards
WO2002037706A1 (fr) * 2000-11-03 2002-05-10 Aryya Communications, Inc. Systeme emetteur-recepteur radio sans fil a bande large multi-protocole
US20060141969A1 (en) * 2000-12-07 2006-06-29 Dubash Noshir B L1/L2 GPS receiver
US20060045126A1 (en) * 2004-08-30 2006-03-02 Interdigital Technology Corporation Method and apparatus for adaptively selecting sampling frequency for analog-to-digital conversion

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Publication number Publication date
EP2127104A1 (fr) 2009-12-02

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