WO2002063756A1 - Appareil de commutation electrique et regulateur electronique - Google Patents

Appareil de commutation electrique et regulateur electronique Download PDF

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Publication number
WO2002063756A1
WO2002063756A1 PCT/KR2002/000150 KR0200150W WO02063756A1 WO 2002063756 A1 WO2002063756 A1 WO 2002063756A1 KR 0200150 W KR0200150 W KR 0200150W WO 02063756 A1 WO02063756 A1 WO 02063756A1
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WO
WIPO (PCT)
Prior art keywords
signal
power
switching
unit
switch
Prior art date
Application number
PCT/KR2002/000150
Other languages
English (en)
Inventor
Joon-Ho Park
Original Assignee
Joon-Ho Park
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Joon-Ho Park filed Critical Joon-Ho Park
Publication of WO2002063756A1 publication Critical patent/WO2002063756A1/fr

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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
    • H05B41/285—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2851—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
    • H05B41/2856—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against internal abnormal circuit conditions
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J1/00—Circuit arrangements for dc mains or dc distribution networks
    • H02J1/14—Balancing the load in a network
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B20/00—Energy efficient lighting technologies, e.g. halogen lamps or gas discharge lamps

Definitions

  • the present invention relates to an electric switch apparatus, and more particularly, to an electric switch apparatus using a switching mode power and to an electronic ballast for a discharge lamp using the electric switch apparatus.
  • Electric switches are frequently items in many electrical systems. They make and break connections in an electrical circuit, such as a direct current (DC) power source, an electric motor, a heating element, etc..
  • DC direct current
  • a problem that often occurs with electrical switches is the surge current generated when the electric products are turned on and off, this is, when a switching operation is performed. Current consumption in this case is considerably large, and without adequate protection it may temporarily or permanently damage the products.
  • the electric switching device includes a switching controller for turning on or off a switching element at a predetermined frequency according to a switching signal, a transformer to which an input power is applied, for controlling the input power according to the on or off state of the switching element and for chopping the input power into a square wave frequency signal, a switch control output unit for rectifying the square wave signal and outputting a DC power, and a switch unit, which turns on or off according to the DC power supplied from the switch control output unit.
  • the switch unit is comprised of a transistor, and the transistor is turned on or off according to a DC power level supplied to the transistor from the switch control output unit, thereby performing a switching operation.
  • the electronic ballast includes at least one discharge lamp, which is lighted using a resonance circuit comprising an inductor and a capacitor, a power supply portion for supplying a power for lighting the discharge lamp by applying a power signal and a square wave signal with a predetermined frequency to the discharge lamp, and a switch unit for turning on or off the discharge lamp by controlling the square wave signal applied to the discharge lamp.
  • the switch unit forms an attenuation filter by the capacitor when the switch unit is turned on and an inductor included in the discharge lamp, thereby attenuating the level of the square wave signal applied to the discharge lamp.
  • FIG. 1A illustrates the structure of a switch controller using a switching mode power supply (SMPS);
  • SMPS switching mode power supply
  • FIG. 1 B is a circuit diagram of the switch controller shown in FIG. 1A;
  • FIG. 1 C is an example illustrating the structure of a switch control output unit
  • FIGS. 1 D through 1 E are another examples illustrating the structure of switches
  • FIG. 2A is an example in which a plurality of switches are connected to an output terminal of the switch control output unit
  • FIG. 2B is an example in which a plurality of switch control output units and a plurality of switches are included;
  • FIG. 3 is an example illustrating the structure of a pulse width modulation (PWM) controller shown in FIG. 1 B;
  • PWM pulse width modulation
  • FIG. 4 is an example in which the switch controller of FIG. 1 is applied to an electronic ballast;
  • FIG. 5 is a detailed circuit diagram corresponding to the electronic ballast of FIG. 4;
  • FIG. 6 illustrates a system for turning on and off a fluorescent lamp in case that a plurality of fluorescent lamps are divided into several groups;
  • FIG. 7 is a graph illustrating a signal attenuation effect due to an
  • FIG. 8A is a detailed circuit diagram of each module included in the upper output unit shown in FIG. 5;
  • FIG. 8B is a detailed circuit diagram of each module included in the lower output unit shown in FIG. 5. Best mode for carrying out the Invention
  • FIG. 1A illustrates the structure of a switch controller using a switching mode power supply (SMPS).
  • a switching controller 111 outputs a switching signal SW 0Ut having a predetermined frequency, and a switching unit 114 disconnects the current flowing through a primary winding of a transformer 115 according to the switching signal SW 0U t of the switching controller 111 to chop an input DC power ⁇ into a square wave signal having a high frequency.
  • the square wave signal is applied to a switch control output unit 117 via a drive transformer 115, and thus the size of the square wave signal is reduced to a predetermined value according to the winding ratio in the coils.
  • a current feedback unit 113 detects the current flowing through the switching unit 114 and feeds back the current into the switch controller 111.
  • the switch control output unit 117 generates a DC voltage according to a signal transmitted from the transformer 115 and turns on and off a switch 119 according to the state of the DC voltage.
  • FIG. 1 B is a circuit diagram of the switch controller shown in FIG.
  • An input voltage ⁇ is applied to a primary winding of a power transformer T,.
  • a filter 10, for eliminating noise from the input voltage V-i is included at a power input terminal and it may be formed of a low pass filter having a pi ( ⁇ ) shape in which capacitors C F ⁇ and C F2 are connected to an inductor L F .
  • the PWM controller 11 generates a switching signal SW 0Ut having a predetermined frequency and applies the switching signal SW 0Ut to a gate terminal of a switching transistor Qi.
  • the switching transistor Qi acts as a switching element,, and turns on and/or off operation according to the switching signal SW 0U t output from the PWM controller 11.
  • a primary winding N p of the power transformer Ti is connected between the input DC power ⁇ and the switching element Qi, and a square wave power signal having a high frequency is supplied to the primary winding N p of the power transformer T-i by turning on and/or off the switching element Q .
  • the power transformer l transmits a power supplied to the primary winding N p of the power transformer Ti to a secondary winding.
  • a current detection unit 13 senses the current flowing through the primary winding N p of the power transformer Ti by turning on and/or off the switching element (transistor Q ⁇ and feeds back the current into the PWM controller 11.
  • a voltage signal is applied to a FB terminal of the PWM controller 11 , and a voltage induced by a feedback winding N FB of the power transformer T . is distributed by the resistors R a and R , and the distributed voltage is applied to the FB terminal of the PWM controller 11.
  • the PWM controller 11 adjusts a switching signal SW 0Ut according to the degree of the variation.
  • the PWM controller 11 controls the on/off duration of the switching signal SW 0Ut according to a voltage level in which input current which varies according to the variation in load or the input voltage V . is detected by the current detection unit 13 and that is input into a SENSE terminal, and according to a voltage level input into the FB terminal, so that the current amount flowing through the primary winding of the power transformer Ti is controlled.
  • the PWM controller 11 includes a shut down terminal S/D and a reset terminal RST so as to turn on and/or off the operation of the PWM controller 11.
  • a logic low signal is applied to the shut down terminal S/D
  • a power applied to the PWM controller 11 is cut off, and in case that a logic high signal is applied to the reset terminal RST, the output of the PWM controller 11 is reset (see FIG. 3).
  • a signal may be applied to the shut down terminal S/D or the reset terminal RST using a mechanical or an electric switch SW ⁇ , and a remote operation may be performed using an optical transmitter 14a and an optical receiver 14b.
  • the optical transmitter 14a emits an optical signal (i.e., infrared signal) having a predetermined frequency, and the optical receiver 14b receives the optical signal so that a logic high or logic low signal is applied t the shut down terminal S/D or the reset terminal RST.
  • a remote control used in a TV or an audio system may be used as the optical transmitter 14a. In this case, an unused predetermined key of the remote control may be used for the PWM controller 11.
  • a switch control output unit 17a for controlling a switch 19a is connected to a secondary winding of the power transformer Ti.
  • the switch control output unit 17a includes a rectifier for converting an AC power into a DC power, and the switch 19a is turned on and off according to the output signal of the rectifier.
  • a diode may be used as a rectifying element, and in case that output current is high, it is preferable that a MOSFET transistor (RDS(on) is less than 0.02 ohm) is used, thereby minimizing the power loss.
  • RDS(on) is less than 0.02 ohm
  • the switch control output unit 17a includes a diode D s , a capacitor Co for ripple elimination, RC snubber circuits R s and C s , and an output load resistor R .
  • FIG. 1 B is an example in which a diode D s is used as a rectifying element.
  • FIG. 1C is another example illustrating the structure of a switch control output unit, in which a transistor is used as a rectifying element.
  • RC snubber circuits shown in FIGS. 1B and 1C will be described below.
  • a resonance circuit is formed by the leakage inductance of a primary coil L p of the power transformer T-, for high frequency and by the junction capacitance of a rectifying diode.
  • a transient overvoltage ringing phenomenon occurs.
  • the ringing may cause noise during a turn off duration and may have a too large amplitude and thereby, destroy the diode.
  • the RC snubber circuits suppress the ringing to have a stable amplitude.
  • the RC snubber circuit may be connected to both ends of the rectifying diode or to both ends of a secondary winding of the power transformer Ti.
  • a transistor Q s used as a rectifying element is a field effect transistor (FET), converts an AC signal induced in the secondary winding of the power transformer T.
  • FET field effect transistor
  • a filtering capacitor C 0 which is an element for suppressing ripple current, smoothes the signal ripple in order to generate a predetermined output voltage V out .
  • An RC circuit comprised of a resistor R S ⁇ and a capacitor C S ⁇ , is a first snubber circuit for preventing ringing due to the leakage inductance Lr of the primary coil L p of the power transformer Ti and the gate input capacitance C G s of the transistor Q s .
  • Another RC circuit comprised of a resistor R S2 and a capacitor Cs2 is a second snubber circuit for preventing ringing due to the leakage inductance of the primary coil L p of the power transformer Ti and the capacitance C oss between a drain and a source of the transistor Q s .
  • the switch 19a is connected to an output port of the switch control output unit 17a.
  • FIG. 1 B shows an example of a switch in which a mechanical switch is used
  • FIG. 1 D presents an example of a switch in which an optical switch is used
  • FIG. 1 E displays an example of a switch in which a transistor is used.
  • the mechanical switch 19a includes an input terminal 192, an output terminal 193, a switch contact 194, and a coil 191 , and connects the input terminal 192 to the output terminal 193 by the mechanical action of the switch contact 194 in case that a voltage is applied to the coil 191.
  • An optical switch 19b that includes a light emitting element 195 and an optical transistor 196, emits light, and turns on an optical transistor 196 in case that a voltage is applied to the light emitting element 195.
  • an output voltage of the switch control output unit 17a is applied between the gate terminal and the source terminal of a FET transistor 198, so that the FET transistor 198 is turned on. That is, the transistor is turned on and/or off by adjusting a voltage between gate and source of the transistor, thereby increasing the switching speed, and considerably reducing the power loss due to current flowing through the transistor.
  • the switching transistor Qi is turned on and/or off in response to the square wave signal SW 0Ut generated by the PWM controller 11.
  • the switching transistor Qi When the switching transistor Qi is turned on, current is charged in the primary winding of the power transformer T 1 f and when the switching transistor Qi is turned off, the current charged in the primary winding of the power transformer Ti is transmitted to the secondary winding of the power transformer T-i, thereby a voltage is induced in both ends of the secondary winding of the power transformer T. according to a winding ratio of the power transformer Ti.
  • the current detection unit 13 is connected between the source terminal of the switching transistor Qi and a minus terminal -Vi of the input voltage V 1( so that a signal generated according to the current flowing when the switching transistor Q1 is turned on, is fed back into the PWM controller 11.
  • the current detection unit 13 senses a variation in the input current according to a variation in current due to a variation of the input voltage Vi or according to a variation in the output load, and feeds back the variation into the PWM controller 11.
  • the PWM controller 11 controls a switching operation in response to a sensing signal SENSE.
  • the current detection unit 13 senses a variation in current l pp according to a variation in the input voltage V-i or a variation in an output voltage, converts the variation into a voltage signal, and feeds the voltage signal into the PWM controller 11.
  • the PWM controller 11 adjusts a pulse duration having a positive phase of the switching signal SW out by reflecting the variation in the input voltage Vi or the variation in an output voltage, so that the output voltage is constant. If the current l pp is increased, a current sensing voltage that is detected by the current detection unit 13 and is fed back into the PWM controller 11 is increased.
  • the PWM controller 11 adjusts the pulse duration of the switching signal SW 0Ut on the basis of the current sensing voltage, to be controlled in a direction in which the current l pp is reduced.
  • the switching transistor Q ⁇ is turned on, current is induced in a secondary winding of a current-coupling transformer T 2 by current flowing through a primary winding of the current-coupling transformer T 2 .
  • a resistor R-i converts the current induced in the current-coupling transformer T 2 into a voltage signal, and a voltage level applied to a sensing terminal SENSE is determined by adjusting the resistance in a variable resistor R 2 .
  • Capacitors C 2 and C 3 eliminate ripple or noise, and a diode D 2 rectifies a detected square wave signal into a DC signal.
  • the ratio of the primary winding to the secondary winding of the current-coupling transformer T 2 is 1 : 50 ⁇ 200.
  • the primary winding of the transformer T 2 is a single turn coil, and the secondary winding is a 100 turn coil.
  • the core material of the transformer T 2 is the same as that of the transformer Ti.
  • a voltage V cc applied to a feedback winding N FB of the primary winding of the power transformer T-i is distributed by the resistors R a and R b and is applied to the FB terminal of the PWM controller 11.
  • the PWM controller 11 generates a switching signal for turning on and/or off the switching element Qi according to the sensing voltage SENSE generated by the input current and according to the voltage input into the FB terminal. The detailed structure thereof will be described with reference to FIG. 3.
  • a self-bias circuit 15 supplies an operating power to an output unit of the switching signal SW 0U t in the PWM controller 11.
  • a voltage induced by a feedback winding N FB (a polarity mark (dot; start point of winding) is reversed from that of a primary winding N p ) of the primary side of the power transformer Ti is applied to a V cc terminal of the PWM controller 11 via a diode D ⁇ .
  • a capacitor Ci serves to eliminate the ripple.
  • supplies a power to an element included in the PWM controller 11 other than the switching output unit.
  • FIG. 2A is an example in which a plurality of switch control output units 251 , 252, . . . , 25n are included in the secondary winding of the power transformer Ti shown in FIG. 1 B, and switches 271 , 272, . . .
  • the present invention is useful in case that large current flows through a signal line that should be turned on and/or off by a switch.
  • a transistor is used as a switching element
  • the total current flowing through the signal line flows as much as 1/n by each transistor, thereby the total power loss can be reduced compared with a case where one transistor is used as a switching element.
  • All of the plurality of switch control output units 251 , 252, . . . , 25n may be connected to the secondary winding of one transformer T1 , or an extra transformer may be included in each switch control output unit or several switch control output units.
  • FIG. 3 is an example of the structure of the PWM controller shown in FIG. 1B, and illustrates a current-mode controlling method.
  • the voltage V cc that is induced by the feedback winding N FB of the primary side of the power transformer Ti supplies power to an amplifier 35 for outputting the switching signal SW 0Ut , and operating power is supplied to circuits such as a clock generator 33, a flip-flop 34, an error amplifier 31 , and a comparator 32, from the input voltage Vi that is applied through a regulator 37.
  • the error amplifier 31 compares the output signal +FB with the reference voltage V ref to generate an error signal that is input into the comparator 32.
  • the sensing signal SENSE which is a voltage signal converted from the sensed output current of the inverter, is input into the comparator 32.
  • the comparator 32 compares the sensing signal SENSE due to the peak switching current with the error signal related to the output signal and inputs the comparison result signal SENSE into the RS flip-flop (latch) 34.
  • the clock generator 33 generates a clock signal, which is a square wave signal corresponding to the switching frequency f s , and the RS flip-flop 34 receives the output of the comparator 32 and the clock signal and generates the switching signal SW 0Ut for turning on and off a switching element.
  • the switching element (transistor) that is connected to the amplifier 35 is turned on and off by the switching signal SWout according to its logic level.
  • a main 'output voltage +FB that is fed back from the final output port is compared with the reference voltage V ref by the error amplifier 31 , and the current feedback signal SENSE is compared with a reference voltage (1.2V) by the comparator 32, and the comparison result is input into the flip-flop 34.
  • the flip-flop 34 increases or decreases the phase (or width) of the clock signal that is generated in the oscillator 33 in response to an output signal of the comparator 32, that is, generates a pulse-width-modulated signal in which the duty cycle of the clock signal is varied, to generate the switching signal SW 0Ut , and thus increases or decreases the current flowing through the power transformer T . according to the variation in the input voltage and load, thereby maintaining a predetermined output voltage at the final output port.
  • the PWM controller 11 further includes the shut down terminal
  • the flip-flop 37 operates according to a logic level of a signal input into the shut down terminal S/D and the reset terminal RST, as follows.
  • all logic high signals or all logic low signals are applied to the shut down terminal S/D and the reset terminal RST, so that the output of the PWM controller 11 is turned on and/or off.
  • a switching signal is normally generated so that a switch control operation is performed, and in case that the output of the PWM controller 11 is turned off, the switching transistor Q-, is turned off (cut off) so that the entire element does not operate.
  • a logic signal may be applied to the shut down terminal S/D and to the reset terminal RST by a mechanical switch or an optical transceiver.
  • FIG. 4 is a block diagram illustrating an example in which the switch controller of FIG. 1 is applied to an electronic ballast.
  • a fluorescent lamp is a kind of a discharge lamp which is lighted using resonance circuits such as an inductor and a capacitor.
  • the DC power Mi is a DC power having a high voltage, determines an output voltage level of the inverter 44, and the other DC power V 2 is supplied to a power of the switching circuit 42.
  • a square wave signal of the inverter 44 and the high voltage power Vi are input into a load unit 45 such as a fluorescent lamp.
  • a plurality of fluorescent lamps 123, . . . , 15n each of which comprising a resonator and a lamp, are shown as an example of the load unit 45.
  • the switching circuit 42 generates a switching signal which operates at a predetermined frequency, for chopping the input DC voltage V 2 into a high frequency square wave signal.
  • the square wave signal is input into the inverter 44 via a drive transformer 43, is amplified into the high voltage power V
  • the inverter 44 generates a square wave signal having a potential level of the input DC voltage V ⁇ according to the frequency of the square wave signal generated in the switching circuit 42.
  • the power Vi and the RF signal are applied to the load unit 45, and an RF switch unit 47 short circuits or opens the RF signal supplied to the load unit 45, thereby the RF switch unit 47 serves as a main switch for simultaneously turning on or off the plurality of fluorescent lamps included in the load unit 45.
  • a switch may be connected to (+) (-) power lines with the RF signal using the circuit of FIG. 2A, so that the (+) (-) power lines are simultaneously turned on and/or off.
  • a current feedback unit 48 detects the output current of the inverter 44 and feeds back the detected output current into the switching circuit 42.
  • the switching circuit 42 compares a reference signal with the feedback signals which are fed back into the switching circuit 42 by the current feedback unit 48, adjusts the pulse phase of the switching signal and the magnitudes of the current and voltage, and thereby the voltage of the final output of the inverter 44 is maintained at a predetermined level.
  • FIG. 5 is a detailed circuit diagram corresponding to the electronic ballast of FIG. 4, where the circuit shown in FIG. 1 is applied to a switch controller 57.
  • a circuit on the left side of FIG. 5 centering on a drive transformer Ti corresponds to the switching circuit 42 of FIG. 4, while a circuit on the right side of FIG.
  • the DC powers V-, and V 2 are power outputs from the input rectifier 41.
  • the DC power is a DC power having a high voltage, which is an amplifying power ("high voltage power”) for determining a voltage level of an output signal, while the other DC power V 2 is supplied to the primary winding of the drive transformer T1 and a power of the PWM controller 21 , and is a power ("switching power") for generating a square wave signal by a switching operation.
  • a capacitor C and an inductor L F which serve as a resonator, are included in fluorescent lamps together with a lamp FL for emitting light by arc discharge.
  • the RF square wave signal that is amplified in the inverter 44 is applied to a fluorescent lamp resonance circuit.
  • Charge current flows during a high level period of the RF square wave signal due to capacitance CF I , C F2 , and C F3 of the resonance circuit, and during a low level period of the RF square wave signal, and the current that is charged in the capacitance C ⁇ , C F2 , and C F3 of the resonance circuit is discharged and flows through a minus terminal -Vi.
  • the fluorescent lamps can be lighted by small current due to the high voltage square wave signal.
  • a switching transistor Q s serves as a switching element for turning on or off in response to a switching signal SW 0Ut output form the PWM controller 51.
  • the primary winding N p of the drive transformer T- is connected between the switching power V 2 and the switching transistor Q s , and an AC power is supplied to the primary winding of the drive transformer T T by turning on and/or off the switching transistor Q s .
  • the drive transformer Ti transmits power supplied to its primary winding to its secondary winding.
  • the PWM controller 51 senses a variation in current according to a variation in output load by the current feedback unit 55, feeds back a sensing signal SENSE obtained from the current feedback unit 55, and generates the switching signal SW 0Ut in consideration of the sensing signal SENSE.
  • a switching element consists of a transistor Q s that is turned on and/or off according to a logic level of the switching signal SW 0Ut of the PWM controller 51 , thereby controlling the current flowing through the primary winding N p of the power transformer T-i.
  • the current flowing through the primary winding N p of the power transformer T . is induced in the secondary winding of the power transformer Ti by turning on and/or off the switching transistor Q s , thereby a voltage is induced in both ends of the secondary winding according to a winding ratio.
  • the square wave signal that is generated by the switching transistor Q s is transmitted to the secondary winding via the power transformer T-, thereby is input into each gate terminal of FETs included in an upper output unit 53 and a lower output unit 54.
  • the FETs included in the upper output unit 53 and the lower output unit 54 are alternately turned on and/or off, thereby an input square wave signal is amplified, and the frequency of the amplified input square wave signal is substantially the same as that of the input square wave signal, and a square wave signal RF amplified to a level of the high voltage power V-i is generated.
  • the internal resistance RDS(on) has a low value (i.e., less than 0.3 ohm) so that the input gate capacitance of the transistor has also a low value (i.e., 220 pF), thereby reducing the power loss.
  • the primary winding of the power transformer Ti includes an auxiliary winding N ⁇ with a primary winding N p .
  • the auxiliary winding N ⁇ stores energy while the switching transistor Q s is turned off and returns the stored energy to an output port when the switching transistor Q s is turned on, thereby transmitting a lower portion of a square wave, that is, the energy of the low level signal, to the output port, and thus increasing an off signal level.
  • a gate signal enough to turn on transistors Q 5 , Q 6 , and Q 7 of the lower output unit 54 can be supplied to the lower portion of a square wave.
  • the primary winding N p stores energy while the switching transistor Q s is turned on, thereby transmitting the stored energy to the output when the switching transistor Q s is turned off, thereby turning on transistors Q ⁇ Q 2 , and Q 3 of the up output unit 53.
  • the primary winding N p and the auxiliary winding N ⁇ are wound with opposite polarity, and an ultra fast switching diode is used as the diode Di.
  • the diode Di is interposed between the primary winding N p and the auxiliary winding N ⁇ , or between the auxiliary winding N ⁇ and the minus terminal -V 2 of the input voltage V 2 , to determine the direction of current while the switching transistor Q s is turned off.
  • the thickness and number of turns of the coil used in the auxiliary winding N ⁇ are substantially the same as those of the primary winding N p .
  • the number of turns of the coil used in the auxiliary winding N ⁇ of the drive transformer T-i is the same as that of the primary winding N p of the drive transformer T-i, but the primary winding N p and the auxiliary winding N ⁇ are wound with opposite polarity.
  • the charge current is supplied by the energy stored in the primary winding N p , to the gate input capacitance of the transistors Qi, Q 2 , and Q 3 of the upper output unit 53 while the switching transistor Q s is turned on.
  • a dead time is not generated in an output signal, thereby achieving high efficiency and small ripple.
  • An output voltage +FB is fed back into a PWM controller 51 , and the sensing voltage SENSE generated by the output current of the inverter 44 is input into the PWM controller 51 , and the PWM controller 51 generates a square wave pulse signal for the on and/off operation of the switching element Q s .
  • the output voltage +FB includes a rectifier (not shown) for rectifying an RF output signal to use a rectified voltage.
  • a self-bias circuit 15 supplies an operating power to an output unit of the switching signal SW 0Ut in the PWM controller 51.
  • a voltage induced by a feedback winding N FB (a polarity mark (dot; start point of winding) is reversed from that of a primary winding N p ) of the primary side of the power transformer Ti is applied to a V cc terminal of the PWM controller 51 via a diode D-i.
  • a capacitor Ci serves to eliminate the ripple.
  • a voltage V in input into the PWM controller 51 supplies a power to an element included in the PWM controller 51 other than the switching output unit, by the self-bias circuit 52.
  • the inverter 44 includes the upper output unit 53 and the lower output unit 54, and each output includes a plurality of circuit modules M1 or M2.
  • a terminal (a) of each module M1 of the upper output unit 53 (that is, a drain terminal of a transistor) is commonly connected to each other, and is further connected to the high voltage power +V-, while a terminal (b) of each module M1 of the upper output unit 53 (that is, a source terminal of a transistor) is commonly connected to each other and forms an output terminal S of the inverter 44.
  • a terminal (d) of each module M2 of the lower output unit 54 (that is, a source terminal of a transistor) is commonly connected to each other, and is further connected to the high voltage power -V
  • FIG. 8A is a detailed circuit diagram of each module included in the upper output unit shown in FIG. 5.
  • the circuit Mi further includes an RC snubber circuit and a charge discharging unit around the transistors.
  • the square wave signal transmitted from the primary winding of the power transformer T-i is transmitted to the circuit Mi, and the transistor Q 2 is turned on and/or off by the square wave signal, the level of which varies according to a winding ratio.
  • a resonance circuit is formed by the leakage inductance of a primary coil of the power transformer Ti for high frequency and by the capacitance C G s between the gate and the source of the transistor Q 2 during a turn-off period. Due to the resonance circuit, a transient overvoltage ringing phenomenon occurs. The ringing may have a too large amplitude, and thereby destroy a diode or transistor during the turn-off duration.
  • An RC circuit comprised of the resistor R s2 and the capacitor C s2 , is a snubber circuit and suppresses the ringing, and is connected in parallel with the secondary winding of the power transformer T
  • a gate resistor R g connected to a gate terminal of the transistor Q 2 is added so that a rising time of the square wave signal transmitted from the power transformer Ti is equal to a rising time of the transistor Q 2 .
  • FIG. 8B is a detailed circuit diagram of each module included in a lower output unit shown in FIG. 5.
  • the circuit M 2 further includes an RC snubber circuit and a charge discharging unit around the transistors.
  • the configuration of the circuit M 2 is substantially the same as that of the circuit Mi having only an opposite position of the polarity mark (dot) of the secondary winding to that in the circuit M ⁇ and thus a detailed description thereof will be omitted.
  • the upper output unit 53 connects in parallel the circuit Mi of FIG. 8A, disperses the current flowing through a plurality of transistors, so that the current flowing through each transistor is small. That is, a plurality of transistors Qi, Q 2 , . . . , are connected in parallel with the upper output unit of the secondary winding of the power transformer Ti (a drain of each transistor is connected to a drain of the successive transistor, and a source of each transistor is connected to a source of the successive transistor), and a charge discharging unit is additionally included in each transistor.
  • the circuit M 2 of FIG. 8B has a parallel-connected configuration.
  • the inverter 44 includes the upper output unit 53 comprising transistors turned on during a positive pulse duration of the square wave signal, and the lower output unit 54 comprising transistors turned on during a negative pulse duration of the square wave signal, and the square wave signal output from the switching unit 12 is input into the gate of each transistor, thereby reducing the current flowing through each transistor by 1/n and reducing the power loss therefrom.
  • the upper output unit 53 and the lower output unit 54 respectively, connects a plurality of the modules Mi and M 2 shown in FIGS.
  • each transistor 6A and 6B in parallel, thereby having a structure in which a plurality of transistors included in each output unit are connected in parallel.
  • the current flowing through each transistor is reduced by 1/n (where, n is the number of transistors used in each output unit), so that the power loss due to internal resistance RDS(on) between the drain and the source of a transistor is minimized, and heat generated in each transistor is minimized, and a stable operation is possible without an additional heat sink.
  • a snubber circuit comprising a diode D d , a capacitor C dl and a resistor R d is connected between the drain and the source of the transistor (see FIGS. 6A and 6B).
  • the heat loss due to the capacitance C oss between the drain and the source of the transistor is emitted from the resistor R d , thereby preventing thermal runaway of the transistor.
  • the upper output unit 53 has a structure in which for example, three modules M1 are connected in parallel, like the configuration shown in FIG. 8A. That is, the upper output unit 53 has a parallel structure in which the drain terminal (a) of the transistor included in each module is commonly connected to a drain terminal (a) of each transistor, and the source terminal (b) of the transistor included in each module is commonly connected to a source terminal (b) of each transistor.
  • the lower output unit 54 has a structure in which three modules M2 are connected in parallel, like the configuration shown in FIG. 8A. In the parallel structure, when the transistor of the output unit is turned on, the current flowing through each transistor is one third of the total current.
  • the power loss due to the on-resistance RDS of the transistor can be reduced by one third, compared with a case when only one transistor is used in the output unit.
  • three modules are included in each output unit.
  • the power loss is reduced more, thereby the system efficiency can be improved.
  • the number of modules in a device can be increased or decreased according to a power rating or a using purpose.
  • the upper and lower output units 53 and 54 of the inverter 44 can be manufactured in the shape of modules with small weight having regular rated output, and a large capacity inverter may be formed by connecting the modules in parallel.
  • the preferred embodiment of the present invention can be applied to a central control type ballast for centrally controlling electronic ballasts included in a separate fluorescent lamp, a battery charger, or a driver for a DC motor, thereby minimizing the volume of the device and improving its efficiency without including an additional heat sink in each transistor.
  • the current feedback unit 55 places a primary coil of the current-sensing transformer T 2 in the output of the inverter 44, as shown in the drawings, because the current l PD c flowing through the transistor sensitively varies according to a variation in an input voltage and/or output voltage.
  • the current feedback unit 55 includes a current-coupling transformer T 2 , and the configuration of winding is shown in the drawings. Resistors R6 and R7 convert the current induced in the secondary winding of the transformer T 2 into a voltage signal. In case that the switching transistor Q s is turned on, the current flows through an output terminal of the inverter 44 via the upper output unit 53 from the high voltage power +V ⁇ , a forward bias is generated in a diode D 3 and thus the diode D 3 is conductive, and a backward bias is generated in a diode D and thus the diode D is not conductive.
  • a capacitor C 6 is used to eliminate the AC noise, a variable resistor VRi is used to adjust a potential level of the output signal SENSE, and the voltage signal SENSE adjusted by the variable resistor VRi is fed back into the PWM controller 51.
  • the switching transistor Q s is turned off, the current flows through the high voltage power -Vi via the primary winding of the lower output unit 54 from a middle tap terminal of the high voltage power V 1 ( a forward bias is generated in the diode D 4 and thus the diode D 4 is conductive, a backward bias is generated in the diode D 3 , and thus the diode D 3 is not conductive.
  • the current feedback unit 55 senses the output current, generates the sensing signal SENSE to control the switching transistor Q s , and electrically separates the switching unit from the inverter output unit by the transformer T 2 .
  • a ground level of the current feedback unit 55 is connected to the minus terminal -V 2 of the switching power V 2 and is electrically separated from the high voltage power Vi to adjust an output level of the inverter.
  • oscillation or noise occurring in the output of the inverter by operating the switching transistor Q 2 at a high frequency can be prevented.
  • the RF switch unit 47 includes the switch controller 57, switches
  • the switch controller 57 turns on and/or off the switch 58, as shown in FIG. 1 B.
  • the switch 58 is turned on by the switch controller 57, the inductance L F of the fluorescent lamp and the shut capacitor C S ⁇ serve as an attenuation filter, thereby attenuating an RF signal applied to the fluorescent lamps.
  • the RF signal is attenuated to less than a predetermined level, the light of the fluorescent lamps are turned off, and thus turning on and/or off the light of the fluorescent lamps can be controlled by turning on and/or off the switch controller 57.
  • FIG. 7 is a graph illustrating a signal attenuation effect due to an RC filter.
  • an RC filter has constant impedance, as the frequency of a signal is increased, the attenuation of the signal is increases linearly.
  • the attenuation of the signal is about 1/100 - 1/1000 (0.1 - 0.01 %), and thus the RF signal applied to the fluorescent lamps can be cut off.
  • a desired attenuation can be achieved by adjusting the capacity of the shunt capacitor by varying the impedance of the RC filter as well as the frequency of the RF signal.
  • FIG. 6 illustrates a system for turning on and off a fluorescent lamp in case that a plurality of fluorescent lamps are divided into several groups.
  • the fluorescent lamps installed in one building are separated into first through n-th groups 851 , . . . , 85n by each floor, and switch units 811 , . . . , 81 n for turning on and/or off an RF signal applied to each group, thereby achieving separate on/off control of each group.
  • a main switch unit 83 for turning and/or off the entire fluorescent lamps of all groups may be additionally included.
  • the switch unit for controlling the fluorescent lamps of each group may be separated on each floor into different rooms, installed in a place such as a central administration room or both.
  • a place such as a central administration room or both.
  • an operating frequency varies according to the optical transceiver included in each switch unit, thereby turning on and/or off the fluorescent lamps by each group.
  • an output voltage of a switching controller is maintained at a predetermined level even though the load, the output voltage and/or current or the operating current varies according to switching, thereby an on and/or off operation of the switch is stably performed, and the switch is used for an AC signal as well as a DC signal.
  • the on and/or off operation of the switch is controlled using a remote control, and the current flowing through elements or components used in the switching device is not large, and thus the elements or components are embedded as one integrated circuit.
  • the switching device can be adopted in an electronic ballast for a discharge lamp and can be used to turn on and/or off the discharge lamp, thereby preventing a surge phenomenon occurring when the power of the discharge lamp is turned on and/or off, and performing a stable operation even though a high number of discharge lamps are simultaneously turned on and/or off.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L'invention concerne un dispositif de commutation électronique utilisant une alimentation à découpage. Le dispositif de commutation électrique comprend une unité de commande de commutation destinée à activer ou à désactiver un élément de commutation à une fréquence prédéterminée en fonction d'un signal de commutation ; un transformateur auquel est appliqué une puissance d'entrée, servant à régler la puissance d'entrée en fonction de l'état activé ou désactivé de l'élément de commutation, et à découper la puissance d'entrée en signal de fréquence carré ; une unité de sortie de commande du commutateur servant à redresser le signal carré et à générer un courant continu ; et une unité de commutateur activée ou désactivée en fonction du courant continu fourni par l'unité de sortie de commande du commutateur. En conséquence, la tension de sortie de l'unité de commande de commutation est maintenue à un niveau prédéterminé même si la charge, la tension de sortie et/ou le courant ou le courant d'exploitation varient en fonction de la commutation, une opération d'activation et/ou de désactivation du commutateur pouvant ainsi être exécutée de manière stable.
PCT/KR2002/000150 2001-02-05 2002-02-01 Appareil de commutation electrique et regulateur electronique WO2002063756A1 (fr)

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Cited By (1)

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EP2315505A1 (fr) * 2009-10-15 2011-04-27 Nxp B.V. Procédé de contrôle d'un circuit à demi-pont, et circuit à demi-pont commandé avec celui-ci

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KR100749761B1 (ko) * 2006-06-29 2007-08-16 주식회사 이노씨스 단일 페어 선을 이용한 시분할 데이터 수집 시스템
KR100865237B1 (ko) * 2007-06-28 2008-10-23 쿠쿠전자주식회사 유도 가열 기기
KR101401719B1 (ko) * 2007-12-17 2014-06-02 대성전기공업 주식회사 차량용 에이치아이디램프 교체 알림 장치
KR101988049B1 (ko) * 2012-10-05 2019-06-12 강동엽 콘덴서를 생략한 발전용 인버터

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JPH11268446A (ja) * 1998-03-20 1999-10-05 Tomohiro Ueda たえず翌月分も見ることができるカレンダー

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JP3521509B2 (ja) * 1994-12-07 2004-04-19 株式会社デンソー 放電灯点灯装置
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JPH08305095A (ja) * 1995-05-02 1996-11-22 Fuji Xerox Co Ltd 画像形成装置
JPH11102525A (ja) * 1997-09-30 1999-04-13 Asahi Optical Co Ltd レンズ位置調整固定装置及びレンズ位置調整固定方法
JPH11268446A (ja) * 1998-03-20 1999-10-05 Tomohiro Ueda たえず翌月分も見ることができるカレンダー

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP2315505A1 (fr) * 2009-10-15 2011-04-27 Nxp B.V. Procédé de contrôle d'un circuit à demi-pont, et circuit à demi-pont commandé avec celui-ci

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