WO2002060047A1 - Dispositif inverseur - Google Patents

Dispositif inverseur Download PDF

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Publication number
WO2002060047A1
WO2002060047A1 PCT/JP2002/000517 JP0200517W WO02060047A1 WO 2002060047 A1 WO2002060047 A1 WO 2002060047A1 JP 0200517 W JP0200517 W JP 0200517W WO 02060047 A1 WO02060047 A1 WO 02060047A1
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WO
WIPO (PCT)
Prior art keywords
section
energization
motor
pwm
inverter device
Prior art date
Application number
PCT/JP2002/000517
Other languages
English (en)
Japanese (ja)
Inventor
Keizo Matsui
Hiroshi Okui
Masanori Ogawa
Original Assignee
Matsushita Electric Industrial Co., Ltd.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Matsushita Electric Industrial Co., Ltd. filed Critical Matsushita Electric Industrial Co., Ltd.
Publication of WO2002060047A1 publication Critical patent/WO2002060047A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/06—Arrangements for speed regulation of a single motor wherein the motor speed is measured and compared with a given physical value so as to adjust the motor speed
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/14—Electronic commutators
    • H02P6/16—Circuit arrangements for detecting position
    • H02P6/18—Circuit arrangements for detecting position without separate position detecting elements
    • H02P6/182—Circuit arrangements for detecting position without separate position detecting elements using back-emf in windings
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P7/00—Arrangements for regulating or controlling the speed or torque of electric DC motors
    • H02P7/06—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current
    • H02P7/18—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power
    • H02P7/24—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices
    • H02P7/28—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices
    • H02P7/285—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices controlling armature supply only
    • H02P7/29—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices controlling armature supply only using pulse modulation

Definitions

  • the present invention relates to an inverter device that drives a motor used in an air conditioner or the like at an arbitrary frequency.
  • Highly efficient DC brushless motors are widely used as motors used in air conditioners. They consist of a stator consisting of windings and a rotor that is a rotor with magnets.
  • an inverter device for driving such a DC brushless motor a DC obtained by rectifying an AC power supply by a rectifier circuit is desirably turned on and off by switching elements connected to the rectifier circuit.
  • the motor is driven by converting it into AC and inputting its output to the three-phase winding of the motor.
  • Figure 15 shows the configuration of a general inverter device.
  • the DC voltage obtained by rectifying the voltage from the AC power supply 1 by the rectifier circuit 2 is converted by the switching elements 5a to 5f, which are connected in parallel with the reflux diodes 6a to 6f, respectively. It is switched and modulated by a modulation method such as PWM (Pulse Width Modulation) to form a three-phase AC voltage.
  • PWM Pulse Width Modulation
  • the three-phase AC is input to the motor 4, and the motor 4 rotates at a desired AC frequency specified by the switching elements 5a to 5f.
  • the zero cross position of the induced voltage of the motor can be calculated from the motor terminal voltage.
  • timer processing is performed so that a predetermined phase angle is obtained from the zero cross position, and the energization pattern is switched.
  • Figure 16 shows the timing when the general three-phase DC brushless motor is driven, the induced voltage of each phase, the zero-cross detection signal of the induced voltage, the timer for phase control, and the timing when the six switching elements are turned on. Show.
  • a 120-degree energization drive which is a drive having a section in which the energization width per phase is 120 degrees in electrical angle, is realized. Disclosure of the invention
  • the waveform of the current flowing through the motor is a rectangular wave with a conduction angle of 120 degrees.
  • the current fluctuated greatly every 60 degrees in electrical angle, and the resulting noise, that is, the noise of the cogging component, became considerably loud.
  • it is necessary to drive the motor with a current having the same shape as the induced voltage of the motor, but the efficiency could not be maximized because of the rectangular wave current.
  • FIGS. 18A to 18D show the paths of the current flowing through the switching element and the motor in the case of the 120-degree conduction method shown in FIG. 18A, 18B, 18C, and 18D correspond to the switching sections (a), (b), (c), and (d) in FIG.
  • the solid line represents the path when shoving is on
  • the thin broken line represents the current path when shoving is off.
  • the thick broken line is the continuous current due to the motor inductance of the current in the previous mode.
  • part of the current flowing through the motor winding is: The current flows through the diode arranged in parallel with the capacitor, and flows backward to the capacitor in the rectifier circuit in a direction different from the normal direction. At this timing, the current flowing through the motor windings and di was rapidly attenuated, so that the current waveform had a more rectangular shape.
  • the current waveform was a rectangular waveform, so that the efficiency was reduced and the vibration noise was large.
  • the present invention solves the above-mentioned problems.When driving a motor at a variable frequency with three-phase AC, the motor efficiency is improved, torque ripple is reduced, noise and vibration are suppressed, and stable motor operation is performed. It is an object of the present invention to provide an inverter device that realizes the above.
  • An inverter device for driving a motor with an alternating current having a desired frequency, comprising: switching means including a plurality of switching elements and a plurality of diodes connected in parallel to the switching elements; Power supply control means for controlling the operation of the switching means to drive the motor at a desired frequency to control the power supply to the motor winding; voltage detection means for detecting the terminal voltage of the motor; Position and speed estimating means for estimating the magnetic pole position and speed of the rotor of the motor by comparing with a reference voltage, and a speed for outputting a voltage for controlling the motor speed to a given target speed to the energizing control means. Control means.
  • the energization control means controls energization according to the rotor magnetic pole position estimated by the position / velocity estimating means, and sets an energization width in a range of 120 degrees or more and less than 180 degrees at that time.
  • a first section for performing PWM control of the switching element is provided in a first portion of one energizing section, and a second section for constantly turning on a predetermined switching element is provided after the first section, After the second section, a third section for controlling the switching element by PWM is provided.
  • the inverter device may further include a PWM position setting unit that shifts a start position of the second energization section according to an output voltage value output by the speed control unit.
  • the PWM position setting means shifts the start position of the second energization section forward in the energization section as the output voltage value output by the speed control section increases. To do.
  • the inverter device may further include an energization width setting unit that changes the energization width of the energization section in accordance with the output voltage value output by the speed control unit.
  • the power supply width setting means makes the power supply width of the power supply section narrower as the output voltage value output by the speed control means becomes larger.
  • the inverter device includes a recirculation period detecting means for detecting a recirculation period in which a current flowing through the motor flows back through the diode, and a width of the energization section according to the length of the recirculation period output by the recirculation period detection means.
  • the power supply width setting means for determining may be further provided.
  • the inverter device includes a recirculation period detecting means for detecting a recirculation period in which a current flowing through the motor returns to the diode, and a second recirculation period output by the recirculation period detecting means.
  • PWM position setting means for determining a start position of a section may be provided.
  • energization is larger than 120 degrees in electrical angle
  • the operation is performed within a range of less than 180 degrees, and when switching of motor current occurs, the switching element of the phase in which switching does not occur is not pulse-width-modulated. A noise level is achieved.
  • the width of the current supply section is changed according to the voltage value corresponding to the speed to be controlled. As a result, a stable, high-efficiency, low-vibration, and low-noise motor drive is realized regardless of the load operation.
  • FIG. 1 is a block diagram showing a configuration of an inverter device according to Embodiment 1 of the present invention.
  • FIG. 2A is a diagram illustrating an energization method in a conventional inverter device
  • FIG. 2B is a diagram illustrating an energization method in the inverter device of the first embodiment.
  • FIG. 3A shows a current waveform under the control of the conventional inverter device
  • FIG. 3B shows a current waveform of the motor current under the control of the inverter device of the present invention.
  • FIG. 4 is a time chart showing the induced voltage at the time of driving the motor by the impeller device according to the present invention, the ON / OFF timing of the switching element, and the like.
  • FIGS. 5A to 5D are diagrams showing paths of a current flowing through the switching element and the motor in the embodiment of the inverter device according to the present invention.
  • FIGS. 6A to 6C are diagrams showing paths of a current flowing through the switching element and the motor in the embodiment of the inverter device according to the present invention.
  • Fig. 7A shows an example of a terminal voltage waveform by the inverter device of the present invention
  • Fig. 7B shows an example of a motor current waveform
  • Fig. 7C shows an example of a current waveform of a DC portion of the inverter device. It is.
  • FIG. 8 is a diagram illustrating the detectable range of the induced voltage for each load torque at different PWM position shift amounts.
  • FIG. 9 is an operation characteristic diagram of the PWM position setting unit of the inverter device according to the first embodiment.
  • FIG. 10 is an operation characteristic diagram of the conduction width setting unit of the inverter device according to the first embodiment.
  • FIG. 11 is a block diagram showing a configuration of a second embodiment of the inverter device according to the present invention.
  • FIG. 12 is a diagram for explaining the principle of detecting the recirculation period based on the motor terminal voltage.
  • FIG. 13 is an operation characteristic diagram of the PWM position setting unit in one embodiment of the inverter device of the present invention.
  • FIG. 14 is an operation characteristic diagram of the conduction width setting unit of the inverter device according to the second embodiment.
  • FIG. 15 is a block diagram showing the configuration of a conventional inverter device.
  • Fig. 16 is a time chart showing the induced voltage and the on-timing of the switching element when the motor is driven by the conventional inverter device.
  • Fig. 17A shows an example of the waveform of the terminal voltage of a conventional inverter device
  • Fig. 17B shows an example of the waveform of the motor current
  • Fig. 17C shows an example of the current waveform of the DC section of the inverter device.
  • FIGS. 18 to 18D are diagrams showing current paths of current flowing through the switching element and the motor of the conventional inverter device. ⁇ Best mode for carrying out the invention
  • FIG. 1 shows a configuration of an embodiment of the inverter device of the present invention.
  • the inverter device 3 has a switching unit 6 including switching elements 5 a to 5 f and free-wheeling diodes 6 a to 6 f connected in antiparallel to the switching elements 5 a to 5 f.
  • the inverter device 3 includes a voltage detection unit 7, a rotor position detection unit 8, a conduction control unit 9, and a speed control unit 1 for controlling the switching operation of each of the switching elements 5a to 5f of the switching unit 6.
  • energization width setting unit 11 and PWM position setting unit 12 are provided.
  • the inverter device 3 converts the DC voltage obtained by rectifying the input from the AC power supply 1 to DC by the rectifier circuit 2 into a three-phase AC voltage by the switching operation of the switching elements 5 a to 5 f of the switching unit 6. To drive a brushless DC motor (hereinafter referred to as “motor”) 4 at a desired frequency.
  • motor a brushless DC motor
  • the voltage detector 7 detects the terminal voltage of each phase of the winding of the motor 4.
  • the rotor position / speed detector 8 estimates and detects the position and speed of the magnetic pole of the rotor of the motor 4 using the detected voltage.
  • the energization control unit 9 drives the switching elements 5 a to 5 f in accordance with a drive signal for driving the motor 4 based on information on the magnetic pole position of the rotor estimated by the rotor position / speed detection unit 8. Output to the switching unit 6 for use.
  • the speed control unit 10 outputs an output so that the speed of the rotor of the motor 4 becomes the target speed based on a deviation between the speed of the rotor estimated by the rotor position speed detection unit 8 and a target speed given from the outside. Calculate and control voltage.
  • the energization width setting unit 11 selects an optimal energization width according to the output voltage information from the speed control unit 10 and outputs it to the energization control unit 9.
  • the PWM position setting unit 12 starts the driving of the switching element by the PWM control based on the output voltage information from the speed control unit 10 (hereinafter referred to as “PWM start position”. Details will be described later).
  • PWM start position the output voltage information from the speed control unit 10
  • the energization control unit 9 drives the motor 4 by controlling the switching elements 5 a to 5 f according to the input energization width and the PWM start position.
  • FIG. 2A shows a base signal waveform in a general 120-degree energization method, and is a diagram showing an output voltage of one phase centered on one energization section.
  • FIG. 2B shows a base signal waveform in the energization method of the inverter device according to the present embodiment.
  • the first 60 degrees are driven to always turn on the switching element, and the second half 6 degrees.
  • the switching elements 5a to 5f are driven by PWM control.
  • the energizing section of each phase is switched every 120 degrees, and any phase is always energized, so that energization to the motor 4 is continuously performed and a torque is applied.
  • the energization interval is set to 120 degrees or more per phase ((120 + H) degrees, Q! ⁇ 0). .
  • the conduction drive is performed by the PWM control during the first predetermined time, and after the predetermined time has elapsed, the conduction drive that is always turned on without performing the PWM control is provided. Then, the energization drive is performed again by the PWM control.
  • the section that is always on without PWM control is started after a lapse of a predetermined time from the start of the energization section, that is, after a predetermined electrical angle (hereinafter referred to as “PWM position shift angle”) ⁇ .
  • PWM position shift angle a predetermined electrical angle
  • the start of the section that is always on without performing the PWM control in the present embodiment is a predetermined shift angle with respect to the start of the section that is always on without performing the conventional PWM control. will be shifted by ⁇ '.
  • the energization section length is set by the energization width setting unit 11
  • the PWM start position that is, the PWM position shift angle
  • the energization width is set to be as wide as 120 degrees or more, and in the energization section, the energization drive is performed by PWM control first, and then the energization control that is always on is performed. I do.
  • the energizing drive in which the pulse width modulation of the switching element is not performed is performed, so that the current waveform is smooth and the motor efficiency is improved. Furthermore, torque ripple is reduced, noise and vibration are suppressed, and stable motor operation is possible.
  • FIG. 3D is a diagram showing a form of a current waveform at the time of driving by the conventional 120-degree conduction method.
  • a current flows through the motor winding in a substantially rectangular waveform.
  • the motor current flows in a section in which the current rise and fall due to the motor inductance are added in addition to the energized section.
  • FIG. 3B is a diagram showing a current form of a conduction method according to the present invention.
  • the motor current flows in a long section exceeding 120 degrees.
  • the current flowing by the inductance component (hereinafter, referred to as “reflux component”) increases. Therefore, the current waveform becomes smoother.
  • FIG. 4 is a diagram illustrating an example of an energization method in the inverter device of the present embodiment.
  • the induced voltage of each phase and the cross-detection signal of the induced voltage see “Comparison of U, V, and W phases” in the figure) during energization in the inverter device of this embodiment
  • FIG. 5 is a diagram showing the timer operation of FIG. 6 and the ON timings of six switching elements (described as U, V, and W phase driving in the figure). In this way, the zero crossing point of the induced voltage of each phase is detected, and the timer is used several times to switch the six switching elements on and off according to the timing.
  • FIGS.5A to 5D and FIGS.6A to 6C show the current flowing through the switching element and the motor winding in the inverter device when driven by the energizing method shown in FIG. 4 for each energizing section. is there.
  • the path of the current flowing through the motor winding that is, the conducting phase
  • the route diagrams in FIGS. 5A to 5D correspond to the switching sections (a) to (d) shown in FIG. 4 respectively
  • the route diagrams in FIGS. 6A to 6C correspond to the switching sections ( e) to (g) respectively.
  • the solid line indicates the path when shoving is on, and the thin broken line indicates the current path when shoving is off.
  • the thick broken line is the continuous current due to the inductance of the current immediately before.
  • FIG. 7A to 7C show waveforms of the current of the motor driven by the inverter device according to the present embodiment, the terminal voltage, and the current (I) of the DC portion of the inverter device.
  • a current of almost the same width is generated in the form of a rectangular wave for the 120-degree energization width, and the Is almost constant at the PWM ON timing as a sum of three phases, and a large current in the opposite direction every 60 degrees (a downward current sometimes seen in Fig. 17C). Peak current).
  • the energization width is widened (130 degrees energization in this example), and the PWM control start timing is set to the voltage drive waveform set at the center.
  • the PWM control start timing is set to the voltage drive waveform set at the center.
  • the PWM position setting unit 12 determines a position (PWM start position) for optimally starting pulse width modulation.
  • the optimum PWM start position is determined in consideration of efficiency improvement and control stability. By moving the PWM start position from the normal position (switching position every 120 degrees in the conventional 120-degree conduction method), a DC reverse current does not occur, which makes the current waveform smoother and efficient. Is improved.
  • FIG. 8 shows the change in the detectable range of the induced voltage with respect to the load torque when the PWM start position shift amount is 0 degree, 10 degrees P, and 20 degrees.
  • the detectable range of the induced voltage becomes narrower as the shift amount of the PWM start position increases and as the load torque increases.
  • the drive stability decreases as the detectable range of the induced voltage becomes narrower, and the drive stability decreases as the load torque increases. Therefore, in order to ensure the driving stability at a certain level, it is preferable to change the shift amount of the PWM position according to the load increase so that the detectable range of the induced voltage does not become narrow even if the load increases. .
  • FIG. 9 is a diagram for explaining the control of the shift amount of the PWM start position by the PWM position setting unit 12 to address the above problem.
  • Load torque is output from speed controller 10 Since the position can be estimated from the force voltage value, the PWM position setting unit 12 determines the PWM start position according to the output voltage value of the speed control unit 10. That is, as shown in FIG. 9, when the output voltage value is equal to or less than the predetermined value D1, the shift angle of the PWM position is set to the predetermined angle ⁇ 1, and the current waveform is smoothed to improve the efficiency. Also, when the output voltage is between the predetermined value D1 and the predetermined value D2, the PWM position shifts gradually as the motor load increases and the output voltage value output by the speed control unit 10 increases. Reduce the angle.
  • the PWM position shift angle is set to a value that can sufficiently secure a detectable range of the induced voltage.
  • the shift amount of the PWM start position is set to 0.
  • the PWM position setting unit 12 changes the shift amount in accordance with the magnitude of the load, thereby securing the detectable range of the induced voltage at a certain level even when the load increases.
  • the motor can be driven stably.
  • the detectable range of the induced voltage changes depending on the conduction width, as in the relationship between the shift amount of the PWM start position and the detectable range of the induced voltage.
  • the wider the conduction width the narrower the range in which the induced voltage can be detected, and vice versa.
  • the energization width is 120 degrees
  • the non-energization section is 60 degrees
  • the induced voltage detectable range is also a range obtained by subtracting the reflux current section from 60 degrees.
  • the detectable range is a narrow range excluding the reflux current section from 40 degrees. Therefore, when the power supply width is wide, the detectable range is narrowed, and the driving stability is further reduced. Therefore, in order to ensure the driving stability more sufficiently, it is preferable to change the conduction width as the load increases.
  • FIG. 10 is a diagram for explaining the control of the power supply width by the power supply width setting unit 11.
  • the power supply width setting unit 11 estimates the load torque based on the output voltage value output from the speed control unit 10 and determines the power supply width according to the output voltage value.
  • the energization width is set to ⁇ , and the current waveform is smoothed to improve the efficiency.
  • the output voltage value is in the range between the predetermined value DA and the predetermined value DB
  • the conduction width is gradually reduced as the output voltage value increases.
  • the energization width is fixed at 120 degrees.
  • negative By controlling the conduction width according to the size of the load, even when the load increases, the detectable range of the induced voltage can be sufficiently secured, and the motor can be driven stably.
  • FIG. 11 shows a block diagram of the inverter device according to the second embodiment.
  • the inverter device 3 a further includes a reflux period detecting unit 13 in addition to the configuration of the device of the first embodiment.
  • the DC voltage obtained by rectifying the input from the AC power supply 1 into DC by the rectifier circuit 2 is converted into a three-phase AC voltage in the switching unit 6, and the motor 4 is driven by the voltage. This is the same as in the case of form 1.
  • the recirculation period detection unit 13 uses the voltage of the motor 4 detected by the voltage detection unit 7 to detect the time length of the period in which the recirculation current of the windings of the motor 4 flows (hereinafter referred to as “reflux period”). I do.
  • the power supply width setting unit 11 determines the power supply width by using the time length information of the circulation period, and instructs the power supply control unit 9 of the power supply width.
  • the PWM position setting unit 12 determines an optimum PWM position by using the time length information of the circulation period, and instructs the energization control unit 9 of the PWM position.
  • FIG. 12 is a diagram for explaining the operation of detecting the time length of the circulation period by the circulation period detection unit 13.
  • FIG. 12 is a diagram showing a waveform of a terminal voltage at a certain timing in one phase of the motor 4.
  • the induced voltage generated in the winding of the motor 4 is detected at the timing of the energization ON of the PWM control.
  • a circulating current is generated due to the inductance of the current flowing through the circuit. Since the terminal voltage of the motor 4 becomes high due to this circulating current, a circulating period in which the voltage is high appears at the front of the non-energized section.
  • the motor terminal voltage is monitored, and it can be determined that the recirculation period has ended when the motor terminal voltage decreases from a value higher than a predetermined level (referred to as a “reflux determination level”) to a lower level. Therefore, the recirculation period detecting unit 13 detects the terminal voltage of the motor 4, and determines that the recirculation period has ended when the value of the terminal voltage becomes equal to or lower than a predetermined recirculation determination level. For example, in Fig.
  • the terminal voltage at time tA is VA
  • the terminal voltage at tB is VB and the recirculation judgment level is VK
  • the recirculation period detector 13 detects the terminal voltage VA and VB when VA> VK and VB and VK, and then detects the time tA. It is determined that the reflux period has ended between and tB.
  • the PWM position setting unit 12 operates as follows.
  • the PWM position setting unit 12 determines the optimal PWM position as in the case of the first embodiment.
  • the optimum PWM position is determined in consideration of efficiency improvement and control stability by the PWM start position.
  • Control stability is determined by the detectable range of the induced voltage, and the narrower the range, the lower the drive stability. Therefore, driving stability is ensured by changing the PWM start position according to the length of the recirculation period detected by the recirculation period detection unit 13.
  • FIG. 13 is a diagram illustrating the control of the PWM start position by the PWM position setting unit 12 of the present embodiment.
  • the PWM position setting unit 12 estimates the load torque based on the recirculation period length, and determines the PWM start position accordingly. As shown in this figure, when the reflux period length is less than L1, the shift angle of the PWM start position is set to ⁇ 1. This smoothes the current waveform and improves efficiency.
  • the motor load increases and the recirculation period length is within the predetermined range, that is, when the recirculation period length is between L1 and L2, the PWM position shift angle is gradually reduced according to the motor load. Let it. Reflux period length is specified value
  • the detectable range of the induced voltage varies depending on the width of the conduction. In other words, the wider the conduction width, the narrower the range in which the induced voltage can be detected, and the lower the driving stability. As the load torque increases and the recirculation period increases, the stability further decreases. Therefore, in order to ensure the driving stability, it is preferable to change the width of the current supply as the reflux period length increases.
  • FIG. 14 is a diagram illustrating the control of the conduction width of the conduction width setting unit 11 according to the present embodiment.
  • the power supply width setting unit 11 determines the power supply width according to the reflux period length. As shown in the figure, when the reflux period length is less than LA, the energization width is set to ⁇ MAX to smooth the current waveform and improve efficiency. Furthermore, when the load on the motor increases and the recirculation period length is within a certain range (between LA and LB), the conduction width is gradually reduced according to the recirculation period length. When the reflux period length is equal to or greater than a predetermined value (LB), the power supply width is fixed at 120 degrees. In this way, by varying the conduction angle width according to the reflux period length, a sufficient detectable range of the induced voltage can be secured even when the load is increased, and the motor can be driven stably. Can be.
  • LB predetermined value
  • impeller device in the present embodiment may be realized by a dedicated hardware circuit or by software using a microcomputer.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)
  • Control Of Ac Motors In General (AREA)

Abstract

L'invention concerne un dispositif inverseur composé d'un bloc de mesure de position/vitesse de rotor (8) destiné à mesurer la position/vitesse d'un rotor à partir d'une tension terminale d'un moteur (4), d'un bloc de commande de vitesse (10) destiné à commander la vitesse du moteur sur une vitesse cible, d'un bloc de réglage de période d'application de courant (11) destiné à régler la période d'application de courant au moteur (11), d'un bloc de réglage de position par modulation d'impulsions en durée (12) destiné à régler la position par modulation d'impulsions en durée dans l'application de courant au moteur, et d'un bloc de commande d'application de courant (9) destiné à commander l'application de courant au moteur. Le bloc de commande d'application de courant (9) commande l'application de courant en fonction de la position d'un pôle magnétique du rotor de manière que la période d'application de courant se situe dans une gamme de 120 ° à 180 °. La première partie d'une période d'application de courant comporte une première section durant laquelle des éléments de commutation sont commandés par modulation d'impulsions en durée, une deuxième section consécutive à la première, durant laquelle un élément de commutation prédéterminé est maintenu en marche, et une troisième section consécutive à la deuxième, durant laquelle les éléments de commutation sont commandés par modulation d'impulsions en durée.
PCT/JP2002/000517 2001-01-26 2002-01-24 Dispositif inverseur WO2002060047A1 (fr)

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JP2001-18424 2001-01-26
JP2001018424A JP4226224B2 (ja) 2001-01-26 2001-01-26 インバータ装置

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JP (1) JP4226224B2 (fr)
KR (1) KR100618218B1 (fr)
CN (1) CN100342636C (fr)
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Cited By (3)

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JP2013085372A (ja) * 2011-10-07 2013-05-09 Aisin Seiki Co Ltd 交流モータの制御装置および制御方法
KR20140010590A (ko) * 2012-07-13 2014-01-27 삼성전자주식회사 모터 구동장치 및 이를 이용한 냉장고

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JP4557955B2 (ja) * 2006-11-08 2010-10-06 株式会社日立製作所 モータ駆動回路及びモータ駆動方法並びに半導体集積回路装置
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JP5051226B2 (ja) * 2007-06-27 2012-10-17 株式会社明電舎 擬似電流形１２０度通流インバータ
WO2011052253A1 (fr) * 2009-10-28 2011-05-05 Three Eye Co., Ltd. Dispositif de commande de moteur pour moteur à vitesse variable
JP5606899B2 (ja) * 2010-12-24 2014-10-15 ミネベア株式会社 ブラシレスモータの駆動制御装置
WO2012086095A1 (fr) * 2010-12-24 2012-06-28 Three Eye Co., Ltd. Appareil de commande de moteur pour la commande d'un moteur triphasé du type à vitesse variable
ITTO20120311A1 (it) * 2012-04-10 2013-10-11 Gate Srl Dispositivo circuitale di controllo per un motore brushless trifase in corrente continua
KR101503980B1 (ko) * 2012-09-28 2015-03-18 삼성전기주식회사 모터 구동 장치 및 모터 구동 방법
JP6425898B2 (ja) * 2014-03-03 2018-11-21 三菱重工サーマルシステムズ株式会社 インバータ制御装置及びその方法
JP6937678B2 (ja) * 2017-12-08 2021-09-22 ルネサスエレクトロニクス株式会社 半導体装置およびモータ駆動システム

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EP1845609A2 (fr) * 2006-04-14 2007-10-17 JOHNSON ELECTRIC MONCALIERI S.r.l. Dispositif de circuit de contrôle pour un moteur à courant continu, triphasé et sans balai
EP1845609A3 (fr) * 2006-04-14 2008-12-24 JOHNSON ELECTRIC MONCALIERI S.r.l. Dispositif de circuit de contrôle pour un moteur à courant continu, triphasé et sans balai
JP2013085372A (ja) * 2011-10-07 2013-05-09 Aisin Seiki Co Ltd 交流モータの制御装置および制御方法
KR20140010590A (ko) * 2012-07-13 2014-01-27 삼성전자주식회사 모터 구동장치 및 이를 이용한 냉장고
EP2685626A3 (fr) * 2012-07-13 2017-06-14 Samsung Electronics Co., Ltd Appareil d'entraînement de moteur BLDC et réfrigérateur l'utilisant
KR101953124B1 (ko) 2012-07-13 2019-03-04 삼성전자주식회사 모터 구동장치 및 이를 이용한 냉장고

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JP4226224B2 (ja) 2009-02-18
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CN1701502A (zh) 2005-11-23
KR20030020266A (ko) 2003-03-08

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