WO1996005650A1 - Systeme d'attaque de moteur - Google Patents

Systeme d'attaque de moteur Download PDF

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Publication number
WO1996005650A1
WO1996005650A1 PCT/JP1995/001435 JP9501435W WO9605650A1 WO 1996005650 A1 WO1996005650 A1 WO 1996005650A1 JP 9501435 W JP9501435 W JP 9501435W WO 9605650 A1 WO9605650 A1 WO 9605650A1
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WIPO (PCT)
Prior art keywords
motor
output
current
voltage
input
Prior art date
Application number
PCT/JP1995/001435
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English (en)
Japanese (ja)
Inventor
Masatoshi Morikawa
Kunio Seki
Yasuhiko Kokami
Kozo Sakamoto
Isao Yoshida
Original Assignee
Hitachi, Ltd.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Hitachi, Ltd. filed Critical Hitachi, Ltd.
Publication of WO1996005650A1 publication Critical patent/WO1996005650A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/06—Arrangements for speed regulation of a single motor wherein the motor speed is measured and compared with a given physical value so as to adjust the motor speed

Definitions

  • the present invention relates to a method for driving a small motor, and more particularly to a method for driving a small and high-precision brushless motor used in 0 A equipment with high efficiency and high reliability, and capable of reducing manufacturing costs.
  • a wide variety of motors are used in many of our daily uses, such as home appliances and office automation equipment.
  • the driving method also varies depending on the type of motor and the purpose of use.
  • rotating disks such as hard disk drives (hereinafter referred to as HDDs)
  • DC brushless motors with simple driving circuits and high reliability during long-time operation especially called spindle motors
  • the demand for smaller and thinner HDDs has led to an increase in the use of sensorless types, in which the position detection sensor for the motor rotor has been removed.
  • the method of driving this motor efficiently is described in NRC Research and Development, Volume 32, Nanno Kuichi 3, July 1991, July, pp. 368 to 378 (NEC Res. & Develop., Vol.
  • This prior art relates to a dry integrated circuit that drives a spindle motor for an HDD using a pulse width modulation (PWM) signal of a three-phase rectangular wave.
  • PWM pulse width modulation
  • This circuit consists of a PWM circuit that sets the duty of the PWM voltage by comparing the error voltage for phase control with the output sense voltage.
  • the difference between the output voltage of each phase and the midpoint potential of the three-phase coil is detected to detect the induced voltage generated by the motor, and the timing for driving the bridge circuit is determined by the selector from the detected voltage. create.
  • the difference between the sense voltage from the current detection resistor connected to the bridge circuit and the error voltage corresponding to the target speed is calculated.
  • the duty of the PWM signal is determined by comparison with the triangular wave voltage of 100 kHz.
  • a drive voltage is generated in the fuse generator based on information from the selector, and the upper arm transistor of the three-phase bridge circuit is driven by a rectangular wave, and the lower arm transistor is driven by a PWM signal.
  • the output current will be Flows through the U-phase upper arm and the coil to the V-phase lower arm, and when the lower arm is off, flows to the diode between the source and drain of the V-phase upper arm due to the inductance characteristics of the coil, and to the power supply Return (reflux state). Therefore, no current flows from the power supply to the ground in the reflux state, and no power is consumed. Due to this repetition, the output current flows in a rectangular waveform energized by 120 degrees.
  • the sensorless motor is realized by detecting the switching timing of each phase from the induced voltage, and ordinary rectangular wave linear drive is performed because PWM control is performed.
  • the power consumption of the power supply can be reduced as compared with.
  • all analog circuits are configured by insulated gate transistors, and do not use bipolar transistors.
  • a symmetrical layout is used to reduce offsets and improve accuracy. ing. This simplifies the manufacturing process, which helps reduce manufacturing costs.
  • synchronous motors are used in applications that require speed control and absolute positioning of rotors, such as machine tools and robots, instead of small motors such as hard disks.
  • the driving method of this motor is described in Japanese Patent Application Laid-Open Publication No. Hei 4-111 (published on Apr. 3, 1992).
  • a table stored in a ROM (read-only storage device) based on pulse information corresponding to the absolute position of the mouth obtained from the encoder such as a pulse generator attached to the motor Generates a three-phase reference sine wave whose phase is shifted by 120 degrees.
  • the current control signal obtained by comparing the output current with the target current value and the reference sine wave are multiplied by a multiplier to amplify the sine wave, and compared with a high-frequency triangular wave (sawtooth wave).
  • a high-frequency triangular wave sawtooth wave.
  • This PWM signal allows six traffic By turning on and off each transistor of a three-phase inverter circuit composed of a transistor, a three-phase sine-wave output current is obtained, and a synchronous motor is driven. It is not suitable for miniaturization of the system because it requires a position detector and R0M.However, since the motor is driven by a pseudo sine wave current, the phase switching becomes smooth, and the This means that the electromagnetic noise that occurs is minimized. It is also characterized by low power consumption due to PWM.
  • the current waveform is still a rectangular wave, and thus the current waveform is caused by L ⁇ diZdt (L: inductance of the motor coil, diZdt: time change rate of the output current). Electromagnetic noise during phase switching was not reduced, and this affected the control system, so the range of use in HDDs was limited. Therefore, there was no product other than the conventional example of the HDD motor driver integrated circuit product using the PWM technology. Also, depending on the power circuit that realizes the analog circuit of the insulated gate type transistor by performing the symmetrical layout, it may not be possible to obtain sufficient accuracy by this method alone.
  • the prior art described later requires a place for installing a rotor rotational position detector such as an encoder, and is not suitable for a field requiring a smaller motor. Furthermore, a ROM and its control circuit were required to extract the information stored in R0M based on the rotational position detection signal and generate a three-phase sine wave. Therefore, the circuit scale is large and the cost is high, and it is not suitable for driving a small motor requiring low cost.
  • An object of the present invention is to solve these two problems of the prior art at once, and to achieve both improvement of motor efficiency and low noise with a simple circuit configuration without using a position detector and its control circuit. Is to provide a motor driving method for realizing the above.
  • Another object of the present invention is to provide a method of driving a motor which is optimal for forming an analog circuit by using insulated gate transistors, thereby realizing a reduction in manufacturing cost and a reduction in system size.
  • the purpose is to detect the induced voltage generated in the motor through a filter, shape and amplify the waveform to form a three-phase sine wave, and then convert the three-phase sine wave to PWM to drive the bridge circuit. Rotating the motor with a sinusoidal output current And is achieved with. Also, current detection means may be provided at each output of the bridge circuit, the detection result may be fed back to the input, the output current may be squeezed, and the induced voltage generated in the motor may be detected.
  • the above and other objects are achieved by configuring a filter, a comparator, and the like by using the switched capacitor technology. It is also achieved by configuring the output circuit with an insulated gate type and driving it by PWM.
  • FIG. 1 is a block diagram of a three-phase motor drive system according to a first embodiment of the present invention.
  • FIG. 2 is a block diagram of a drive system of a spindle motor for a 2.5-inch hard disk drive according to a second embodiment of the present invention.
  • FIGS. 3a and 3b are circuit diagrams of a filter according to the second embodiment of the present invention.
  • FIG. 4 is a configuration diagram of a sine wave amplitude control unit.
  • FIGS. 5a and 5b are a circuit diagram of a sample-and-hold type comparator and an operation timing diagram thereof.
  • FIG. 6 is an input / output characteristic diagram of a comparator according to the second embodiment of the present invention.
  • FIGS. 7a and 7b are a diagram of a through current prevention circuit according to a second embodiment of the present invention and an explanatory diagram of its operation.
  • FIGS. 8a to 8c are output current waveform diagrams in the second embodiment of the present invention.
  • FIGS. 9a and 9b are diagrams showing the effect obtained in the second embodiment of the present invention.
  • D FIG. 10 is a block diagram of a three-phase motor drive system according to a third embodiment of the present invention.
  • FIG. 11 is a specific circuit diagram for creating a sine wave PWM signal in the third embodiment of the present invention.
  • FIG. 12 is a diagram showing the effect of the offset in the third embodiment of the present invention.
  • FIG. 13 is a block diagram of a three-phase motor drive system according to a fourth embodiment of the present invention.
  • FIG. 14 is a block diagram of a three-phase motor drive system according to a fifth embodiment of the present invention.
  • FIG. 15 is a diagram showing details of a part of a three-phase motor drive system according to a fifth embodiment of the present invention.
  • FIG. 16 is a block diagram of a three-phase motor drive system according to a sixth embodiment of the present invention.
  • FIG. 17 is a detailed circuit diagram of a three-phase motor drive system according to a sixth embodiment of the present invention.
  • FIG. 18 is a diagram showing switching characteristics of a current mirror according to the sixth embodiment of the present invention.
  • FIG. 19 is a timing chart of the PWM drive in the sixth embodiment of the present invention.
  • FIG. 20 is an output current waveform diagram in the sixth embodiment of the present invention.
  • FIG. 1 shows a block diagram of a three-phase motor drive system which is a typical embodiment of the present invention.
  • Reference number 1 is a three-phase motor consisting of U, V, and W phases, 2 to 7 are upper and lower arms of each phase composed of output transistors, 8 is a power supply for driving the motor, and 9 is a power supply for each phase.
  • Output voltage, 10 is a low-pass filter for extracting the induced voltage generated in the motor from the output voltage, 11 is the induced voltage of each phase, and 12 is the converted voltage to make the induced voltage a sine wave for driving the motor.
  • the amplitude control unit 13 performs pulse width modulation of a sine wave (Pulse Width Modulation);
  • a triangular (or sawtooth) carrier for PWM) 14 is a rotational speed detector that detects the motor rotation state from the induced voltage, and 15 is the motor speed from the rotational speed detector 14 detection signal.
  • Microprocessor or speed error detection circuit to judge and issue acceleration or deceleration command, 16 to 18 convert sine wave of amplitude control unit 12 to pulse with triangular wave PWM carrier 13 and It is a pulse generator that drives each arm 2-7.
  • a special feature of this system is that it has a system that drives a motor by turning on and off a bridge circuit with a sine wave PWM signal, making it possible to make the motor sensorless. The point is that, in the configuration of the members 9 to 12, a waveform detecting and shaping means for utilizing the induced voltage for the PWM sine wave is provided.
  • FIG. 2 is a block diagram of a system for driving a spindle motor for a 2.5-inch hard disk drive.
  • This motor is a sensorless brushless DC motor with a rated power supply voltage of 5 V, an internal resistance per phase of 1.9 ⁇ , and a coil inductance of 0.2 mH.
  • the present system is composed of an integrated circuit 300 having a one-chip motor drive circuit and an external microprocessor 15.
  • reference numerals 19 to 24 are insulated gate field effect transistors (hereinafter referred to as “insulated gate field effect transistors”).
  • MO SFET MO SFET
  • the upper arm is a P-channel transistor with a drain withstand voltage of 15 V and an on-resistance of 15 ⁇ ⁇ ⁇ . This is a ⁇ channel transistor.
  • 25 to 27 are comparators for modulating sine and triangular waves into PWM signals
  • 28 to 30 are for the upper and lower arms to be turned on at the same time, causing a through current from the power supply to ground. This is a through current prevention circuit for preventing such a situation.
  • MOSFETs are used as output elements because of their low resistance and high switching speed compared to bipolar transistors, and because they have a built-in diode between source and drain, they are suitable for PWM drive. It is.
  • a bipolar transistor may be used.
  • the reason why the upper arm is set to the ⁇ channel is that it is necessary to boost the maximum value of the driving pulse applied to the gate electrode to the power supply voltage or more. Because there is no. If a booster circuit such as a booster can be used, both upper and lower channels can be used.
  • the induced voltage can be extracted from the output voltage by the filter 10 composed of a capacitor and a resistor, and is input to the amplitude control circuit 12 and the phase detection circuit 14.
  • This finalizer is a so-called low-pass filter that removes the PWM carrier frequency 100 kHz from each output voltage and extracts only the 240 Hz induced voltage, and has a cutoff frequency f cut force of 2 kHz.
  • the induced voltage has a frequency of 1 Z 10 compared to f cut, so there is almost no phase shift due to the filter, and the bridge circuit can be driven simply by controlling the amplitude with this phase.
  • this form of filter requires very large capacitor and resistance values, which is not practical for a single semiconductor chip. Therefore, the desired characteristics are realized with a small element area by replacing the resistor with a capacitor using the switch-capacitor technology as shown in Fig. 3b and turning on and off SW1 and 2 alternately. .
  • a rectangular pulse proportional to the frequency of the induced voltage is formed in the rotation speed detecting circuit 14, and the pulse width of the rectangular pulse is counted by the external microprocessor 15 by the reference pulse.
  • reference numeral 12 denotes a sine wave amplitude control unit obtained from the induced voltage, and its configuration is shown in FIG.
  • Charge pump or DZA converter 201 that receives speed error signal 200 from external microprocessor 15 and converts it into amplitude control signal 202, and 203 according to its amplitude control signal 202
  • a gain control unit that controls the amplitude of the sine wave by adjusting the gain of the operational amplifier.
  • the operational amplifier used here is composed of a differential amplifier circuit of MOSFET, and the difference in offset voltage of each phase is minimized by using a method of symmetrically laying out differential pairs (common centroid). And
  • FIG. 5a is a simplified circuit diagram of the sample and hold type comparator
  • FIG. 5b is the timing of the switch operation.
  • reference numeral 2 12 is a CMOS inverter
  • 2 13 is a latch circuit. This switch requires a high-speed pulse of about several MHz, but in this case, the clock of the microphone processor is used.
  • FIG. 6 shows the input / output characteristics of the comparators 25 to 27.
  • the PWM signal is a rectangular wave with the same frequency as the triangular wave and a duty proportional to the size of the sine wave.
  • the arms 19 to 24 are driven by this PWM signal.
  • the upper and lower arms 19 and 20 for the U phase are controlled by the U-phase PWM signal 34
  • the upper and lower arms 21 and 22 for the V phase are controlled by the PWM signal 35 for the V phase.
  • the upper and lower arms 23, 24 for the W phase are driven by the signal 36.
  • FIG. 7a shows a through current prevention circuit in the U phase
  • the input inverter has the ability to charge and discharge the gate capacitances 41 and 42 sufficiently.
  • the sine wave PWM signal is 43
  • the switch 37 is turned on and the switch 38 is turned off.
  • the signal is "H”
  • the switch is turned off and on.
  • the sine wave PWM signal 4 3 In the case of “L”, the upper arm charges the gate capacitor 41 at high speed without the resistor and the lower arm Charging is performed according to the time constant of 0 and the gate capacitance 42.
  • the sine wave PWM signal 43 is "H"
  • the upper arm discharges according to the time constant of the resistor 39 and the gate capacitance 41.
  • the lower arm discharges at a high speed from the gate capacitance 42 without the intervention of a resistor, which causes the gate voltage 44 to fall and the gate voltage 45 to rise and have a delay time. This delays the turn-on of the transistors 2 and 3, which makes it possible to prevent shoot-through current. It is sufficient if the CR time constant is 0.5. Since the gate capacitances 41 and 42 are 211? And 1 nF, respectively, the resistors 39 and 40 are 25 0 ⁇ and 500 ⁇ .
  • FIG. 8 shows an output current waveform according to the second embodiment of the present invention. 4 6, 4 7,
  • 4 8 are sine wave signals of U, V and W phases, respectively, 49, 50 and 51 are output currents,
  • the output current of each phase is composed of the following current components.
  • the combination of the above 1) to 4) is determined by the on / off timing of each arm, and the output current has a zigzag waveform. What actually needs to be considered as the current consumption of the power supply is the combination of 1) and 3) above, and this power consumption does not perform PWM. Very small compared to normal linear drive. Also, by increasing the PWM carrier frequency, the output current zigzag can be ignored. Therefore, the output current can be regarded as almost a sine wave, and the electromagnetic noise of L ⁇ diZdt generated in the motor coil can be reduced.
  • FIGS. 9a and 9b The effects of this embodiment are shown in FIGS. 9a and 9b.
  • This is a comparison of the square wave drive and the square wave PWM drive, which are generally used as the spindle motor drive system of a hard disk drive, with the power consumption and the electromagnetic noise and spectrum of this embodiment.
  • Fig. 9a shows the dependence of the power consumption on the carrier frequency
  • Fig. 9b shows the frequency spectrum comparison of the output current.
  • the rectangular wave linear drive is independent of the carrier frequency, so the characteristics of this method were used as a reference for comparison.
  • the power consumption ratio does not change with the carrier frequency in both the present embodiment and the rectangular wave PWM drive, and is smaller than 0.4 as compared with the linear drive.
  • the integrated circuit is constituted by the MOS FET circuit without using the bipolar transistor circuit.
  • the advantage of MOS FET can be utilized by the PWM drive, and the use of the MOSC analog circuit has been made possible by using the common-centroid layout switch capacitor technology. Therefore, it can be said that the present invention has an optimal circuit configuration on all M0S of the motor driving integrated circuit.
  • the production process power was simplified by the use of all MOS, and the production cost was reduced by about 30% as compared with the conventional bipolar use.
  • FIG. 10 shows a block diagram of a three-phase motor drive system which is a typical embodiment of the present invention.
  • the difference between this embodiment and the above-described second embodiment is that, in the second embodiment, the operation of preventing a through current was performed after the generation of the sine-wave PWM signal, whereas in this embodiment, the generation of the sine-wave PWM signal was performed.
  • the PWM signals for the upper and lower arms are created separately, and the center potential of the triangular wave carrier at the time of creation is offset up and down from the center potential of the sine wave. It is to let.
  • FIG. 10 shows a specific circuit for creating a sine wave PWM signal in this case, and FIG. 12 shows the effect of the offset.
  • FIGS. 11 and 12 illustrate only one phase.
  • offset circuits 106 and 107 are composed of a combination of an operational amplifier and a resistor R. In the case of the upper arm, the midpoint potential V M + V is applied to one end of the operational amplifier.
  • FIG. 13 is a block diagram of a three-phase motor drive system according to a first embodiment of the present invention in which current detection and control functions are added to perform closed-loop control.
  • Reference numeral 55 denotes a current detection unit for detecting the sum of currents of the plunger circuit in proportion to the output current
  • 56 denotes a detection signal.
  • 55 uses an external high-precision resistor. Using this technology, the output current level can be fed back to the input, and the sine wave amplification level can be controlled by comparing it with the control command from the microprocessor, making it possible to accurately set the output current to a constant value. It became possible to suppress the fluctuation of the rotation speed.
  • the maximum voltage of the sine wave PWM signal is equal to the power supply voltage, and the minimum voltage is equal to the source voltage of the lower arm, with exceptions. That is when the power supply voltage is higher than the allowable input voltage of the output transistor.
  • the microprocessor is a separate chip, but if there is a demand for further integration, it can also be a single chip.
  • FIG. 14 is a block diagram of a method of detecting an output current of each phase and feeding it back to an input, thereby enabling control of an output current and detection of an induced voltage.
  • reference numerals 310 to 303 denote output current detection means
  • 304 to 310 denote output current detection results
  • 307 to 309 denote output current control operational amplifiers.
  • the signal output from the sine wave amplitude control means 1 2 is input to the operational amplifiers 3 0 7 to 3 0 9, and the output current detection results 3 0 4, 3 0 5, 3 0 6 Such a signal is applied to each output arm via the PWM signal generating means 16, 17, 18. This makes it possible to provide the motor with the optimum output current for the target rotation speed.
  • FIG. 15 is a block diagram in the case of using a resistor as the current detecting means of FIG. In Fig. 15, only the U-phase circuit is shown to avoid complicating the figure, but the other phases have the same format as the U-phase.
  • Reference number 1 is a spindle motor for a 3.5-inch hard disk drive (interphase inductance 3 mH, interphase resistance 6.6 ⁇ , number of poles 8, rated rotation speed 450 Orp m, rated voltage 12 V) , 19, 21, 23 are P channel insulated gate transistors (on-resistance 1.0 ⁇ ) that are the upper arm of each phase output circuit, and 20, 22 and 24 are the N channels that are the lower arm It is an insulated gate transistor (on resistance is 0 ⁇ ).
  • 3 1 1 to 3 13 are resistors for detecting the current of each phase (resistance 0.1 ⁇ )
  • 3 14 is an operational amplifier for detecting the voltage drop in the detection resistor 3 11
  • 3 15 is an output circuit.
  • a drive circuit 13 for driving is a sawtooth wave generation circuit (PWM frequency; 156 kHz) for PWM control.
  • PWM frequency 156 kHz
  • a resistor external to the IC is used here, and in order to reduce the number of components, a resistor built in the IC chip and a bonding wire resistance during packaging can be used.
  • Vout Vbemf + I- (r + wL) + IR Formula (1)
  • the output current I is sufficiently reduced by controlling the input signal
  • Vout can be approximated by the following equation.
  • the output voltage can be detected by passing the output voltage through a low-pass filter to remove harmonic components.
  • FIG. 16 is a block diagram of a motor drive system when a current mirror is used as an output circuit. Like FIG. 15, FIG. 16 shows only the U-phase circuit to avoid complicating the figure.
  • Reference numerals 401 and 402 are current mirrors for the upper and lower arms, respectively.
  • 403.404 is current detection means
  • 405 and 406 are PWM signal generation means
  • 407 and 408 are current mirrors 401 and 402 on and off.
  • 409 is a three-differential amplifier for generating an input signal of each phase current mirror
  • 410 is a matrix circuit for shaping the induced voltage into an input signal to the three-differential amplifier 409.
  • the output of FIG. 16 is shown in more detail in FIG.
  • the comparator 501 is used as the current detection means 404, and it is determined whether or not the output current is at the target level by comparison with an arbitrary reference voltage 502. The result is transmitted to the PWM signal generating means 406, and a PWM signal 504 is generated by a combination with the clock 503 of the PWM reference frequency. With this signal 504, the gate of the transistor 505, which is the switch 408 for turning on and off the current mirror 402, is driven. Tran When the register 505 is on, the control current I 2 from the three-differential amplifier 409 is not input to the current mirror 402, so that the current mirror 402 is turned off. On the other hand, when the transistor 505 is off, the current mirror 402 is on.
  • the transistors 508 and 509 forming the current mirror 402 have a ratio of gate width / gate length of about 1: 100. For example, if the current flowing through 508 is 1 mA, 1 A flows through the output 509. This is a setting for realizing the current required when starting the motor with a small input current.
  • Fig. 18 shows the behavior of the input / output voltage and current to the current mirror.
  • Fig. 18 shows the PWM signal 504 of the current mirror 4002 when the motor is loaded, the output voltage 601 of the power mirror 4002, and the output current 600 flowing through one phase of the motor. 2 is shown.
  • the PWM signal 504 is between the power supply voltage Vcc and the current mirror is off, the output voltage is near Vcc and no output current flows.
  • the gate voltage 600 changes to zero, the current mirror changes from off to on, and the output voltage temporarily drops to near zero. This is because the output current cannot flow rapidly because the load is inductance, and the output transistor operates in the unsaturated region.
  • the output voltage 6001 starts to rise slightly, and then rises sharply when the operation changes from the non-saturation to the saturation region.
  • the output current 602 increases substantially according to the load time constant RZL.
  • the output current reaches a level determined by the current mirror ratio, the output voltage becomes constant.
  • the input is turned off again, the output current flows into the body diode of the upper arm and becomes a return current to discharge the energy stored in the inductance.
  • the output voltage instantaneously increases above the power supply voltage, and then decreases according to the load time constant.
  • the input is turned off by detecting that the target voltage has become 502.
  • detecting the output voltage 601 has the same meaning as detecting the output current.
  • the point of operation of this circuit is when the output voltage 6001 enters the saturation region from the non-saturation region.
  • One step is to detect the output result of the comparator 501, and to switch the PWM signal 504 from off to on by the clock signal 503.
  • FIG. 19 shows the respective terminal voltages of the PWM signal generating means 406 in FIG.
  • reference numeral 601 is the output voltage of the current mirror
  • 502 is the target voltage
  • 701 is the output of the comparator 501
  • 702 to 704 are the NAND gates 51.
  • Reference numeral 2 denotes an input / output signal
  • reference numeral 503 denotes a PWM frequency clock signal
  • reference numeral 601 denotes an output signal of the flip-flop 513
  • reference numeral 602 denotes an output current of the current mirror.
  • a signal of 701 is obtained.
  • the signal obtained by inverting the result is 70 2
  • the signal obtained by delaying the signal for a certain time by the RC circuits 51 0 and 51 1 is 70 3.
  • the resistance value of 510 is 100 kQ
  • the capacitance value of 511 is 10 pF
  • the delay time is about 1 ms.
  • FIG. 20 shows output characteristics when the spindle motor is rotated according to the present embodiment.
  • 52 forces, 54 and 54 are the induced voltages of each phase
  • 801 to 803 are the output voltages of the three-acting amplifier for driving the upper arm
  • 804 to 806 are the lower arm drive.
  • the output current 602 rises and falls more slowly than before.
  • the rise and fall of the output current in the related art is about 2 AZm, but in the present embodiment, about 0.5 A / m second is realized.
  • the electrical and acoustic noise at the time of phase switching was significantly improved. Therefore, similarly to the effect described in the first embodiment, a driving method that is equivalent to the conventional one with respect to the switching noise and consumes low power is enabled.
  • the present invention it becomes possible to drive a sensorless brushless motor with lower power consumption and lower noise than before.
  • the power consumption of the power source was reduced by about 60% or more, and the harmonic components of electromagnetic noise were significantly reduced.
  • the manufacturing cost was reduced by about 30%.

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Abstract

Le circuit d'attaque d'un moteur triphasé (1) génère un signal sinusoïdal de modulation d'impulsions en largeur au moyen d'une tension induite (11) et extrait un courant sinusoïdal par des bras d'attaque supérieurs et inférieurs (2, 3, 4, 5, 6 et 7) en fonction des signaux de modulation d'impulsions en largeur. Un filtre (10) sélectionne la tension induite (11) à partir d'une tension de sortie (9) et envoie la tension (11) à un régulateur d'amplitude sinusoïdale (12) et à un tachymètre (14). Un microprocesseur (15) mesure la vitesse de rotation du moteur (1) en se servant du signal 'vitesse' délivré par le tachymètre (14) et régule l'amplitude de la tension induite (11) en se servant du signal de régulation d'amplitude d'accélération et de décélération. Les générateurs de modulation d'impulsions en largeur produisent ensuite des signaux sinusoïdaux de modulation d'impulsions en largeur à l'aide d'une porteuse à onde triangulaire (13). Afin d'éviter la génération du courant traversant au niveau de la sortie, sont montés des circuits de blocage (28, 29 et 30) comprenant des commutateurs (35 et 36) et des résistances (37 et 38). On empêche également le courant traversant par un décalage de la porteuse (13). Tous les circuits analogiques du circuit intégré sont constitués de circuits MOS de façon à simplifier la processus. Grâce à ce système, la consommation électrique d'un moteur sans balai ne comportant pas de détecteur est réduite de moitié ou plus, et d'autre part, le bruit électromagnétique du moteur est considérablement réduit. De plus, puisque les circuits analogiques sont constitués de circuits à effet de champ MOS, les coûts de fabrication du circuit intégré sont également réduits.
PCT/JP1995/001435 1994-08-11 1995-07-19 Systeme d'attaque de moteur WO1996005650A1 (fr)

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JP18924694 1994-08-11
JP6/189246 1994-08-11

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JP2002084772A (ja) * 2000-09-08 2002-03-22 Rohm Co Ltd ブラシレスモータ用駆動制御装置
JP2003348874A (ja) * 2002-05-24 2003-12-05 Toshiba Corp 三相モータ駆動装置
JP2006042423A (ja) * 2004-07-23 2006-02-09 Rohm Co Ltd ピークホールド回路、それを備えるモータ駆動制御回路、及びそれを備えるモータ装置
WO2009054352A1 (fr) * 2007-10-23 2009-04-30 Daikin Industries, Ltd. Dispositif de détection de courant, appareil de conditionnement d'air, système de calcul de constante de correction et procédé de calcul de constante de correction

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Cited By (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2001282046A (ja) * 2000-04-03 2001-10-12 Canon Inc 画像形成装置及びそのモータ駆動制御回路
JP4557360B2 (ja) * 2000-04-03 2010-10-06 キヤノン株式会社 画像形成装置及びそのモータ駆動制御回路
JP2002084772A (ja) * 2000-09-08 2002-03-22 Rohm Co Ltd ブラシレスモータ用駆動制御装置
JP4674942B2 (ja) * 2000-09-08 2011-04-20 ローム株式会社 ブラシレスモータ用駆動制御装置
JP2003348874A (ja) * 2002-05-24 2003-12-05 Toshiba Corp 三相モータ駆動装置
JP2006042423A (ja) * 2004-07-23 2006-02-09 Rohm Co Ltd ピークホールド回路、それを備えるモータ駆動制御回路、及びそれを備えるモータ装置
JP4641751B2 (ja) * 2004-07-23 2011-03-02 ローム株式会社 ピークホールド回路、それを備えるモータ駆動制御回路、及びそれを備えるモータ装置
WO2009054352A1 (fr) * 2007-10-23 2009-04-30 Daikin Industries, Ltd. Dispositif de détection de courant, appareil de conditionnement d'air, système de calcul de constante de correction et procédé de calcul de constante de correction
US8400083B2 (en) 2007-10-23 2013-03-19 Daikin Industries, Ltd. Current detecting device, air conditioning apparatus, correction constant calculating system and correction constant calculating method
CN101849349B (zh) * 2007-10-23 2013-05-15 大金工业株式会社 电流检测装置、空气调节装置、修正常数计算系统及修正常数计算方法

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