WO1994010806A1 - Procede et appareil de mise en phase de circuits video numeriques a effet de volant - Google Patents

Procede et appareil de mise en phase de circuits video numeriques a effet de volant Download PDF

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Publication number
WO1994010806A1
WO1994010806A1 PCT/US1993/010627 US9310627W WO9410806A1 WO 1994010806 A1 WO1994010806 A1 WO 1994010806A1 US 9310627 W US9310627 W US 9310627W WO 9410806 A1 WO9410806 A1 WO 9410806A1
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WIPO (PCT)
Prior art keywords
phasing
counter
phase
flywheel
signal
Prior art date
Application number
PCT/US1993/010627
Other languages
English (en)
Inventor
Jan S. Wesolowski
Original Assignee
Ampex Corporation
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
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Publication date
Application filed by Ampex Corporation filed Critical Ampex Corporation
Publication of WO1994010806A1 publication Critical patent/WO1994010806A1/fr

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N9/00—Details of colour television systems
    • H04N9/79—Processing of colour television signals in connection with recording
    • H04N9/80—Transformation of the television signal for recording, e.g. modulation, frequency changing; Inverse transformation for playback
    • H04N9/808—Transformation of the television signal for recording, e.g. modulation, frequency changing; Inverse transformation for playback involving pulse code modulation of the composite colour video-signal
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N9/00—Details of colour television systems
    • H04N9/79—Processing of colour television signals in connection with recording
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04N—PICTORIAL COMMUNICATION, e.g. TELEVISION
    • H04N9/00—Details of colour television systems
    • H04N9/79—Processing of colour television signals in connection with recording
    • H04N9/80—Transformation of the television signal for recording, e.g. modulation, frequency changing; Inverse transformation for playback
    • H04N9/804—Transformation of the television signal for recording, e.g. modulation, frequency changing; Inverse transformation for playback involving pulse code modulation of the colour picture signal components

Definitions

  • This invention relates generally to a method and apparatus for phase change detection and phasing for the sync flywheel circuits of a digital component video input interface.
  • the input video interface of a digital video tape recorder is required to produce several types of signals representative of the timing of the incoming video data.
  • Several types of timing signals have to be derived from the incoming digital video signal by the input interface. These timing signals need to be produced by so called flywheel circuits even if the input signal disappears or is not continuous. This is done by flywheel circuits consisting of a phase locked oscillator, counters and decoders.
  • flywheel circuits consisting of a phase locked oscillator, counters and decoders.
  • the flywheel circuits have to be initially phased to the synchronization components of the incoming digital input video signal and rephased every time a change in the phase relationship between flywheeled signals and the input video signal is detected.
  • a flywheel counter is periodically loaded by each phasing pulse with a phase value stored in the phase register, thereby constantly updating the flywheel counter to the desired phase represented by the value in the phase register. Detecting the phase change was therefore not needed for the purpose of phasing the flywheel circuits, but sometimes it was done for another purpose, for example, detection of so called "hot switch" in video synchronizers and certain designs of time base correctors. Whenever it was required, it was done by circuits dedicated to this function alone.
  • a circuit detecting change of phase relationship between the digital input video signal and flywheeled sync signals uses an equality detector for comparing the state of a flywheel counter to the state of a phase register. Phasing of the sync flywheel circuit is accomplished by setting a flywheel counter to a predetermined number (phase word) at the time when the corresponding riming reference code, or synchronization portion of the incoming data, is detected in the digital component video signal.
  • phase word is preloaded by a microprocessor in a phase register, from which, at phasing time, it is copied into the flywheel counter.
  • a rate register is provided for storing a minimum number, preloaded by a microprocessor, to which the counter is reset after it reaches its maximum and produces a carry. After resetting, the counter continues counting up until it reaches its maximum again. The above described cycle is repeated all the time, if phasing is disabled.
  • a two input multiplexer is provided for transferring the contents of one of the rate register and phase register to the counter on command of a load control, initiahzed by the phasing pulses to provide a select output to the multiplexer and a load enable output to the counter.
  • the microprocessor For purposes of phasing the counter and subsequent detection of phase shift, the microprocessor loads the phase register with a value representing the desired phase. At the time when the phasing pulse arrives, the phase value is loaded into the counter. Soon after, the microprocessor disables the phasing and the counter resumes its normal cycle of counting up to the maximum number and then automatically resets to the minimum number as determined by the contents of the rate register, with the equality detector then making a comparison between the contents of the counter and phase register. The result of this comparison is clocked into a latch on coincidence with a phasing pulse. If there is an inequality, the microprocessor is notified. In response, the microprocessor checks the parameters of the incoming data signal to determine if the data clock is present, if the data sync is present, if the error rates are low, and, if so, re-phase the flywheel.
  • Figures IA and IB collectively referred to as Figure 1, show a block diagram of a component input deformatter system incorporating the system for providing noise immunity for a digital video input interface of a digital video recorder according to the invention
  • Figures 2A, 2B and 2C collectively referred to as Figure 2, show a block diagram of the system for providing noise immunity for a digital video input interface of a digital video recorder
  • Figure 3 is a block diagram of the clock presence detector used in the system of Figure 1; and Figure 4 is a modified block diagram of a flywheel circuit phasing arrangement with more detail of the phase change detector for the flywheel circuits of the system of Figure 1 , which diagram, in part, is similar to the block diagram of Figure 2B.
  • FIG. 10 a block diagram of a component input deformatter system, generally designated 10, incorporating the system for detecting stability of a digital component video signal for a digital video input interface of a digital video recorder according to the invention.
  • the input deformatter system 10 is the main part of the record side of the video application layer of a video tape recorder.
  • the major circuits of the system 10 include an input selector, generally designated 14, a control interface, generally designated 20, a video block, generally designated 30, a sync block, generally designated 40, a flywheel block, generally designated 60, a test block, generally designated 70, and a clock presence detector, generally designated 80.
  • an audio data block which forms no part of the invention, is likewise part of the system for processing the audio portion of the incoming signal.
  • the input selector 14 has four inputs 15-18, respectively designated "Serial Input Data”, “Serial Input Clock”, “Parallel Input Data”, and “Parallel Input Clock”.
  • the serial and parallel inputs are 10 lead lines for providing 10 bits of data, while the clock inputs are single leads.
  • the outputs of the input selector 14 include a 10 bit data output bus 12 and a clock line 19.
  • the control interface 20 has five inputs, an 8 bit control data bus 22, a 7 bit control address bus 23, a chip select lead 24, a write strobe 25 and a read strobe 26.
  • the output of the interface 20 provides signals over an internal control bus 28 which communicates with each of the video block 30, the sync block 40, the flywheel block 60, and the test block 70 (which also communicates with the bus 28 via its output).
  • the input selector block 14 receives a serial input clock on line 16 and a parallel input clock on line 18, the selected clock of which is output on line 19 to clock presence detector 80, which outputs an input clock present signal on lead 81.
  • the selected data clock signal on lead 19, at a nominal frequency of 27 MHz, is delivered to an external phase locked loop including a crystal VCO circuit (not shown in Figure 1, but shown in Figure 2B), from which a regenerated 27 MHz clock returns to the deformatter on CLK27 lead 31 for clocking most of the internal system operations. This clock must always be present for proper operation of the System 10.
  • the regenerated 27 MHz clock is also provided over CLK27 lead 31 to each of the video block 30, the sync block 40, and the flywheel block 60.
  • CLK135 and CLK675 Two other clock signals are provided, these being designated CLK135 and CLK675, respectively, which are derived by two stages of divide-by-two circuitry from the CLK27 clock signal and which can be considered part of the flywheel block 60.
  • CLK135 is an output video data clock, of a 13.5 MHz nominal ftequency, and is provided as an input clock signal to the video block 30 over lead 32, to the sync block 40 over lead 42, and to flywheel block 60 over lead 62.
  • Positive going transition of this clock clocks data out CLK675 is a 6.75 MHz nominal frequency output data clock for chroma demultiplexing and is provided as an input over lead 33 to the video block 30.
  • the selected input data is also reclocked inside the input selector 14 with the regenerated 27 MHz clock before further use.
  • the reclocking circuit provides relative insensitivity to the phase relationship between input data and the regenerated clock.
  • the video block 30 extracts only active video from the selected input. It outputs data on three lines 35-37, these signals being, respectively, luminance output, non-blanked luminance output and chroma output This block does not form a part of the present invention and further discussion thereof is unnecessary.
  • the sync block 40 receives data inputs from the input selector 14 over line 12 and control signals over internal control bus 28, with the outputs appearing on lines 43-47 being respectively designated S AV (Start of Active Video), EAV (End of Active Video), Input Horizontal Blanking, Input Vertical Blanking, and Field ID.
  • the sync block 40 extracts the sync information from the incoming data over line 12 and provides phasing information for the flywheel block 60 which produces various sync pulses for use both internally - by the system 10, and externally - by other parts of the video tape recorder.
  • leads 48-51 Other output signals appear on leads 48-51, these signals being, respectively, 525/625 (the TV line standard according to which the input data has been generated), sync present, single bit err (error) and multiple bit err (error); the last three of these signals on leads 49-51 are also provided as inputs to the test block 70, which counts them, and the results of counting are sent to the microprocessor 150 (See Fig. 2A) and are utilized, as will be hereafter explained, to determine if the input signal is free, or relatively free, of disturbances to provide a quiescent period during which the flywheel phasing may be enabled.
  • the deformatter system 10 For making continuous sync information available while input data is absent, the deformatter system 10 provides a sync flywheel function via the flywheel block 60. It is important to emphasize that the sync block 40 extracts sync information from the incoming data so long as there is an incoming signal; however, whether the data is distorted, as a consequence of noise or the like, whether the data is continuous or not, or even if the data disappears, the flywheel block 60 continues to provide sync pulses which are phased to the incoming sync information. For this purpose a frame phasing pulse on line 52, and a horizontal phasing pulse on line 43 are provided from sync block 40 to the flywheel block 60, along with the clock signals on leads 31 and 42, and data from the internal control bus 28.
  • flywheel block 60 Shown in broken lines within the flywheel block 60 are two sub-blocks 60a and 60b, respectively designated frame flywheel 60a and horizontal flywheel 60b, with the frame phasing pulse on lead 52 providing an input to the frame flywheel sub-block 60A and the horizontal phasing pulse on lead 43 providing an input to the horizontal flywheel 60B.
  • these flywheel sub-blocks are generally identical in construction and configuration.
  • the flywheel circuits of flywheel block 60 output a horizontal sync pulse on lead 62, a vertical sync pulse on lead 63, and a frame sync pulse on lead 64, as well as an encoded component sync signal on lead 61 (combined horizontal and vertical sync information), plus two signals made specially for use as servo references: the servo reference frame signal on lead 68, and an encoded servo reference signal (combined 180/200 Hz reference with frame sync information) on lead 67. Timing of the group of flywheeled sync signals relative to the selected input data is determined by phase values preset by the microprocessor and loaded into flywheel counters within flywheel block 60 at a time determined by phasing pulses derived from the input data.
  • the phasing pulses can be enabled or disabled by a microprocessor command.
  • the microprocessor senses the new phase signal on lead 69 from the flywheel block 60 and determines that re-phasing is required, and if the incoming signal is stable, the phasing pulses are enabled for a short time, within which both phasing pulses are received at least once.
  • the encoded servo reference signal is TV standard dependent, that is, the frequency of its basic component is 180 Hertz in case of the 525 standard and 200 Hertz in the case of the 625 standard. It is used by the servo system of the video tape recorder during record, since the scanner and the capstan both have to be synchronized to the incoming video signal and that synchronization is provided through this line.
  • the test block 70 receives as inputs the aforedescribed signals on leads 48-51 from the sync block as well as input clock present signal from the clock presence detector over lead 81.
  • the input of the test block is coupled to receive signals via internal control bus 28 and to output the signals to the same internal control bus.
  • the test block 70 in part, is used to process the appropriate signals to determine the time during which the incoming signal is relatively free of disturbances, at which time the flywheel phasing is enabled.
  • FIG 2 there is shown a modified block diagram of the invention, in which certain of the component blocks depicted therein are grouped together for ease of discussion, although some of the components, such as those shown in the broken line block 120 (in Figure 2A), designated sync separator and stability detector, may be found in more than one of the blocks described in Figure 1.
  • the drawing of Figure 2 is essentially a compilation of parts or components from the block diagram of Figure 1 showing only those components which are essential to the method and apparatus for providing noise immunity for the input interface of a digital video recorder operation.
  • the sync detector 122, the sync error detector and corrector 124 and the sync presence detector 128 are functionally located within the sync block 40, while the data clock presence detector 80 is the clock presence detector 80 shown as a separate component in Figure 1.
  • the single bit error counter 126 and the multiple bit error counter 130 are located within the test block 70 of Figure 1.
  • the outputs of the sync separator and stability detector 120 include input clock present line 81 , sync present line 49, single bit error rate signal on lead 127, and multiple bit error rate signal on lead 129, the signals on the latter two leads resulting from the single bit error signal and multiple bit error signals on leads 50 and 51, respectively, being transmitted to the respective error rate counters 126 and 130.
  • the counters' outputs are read by the microprocessor 150 as "rates".
  • the signal lines 81, 49, 50 and 51 are designated on Figure 1 , with all being output from the sync block 40, except for the input clock present line 81 , which is output from the clock presence detector 80.
  • FIG. 2B A second portion of the block diagram is enclosed in broken lines in Figure 2B, this portion 60A being generically designated "horizontal flywheel circuit".
  • the blocks identified as the horizontal flywheel counter 134, the horizontal flywheel decoder 135, the horizontal phasing control 136, the horizontal phase register 137 and the horizontal phase change detector 138 are all component parts of the flywheel block 60 of Figure 1, while the flywheel VCO 140 is completely external to the deformatter system, this VCO being that which has heretofore been discussed in conjunction with the block diagram of Figure 1.
  • the system control CPU or microprocessor 150 Also shown in Figure 2 A, and external to the deformatter system 10, is the system control CPU or microprocessor 150.
  • system control bus 160 Interconnecting the various components is a system control bus, generally designated 160 which, on the input side of the microprocessor 150 is designated “read”, and on the output side is designated “write”.
  • the deformatter system 10 of Figure 1 is implemented on an ASIC (application specific integrated circuit) while the microprocessor 150 is external to the system.
  • the system control bus 160 shown in Figure 2 represents the internal control bus 28 of that ASIC as well as the bus between the deformatter system 10 and the microprocessor 150.
  • FIG. 2C A third portion of the block diagram is enclosed in broken lines in Figure 2C, this portion 60A being generically designated frame flywheel circuit.
  • the blocks identified as the frame flywheel counter 134a, the frame flywheel decoder 135a, the frame phasing control 136a, the frame phase register 137a and the frame phase change detector 138a are all component parts of the flywheel block 60 of Figure 1.
  • the horizontal sync signal on lead 62 is provided to the frame flywheel circuit 60A.
  • timing signals For operational purposes, several types of timing signals have to be derived from the incoming digital video signal on bus 12 by the input interface of a digital video recorder. These timing signals need to be produced by the flywheel circuits even if the input signal disappears or is not continuous.
  • the flywheel circuits have to be initially phased to the synchronization components of the input video signal and rephased every time a change is detected in the phase relationship between flywheeled signals and the input video signal. Before the phasing of the flywheel circuits is enabled, it must be determined that the video signal is present and stable.
  • the determination of the presence and stability of the input digital video signal on bus 12 is based on the detected presence of the input data clock (lead 81 ), the detected presence of timing reference code words, and the detected rate of correctable and uncorrectable errors of timing reference code words in the video signal.
  • the presence and stability of the input digital video signal is determined by the system control microprocessor 150 running a program for periodically reading signals from the input data clock presence detector circuit 80, the circuit detecting presence of timing reference code words in the input digital video signal, and the circuits measuring rates of single-bit and multiple-bit errors in detected timing reference code words.
  • the input signal is determined to be present and stable if the input data clock is present, timing reference code words are present, and if both measured error rates do not exceed some experimentally determined threshold values.
  • the digital component video signal appearing on bus 12 from the input selector 14 is transmitted to the sync detector 122 of the sync separator and stability detector 120.
  • the sync separator and stabihty detector 120 generally processes and monitors the incoming signal to determine certain qualities of the signal.
  • An initial check is to determine, via the clock presence detector 80, whether the selected input data clock (from the input selector 14) is present with the result being signified on output line 81 to the system control microprocessor 150.
  • the output of the sync detector 122 is provided to the sync error detector and corrector 124, wherein certain processing occurs, that is, single bit errors are detected and corrected, while multiple bit errors are not corrected, and may or may not be detected depending on the size and kind of errors.
  • the results of the processing in the sync error detector and corrector 124 provide outputs to the sync presence detector 128, the single bit error counter 126 and the multiple bit error counter 130.
  • the sync presence detector 128 a check is made to determine whether the sync is present, with this result being output on lead 49 to the microprocessor 150.
  • the single bit error counter 126 counts the detected occurrences of single bit errors and provides an output indicative of a single bit error rate to microprocessor 150 via a signal on lead 127.
  • the multiple bit error input to the multiple bit error counter 130 provides an output indicative of a multiple bit error rate, via lead 129, to the microprocessor 150.
  • This signal processing on the incoming signal on bus 12 is performed over a predetermined time period prior to output of the corresponding signals.
  • the signal processing operations are being performed on the incoming video signal to, in part, provide a determination as to the error rate present in the sync portion of the incoming data, this information providing an indication as to the quality and stability of the incoming data and the absence of disturbances in the data.
  • Two error checks are performed, for single bit error rate and for multiple bit error rate, with these outputs being provided to the microprocessor 150, along with a signal designated new phase appearing on lead 69 from the phase change detector 138. (The new phase signal on lead 69 is an output of the flywheel block 60 of Figure 1 and its origin will be described in conjunction with Figures 2B and 2C.)
  • the sync separator and stability detector 120 outputs a frame phasing pulse over lead 52 and a horizontal phasing pulse over lead 43 from the sync error detector and corrector 124, each pulse of which is utilized by the respective flywheel circuit, specifically by the phase change detector 138a or 138, respectively. (These phasing pulses are shown as outputs from the sync block 40 to the flywheel block 60 in Figure 1 A).
  • FIGS 2B and 2C show, respectively, the horizontal flywheel circuit 60A and the frame flywheel circuit 60B, both of which are essentially identical, with the exception of the clocking, that is, a VCO 140 is used to clock the horizontal flywheel circuit 60A, while the horizontal sync pulse on lead 62 clocks the frame flywheel counter 134a of the frame flywheel circuit 60B.
  • the horizontal phasing pulse on lead 43 is used as an input to the horizontal phase change detector 138 and the frame phasing pulse on lead 52 is used as an input to the frame phase change detector 138a.
  • Each of these phase change detectors can output a new phase signal on lead 69a or 69b, respectively, the two signals being logically ORed via an OR gate 90.
  • the microprocessor 150 after making a determination as to signal stability of the incoming signal as described, transmits the command and control signal information, via the system control bus 160, to both the horizontal flywheel circuit 60A and the frame flywheel circuit 60B, specifically to the phasing controls 136 and 136a, the phase registers 137 and 137a, and to the flywheel VCO 140.
  • Phasing of the horizontal (and frame) sync flywheel circuit 60A (and 60B) is accomplished by setting the flywheel counter 134 (and 134a) to a predetermined number (phase word via line 139 from the phase register 137 (or 137a)) at the time when the corresponding timing reference code is detected in the digital component video signal on bus 12 and a phasing pulse derived from the timing reference code is delivered to the flywheel circuit.
  • the phase word is usually preloaded by the microprocessor 150 in the phase register 137 (and 137a), from which, at phasing time, it is copied into the flywheel counter 134 (and 134a). Immediately after, the phasing is disabled.
  • phase change detection in the form of an identity or phase change detector 138 (or 138a) connected between the flywheel counter 134 (or 134a) and the phase register 137 (or 137a).
  • Output of the phase change detector 138 (and 138a) is made available to the system control microprocessor 150 as a new phase signal on lead 69, either for periodic reading or as an interrupt request signal.
  • the microprocessor 150 enters a flywheel re-phasing procedure.
  • the digital video signal may be supplied to the input of a digital video tape recorder in the form of parallel data which must be accompanied by a clock. Detecting the presence of that clock is preliminary for detecting whether the incoming digital input video data on line 12 is present.
  • the typical design of an input data clock presence detector is based on the principle of a retriggerable one shot multivibrator, the time constant of which is set to be longer than the period of the clock which triggers it As long as the clock is present, it keeps the multivibrator in its astable state and the detector output in a state corresponding to the clock presence. Disappearance of the clock allows the astable state to expire and the detector output switches to the state corresponding to the absence of the clock.
  • Such a prior art multivibrator can be implemented as analog device or a digital circuit. However, the analog version cannot be used inside of a digital ASIC, and the digital version requires some other clock (reference clock) operating at a higher rate for clocking the digital one shot.
  • a data clock presence detector circuit 80 suitable for implementation inside of a digital ASIC.
  • the clock presence detector 80 has two inputs, one being the selected data clock 19, and the other being the reference clock signal CLK135 (operating at 13.5 MHz) on lead 42, each of which are transmitted through 4 nanosecond pulse formers 150 and 151, respectively.
  • the pulse formers 150 and 151 provide outputs over leads 153 and 154, respectively entitled “set” and “clear” which provide the two inputs to an R/S flip/flop 156.
  • the output of flip/flop 156 is provided as an up/down count command over lead 158 to an up/down counter 160, which is clocked over lead 42 by the reference clock signal CLK135.
  • the counter 160 provides two outputs to a latch 164 over leads 161 and 162, these output signals being designated “at limit” and "MSBi"
  • the latch 164 provides the input clock present signal on output lead 81, which is the signal utilize in the previously described circuits.
  • the clock presence detector 80 utilizes the up/down counter 160 clocked by the reference clock signal CLK135 on lead 42, which operates at a nominal rate which is half of the nominal rate of the input data clock.
  • the R/S flip-flop 156 causes the up/down counter 160 to count up when set via the input on lead 153 from the selected data clock signal on lead 19, and to count down when reset or cleared via the reference clock signal CLK135 on lead 42. In other words, the R/S flip-flop 156 is cleared by the reference clock and set by the input data clock.
  • the counter 160 is configured to count up to its maximum number and stay at that maximum count when continuously clocked up by the continuous sensing of the input or selected data clock on lead 19.
  • the counter when continuously clocked down, the counter reaches its minimum number (zero) and stays at it. If the input or selected data clock on lead 19 is present and has the correct rate, after each reference clock pulse (CLK135 on lead 42) resetting the flip-flop 156 and preparing the counter 160 to count down, there is at least one input or selected data clock pulse on lead 19 that sets the flip-flop 156 and prepares the counter 160 to count up. It is important to note, that due to propagation delays in pulse former 151 and in flip-flop 156, a change on the output of the flip-flop 156 caused by the reference clock is delivered to the up/down counter 160 after the counter is clocked up by the same clock pulse that caused the change.
  • each reference clock pulse thereafter is counted up, and eventually the counter reaches its maximum number indicating presence of the input data clock on output lead 81.
  • the R/S flip-flop 156 remains cleared or reset, whereupon the reference clock pulses (CLK135 on lead 42, via lead 154) are counted down, and eventually the counter 160 reaches its minimum indicating the absence of the input data clock on lead 81.
  • the "at limit" signal is output from the Up/Down counter 160 on lead 161 to the latch 164 when it reaches its maximum or minimum count (zero).
  • the MSBi (Most Significant Bit) output signal on lead 162 from the counter 160 differentiates between the maximum count and zero.
  • the At Limit signal 161 enables latching the value of the MSBi signal 162 in the latch 164 by the clock 42.
  • the latched value is output from latch 164 as the Input Clock Present signal 81.
  • the latch 164 With a maximum count, the latch 164 provides a true output on lead 81, indicating presence of the input data clock, while at a minimum count, the latch 164 provides a false output on lead 81 indicating the absence of the input data clock.
  • each reference clock pulse on lead 42 arrives when the R/S flip/flop 156 has been set by the input data clock pulse, causing the up/down counter 160 to count up, and eventually reach the maximum count indicating input clock presence on lead 81.
  • the up/down counter must be at least two bits long. The longer it is (i.e., greater number of bits), the greater the integration period and response time of the clock presence detector 80.
  • phase change detection circuit is shown in broken lines, designated 138, within a flywheel circuit formed as a larger block enclosed in broken lines and generally designated 170.
  • the block 170 is generally equivalent to the horizontal flywheel circuit 60A of Figure 2B, absent the horizontal flywheel decoder 135, and absent the VCO 140 (although the clock output thereof shows as a CLK27 input on lead 31 in Figure 4).
  • the detector 138 detects a change of phase relationship between the input video signal and the flywheeled sync signals on leads 61-64 (See Figures 1 A and 2B) using an equality detector 190 for comparing the state of the flywheel counter 186 to the state of the phase register 137.
  • the flywheel circuitry 170 has three inputs, these being, respectively, the phasing pulse on lead 43, data from the system control bus 160 (which includes the internal control bus 28) and the regenerated clock signal CLK27 on lead 31 (the VCO 140 output of Fig. 2B). There are three outputs, these being respectively designated "new phase” on lead 69, "carry” on lead 172, and "to flywheel decoder” on line 141, this line corresponding to the output of the flywheel counter 134 in Figure 2B.
  • Data and signals on the system control bus 160 are input to a load control 174, a rate register 176 and the phase register 137.
  • the phasing pulse on lead 43 is provided as a second input to the load control 174 and as an input to the new phase latch 192.
  • the clock signal CLK27 on lead 31 is provided as a clocking input to a counter 186 and the new phase latch 192.
  • the data output from the rate register 176 is provided as a first input over line 175 to a multiplexer 180, the other input of which is received from the phase register 137, via line 139, which data is also provided as an input to an equality detector 190. As indicated by the broken line enclosure, the equality detector 190 plus the latch 192 is identical to the phase change detector 138 of Figure 2B.
  • the load control 174 provides a first output signal, designated “select” to multiplexer 180, via lead 179, and a second signal, designated “load enable” to counter 186, via lead 181.
  • the counter 186 outputs a "carry” signal on lead 172, along with its data value via line 141 to the equality detector 190, as well as to the flywheel encoder, as previously described.
  • FIG 4 is a functional variation of the flywheel circuit 60A of Figure 2B with more details in those blocks of Figure 2B needed for facilitating explanation of the phase change detection and rephasing enablement operation.
  • the flywheel counter block 134 has been expanded to show internal details, such as a rate register 176, and a multiplexer 180.
  • the flywheel counter block 134 also includes part of the load control 174 shown in Figure 4.
  • the load control 174 of Figure 4 also includes the phasing control 136 of Figure 2B, that is, part of the load control 174 is shown in Figure 2B as the phasing control 136.
  • the "carry” signal on lead 172 is the ripple carry output of the counter 186. It is used to reinitialize the counter 186, via load control 174, with the number or value from the rate register 176, from which the counter 186 counts up; that number effectively determining the flywheel rate.
  • the "carry” signal on lead 172 is a functional name given to a generic signal which, for the instant function, is comprised of the horizontal sync signal on lead 62 (See Figs. 1 A and 2B).
  • the Horizontal Sync signal, on lead 62 serves several purposes, one of which is to provide the "carry” signal from the counter 186. It is used internally by the Horizontal Flywheel Circuit, as well as a clock enable input to the Frame Flywheel Circuit, as well as an output from the Input Deformatter ASIC.
  • the microprocessor 150 loads the phase register 137 with a value representing the desired phase. At the time when the horizontal phasing pulse arrives on lead 52, that value is loaded into the counter which normally continues to count from that number up to some maximum number. The loading of this value is determined by the select signal on lead 179 which causes the multiplexer 180 to select the contents of the phase register 137 for transfer to the counter 186 on occurrence of the load enable pulse on lead 133 originated by the phasing pulse on lead 164.
  • the contents of the Rate Register 176 determine the minimum number to which the counter is reset after it reaches its maximum and produces a carry output on lead 172.
  • the carry output is fed to the Load Control block 174, which drives the Select input of the multiplexer 180 via line 179 and forces the multiplexer 180 to select the Rate Register 176 as the source of a number to be loaded into the counter 186.
  • the Load Control 174 produces a load enable pulse to the counter 186 via line 181 causing the next incoming clock pulse from line 31 to finally load the number into the counter 186.
  • the load enable signal on lead 181 ends and counter 186 resumes counting up until it reaches its maximum again.
  • the above described cycle is continually repeated so long as phasing is disabled.
  • the Load Control 174 doesn't respond to the phasing pulses on lead 43. But every phasing pulse on lead 43 serves as a clock enable for the latch 192, which is part of the Phase Change Detector 138.
  • the latch 192 stores the result of a comparison between the counter 186 and the Phase Register 137 produced by the Equality Detector 190 at that time. If the numbers in counter 186 and register 137 are not equal, the New Phase output on lead 69 of latch 192 is seen by the microprocessor 150 as a phasing request.
  • the microprocessor 150 checks the parameters of the incoming data signal as previously described, and, if the data clock is present, the data sync is present and the sync error rates are low, it enables the flywheel phasing by sending an appropriate command to the Load Control 174 via system control bus 160.
  • the Load Control 174 produces Select signal on lead 179 to the multiplexer 180, which makes the multiplexer select the output of the Phase Register 137 as a source of the number to be loaded into the counter 186.
  • the Load Control 174 produces a load enable pulse to the counter 186 via line 181 causing the next coming clock pulse from line 31 to finally load the number into the counter. Soon after, the load enable 181 ends and counter 186 resumes its normal counting cycle.

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  • Engineering & Computer Science (AREA)
  • Multimedia (AREA)
  • Signal Processing (AREA)
  • Television Signal Processing For Recording (AREA)

Abstract

La détection de changements de phase permet une mise en phase à effet de volant lorsqu'une mise en phase est requise. Un changement de phase détecté entre un signal vidéo numérique d'entrée et des signaux de synchronisation à effet de volant utilise un détecteur d'égalité pour comparer l'état d'un compteur à effet de volant à l'état d'un registre de phase. On met en phase le circuit à effet de volant de synchronisation en ajustant un compteur à effet de volant sur un numéro prédéterminé (mot de passe) au moment où le code correspondant de référence de synchronisation, ou la partie de synchronisation des données entrantes, est détecté dans le signal vidéo numérique constitutif. Le résultat de la comparaison entre le compteur à effet de volant et le registre de phase est cadencé dans un dispositif de verrouillage lors d'une coïncidence avec une impulsion de mise en phase. En cas d'inégalité, un microprocesseur vérifie les paramètres du signal de données entrantes afin de déterminer si l'horloge de données est présente, si la synchronisation des données est présente et si les taux d'erreur sont faibles; si c'est le cas le microprocesseur remet en phase le volant.
PCT/US1993/010627 1992-11-05 1993-11-05 Procede et appareil de mise en phase de circuits video numeriques a effet de volant WO1994010806A1 (fr)

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US97219892A 1992-11-05 1992-11-05
US07/972,198 1992-11-05

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Citations (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4122487A (en) * 1977-01-28 1978-10-24 Ampex Corporation Precision phase controlled clock for sampling television signals
US4301466A (en) * 1980-02-01 1981-11-17 Ampex Corporation Fast acting phase shifting apparatus for use in digital sampling systems
GB2117582A (en) * 1982-03-31 1983-10-12 British Broadcasting Corp Synchronising circuit for phase-locking repetitive signals, e.g. television signals
GB2140239A (en) * 1983-05-18 1984-11-21 Sony Corp Television frame signal synchronizing circuits
US4752837A (en) * 1983-10-26 1988-06-21 Deland Jr Robert S Data synchronizer for use with a variable rate input source
US4797730A (en) * 1987-04-10 1989-01-10 Ampex Corporation Method and apparatus for controlling the sampling phase of an analog color television signal
GB2226733A (en) * 1988-12-31 1990-07-04 Samsung Electronics Co Ltd Digital recording of colour television signals
WO1991003909A1 (fr) * 1989-09-07 1991-03-21 Advanced Television Test Center, Inc. Convertisseur de signaux numeriques de formats de television a haute definition multiples

Patent Citations (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4122487A (en) * 1977-01-28 1978-10-24 Ampex Corporation Precision phase controlled clock for sampling television signals
US4301466A (en) * 1980-02-01 1981-11-17 Ampex Corporation Fast acting phase shifting apparatus for use in digital sampling systems
GB2117582A (en) * 1982-03-31 1983-10-12 British Broadcasting Corp Synchronising circuit for phase-locking repetitive signals, e.g. television signals
GB2140239A (en) * 1983-05-18 1984-11-21 Sony Corp Television frame signal synchronizing circuits
US4752837A (en) * 1983-10-26 1988-06-21 Deland Jr Robert S Data synchronizer for use with a variable rate input source
US4797730A (en) * 1987-04-10 1989-01-10 Ampex Corporation Method and apparatus for controlling the sampling phase of an analog color television signal
GB2226733A (en) * 1988-12-31 1990-07-04 Samsung Electronics Co Ltd Digital recording of colour television signals
WO1991003909A1 (fr) * 1989-09-07 1991-03-21 Advanced Television Test Center, Inc. Convertisseur de signaux numeriques de formats de television a haute definition multiples

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
PERRY R.: "HDTV Digital Frame Recorder", SMPTE JOURNAL, vol. 100, no. 1, 30 January 1991 (1991-01-30), SCARSDALE, NY US, pages 10 - 13, XP000173301 *

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