US6373734B1 - Power factor correction control circuit and power supply including same - Google Patents

Power factor correction control circuit and power supply including same Download PDF

Info

Publication number
US6373734B1
US6373734B1 US09/663,547 US66354700A US6373734B1 US 6373734 B1 US6373734 B1 US 6373734B1 US 66354700 A US66354700 A US 66354700A US 6373734 B1 US6373734 B1 US 6373734B1
Authority
US
United States
Prior art keywords
input terminal
feedback amplifier
responsive
output terminal
voltage
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Fee Related
Application number
US09/663,547
Other languages
English (en)
Inventor
Robert M. Martinelli
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Artesyn Embedded Technologies Inc
Original Assignee
Artesyn Technologies Inc
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Artesyn Technologies Inc filed Critical Artesyn Technologies Inc
Priority to US09/663,547 priority Critical patent/US6373734B1/en
Assigned to ARTESYN TECHNOLOGIES, INC. reassignment ARTESYN TECHNOLOGIES, INC. ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: MARTINELLI, ROBERT M.
Priority to PCT/US2001/028919 priority patent/WO2002023694A2/fr
Priority to JP2002527026A priority patent/JP2004509587A/ja
Priority to AU2001290997A priority patent/AU2001290997A1/en
Priority to EP01971066A priority patent/EP1364445A2/fr
Publication of US6373734B1 publication Critical patent/US6373734B1/en
Application granted granted Critical
Assigned to FLEET CAPITAL CORP. reassignment FLEET CAPITAL CORP. SECURITY INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: ARTESYN TECHNOLOGIES, INC.
Assigned to ARTESYN TECHNOLOGIES, INC. reassignment ARTESYN TECHNOLOGIES, INC. ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: BANK OF AMERICA, N.A.
Anticipated expiration legal-status Critical
Expired - Fee Related legal-status Critical Current

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
    • Y02P80/00—Climate change mitigation technologies for sector-wide applications
    • Y02P80/10—Efficient use of energy, e.g. using compressed air or pressurized fluid as energy carrier

Definitions

  • the present invention relates generally to power electronics and, more particularly, to power factor correction (PFC) control circuits.
  • PFC power factor correction
  • the average power obtained from an AC line supply through an AC-to-DC power supply is always less than the product of the RMS (root mean square) voltage and the RMS current.
  • the ratio of the average power to the product of the RMS voltage and the RMS current is known as the power factor.
  • a converter having a power factor of 70% means that the power drawn from the line supply is 70% of the product of the voltage and current in the line and, thus, only 70% of what could be obtained with a unity power factor.
  • PFC power factor correction
  • variable, rectified sine wave reference is coupled to one input of an amplifier, and the other input is coupled to the rectified AC input current.
  • the current feedback loop is arranged so that the output of the amplifier will cause the boost converter to operate in a way to force the current to follow the rectified sine wave reference. That is, if the instantaneous input current deviates from the rectified sine wave reference, the output of the amplifier drives the converter to decrease the deviation.
  • the rectified sine wave reference is sinusoidal and in phase with the input voltage
  • the input current is also sinusoidal and in phase with the input voltage to realize PFC. Accordingly, if the load at the output increases, a resulting decrease in output voltage will cause the error signal to increase and, via the analog multiplier, cause the rectified sine wave reference to increase. This is turn will force the converter input current to increase, which will cause the output voltage to recover to the desired value.
  • the boost converter may be over-designed to, for example, include a larger inductor or a higher-rated FET.
  • the present invention is directed to a power factor correction circuit for a boost power supply.
  • the boost power supply includes a boost converter responsive to a rectified AC line voltage
  • the power factor correction includes: a voltage feedback amplifier having a first input terminal responsive to an output voltage of the boost converter; a switching multiplier circuit having a first input terminal connected to an output terminal of the voltage feedback amplifier and a second input terminal responsive to the rectified AC line voltage; a current feedback amplifier having a first input terminal connected to an output terminal of the switching multiplier circuit and having a second input terminal responsive to an input current of the boost converter; and a pulse width modulator control circuit having an input terminal connected to an output terminal of the current feedback amplifier and having an output terminal for connection to a pulse width modulated switch of the boost converter.
  • the power factor correction circuit includes: a first multiplier circuit having a first input terminal responsive to an input current of the boost converter and a second input terminal responsive to the rectified AC line voltage; a power feedback amplifier having an input terminal connected to an output terminal of the second multiplier circuit; a second multiplier circuit having a first input terminal connected to an output terminal of the power amplifier and a second input terminal responsive to the rectified AC line voltage; a current feedback amplifier having a first input terminal connected to an output terminal of the switching multiplier circuit and having a second input terminal responsive to the input current of the boost converter; and a pulse width modulator control circuit having an input terminal connected to an output terminal of the current feedback amplifier and having an output terminal for connection to a pulse width modulated switch of the boost converter.
  • the power factor correction circuit includes: a voltage feedback amplifier having a first input terminal responsive to an output voltage of the boost converter; a first switching multiplier circuit having a first input terminal responsive to an input current of the boost converter and a second input terminal responsive to the rectified AC line voltage; a power feedback amplifier having an input terminal connected to an output terminal of the first switching multiplier circuit; a second switching multiplier circuit having a first input terminal connected to both an output terminal of the voltage feedback amplifier and an output terminal of the power feedback amplifier, a second input terminal responsive to the rectified AC line voltage, and an output terminal, wherein only one of the output terminal of the voltage feedback amplifier and the output terminal of the power feedback amplifier is operatively connected to the first input terminal of the switching multiplier circuit; a current feedback amplifier having a first input terminal connected to the output terminal of the second switching multiplier circuit and having a second input terminal responsive to the input current of the boost converter; and a pulse width modulator control circuit having an input terminal connected to an output terminal of the current feedback amplifier and having an output
  • the present invention is directed to a boost power supply including: a full-wave rectifier circuit coupled to an AC power source; a boost converter connected to the full-wave rectifier circuit for converting a rectified AC input voltage produced to a DC output voltage, the boost converter having a pulse width modulated switch; a pulse width modulator control circuit having an output terminal connected to a control terminal of the pulse width modulated switch of the boost converter; a voltage feedback amplifier having a first input terminal responsive to an output voltage of the boost converter; a first switching multiplier circuit having a first input terminal connected to an output terminal of the voltage feedback amplifier and a second input terminal responsive to the rectified AC line voltage; and a current feedback amplifier having a first input terminal connected to an output terminal of the switching multiplier circuit, a second input terminal responsive to an input current of the boost converter, and an output terminal connected to an input terminal of the pulse width modulator circuit.
  • the power supply additionally includes a second switching multiplier circuit having a first input terminal responsive to the input current of the boost converter and a second input terminal responsive to the rectified AC line voltage, and a power feedback amplifier having an input terminal connected to an output terminal of the second multiplier circuit and an output terminal connected to the first input terminal of the first switching multiplier circuit, wherein only one of the output terminal of the voltage feedback amplifier and the output terminal of the power feedback amplifier is operatively connected to the first input terminal of the switching multiplier circuit.
  • the present invention provides an advantage in comparison with prior art power factor correction techniques because it is capable of more precisely limiting the input power. Using the PFC technique of the present invention, it is reasonable to expect the power limit accuracy to be on the order or +/ ⁇ 5%. In addition, the improved accuracy of the switching multiplier permits the use of less expensive components in the boost power supply.
  • FIG. 1 is a combination block/schematic diagram of a boost power supply according to one embodiment of the present invention
  • FIG. 2 is a combination block/schematic diagram of the PWM control circuit and the PFC control circuit of the boost power supply of FIG. 1 according to one embodiment of the present invention
  • FIG. 3 is a schematic diagram of a current reference multiplier circuit of the PFC control circuit of FIG. 2 according to one embodiment of the present invention
  • FIG. 4 is a schematic diagram of a power multiplier circuit of the PFC control circuit of FIG. 2 according to one embodiment of the present invention
  • FIG. 5 is a schematic diagram of a current reference multiplier circuit of the PFC control circuit of FIG. 2 according to another embodiment of the present invention.
  • FIG. 6 is a schematic diagram of a power multiplier circuit of the PFC control circuit of FIG. 2 according to another embodiment of the present invention.
  • FIG. 7 is a schematic diagram of a circuit for implementing the current source of the power multiplier of FIG. 6 according to one embodiment of the present invention.
  • FIG. 1 is diagram of a boost power supply 10 according to one embodiment of the present invention.
  • the power supply 10 includes an AC power source 12 , an EMI filter 14 , a rectifier circuit 16 , a boost converter circuit 18 , a pulse width modulator (PWM) control circuit 20 , and a power factor correction (PFC) control circuit 22 .
  • the power supply 10 illustrated in FIG. 1 may be used to provide a regulated DC voltage output (V out ) of, for example, 400V from the AC voltage supplied by the AC power source 12 .
  • V out regulated DC voltage output
  • the AC power source 12 may supply a sinusoidal voltage signal having a fundamental frequency ⁇ .
  • the fundamental frequency ⁇ may be, for example, 60 Hz.
  • the EMI filter 14 may be connected between the AC power source 12 and the rectifier circuit 16 , as illustrated in FIG. 1, and may filter unwanted noise.
  • the rectifier circuit 16 may be a full-wave rectification circuit capable of converting the sinusoidal input voltage signal from the AC power source 12 to a voltage waveform in which each half cycle is positive.
  • the fill-wave rectified input voltage is denoted as V ac and is referred to hereinafter as the rectified AC input voltage.
  • the rectifier circuit 16 may include a four-diode bridge rectifier circuit.
  • the boost converter circuit 18 converts the rectified AC input voltage V ac to a DC output voltage (V out ) that may be used to power a load (not shown).
  • the boost converter circuit 18 may include an inductor 24 , a diode 26 , a power switch 28 , a sense resistor 30 , and a capacitor 32 .
  • the inductor 24 , the diode 26 , and the capacitor 32 are connected in series, with the capacitor 32 connected across the output of the boost power supply 10 .
  • the power switch 28 is connected across the diode 26 and the capacitor 32 such that the duty cycle of the power switch 28 controls the voltage across the capacitor 32 (and hence the output voltage V out ).
  • the power switch 28 may be a voltage-controlled switch such as, for example, a field effect transistor (FET), such as an n-type enhancement mode MOSFET as illustrated in FIG. 1 .
  • FET field effect transistor
  • the diode 26 With the voltage at this node increasing, the diode 26 becomes forward-biased, and current flows through the diode 26 to the capacitor 32 . After the energy stored by the inductor 24 has been transferred to the capacitor 32 through the diode 26 , the power switch 28 is closed, thus again causing the diode 26 to be reversed biased and another quantity of energy to stored in the inductor 24 .
  • the duty cycle of the power switch 28 may be modulated to regulate the voltage across the capacitor 32 , and hence the output voltage V out .
  • the duty cycle of the power switch 28 is controlled by the PWM control circuit 20 and the PFC control circuit 22 based on the output voltage V out , the rectified AC input voltage V ac , and the voltage across the sense resistor 30 (V lac ) to provide a desired output voltage with appropriate power factor correction.
  • the sense resistor 30 may be connected in the return loop of the boost converter 18 .
  • the voltage across the resistor 30 may be used by the PFC control circuit 22 , as described further hereinbelow, as a voltage signal proportional to the current of the rectified AC input line (denoted as V lac hereinafter).
  • An amplifier (not shown) may be connected to the sense resistor 30 to provide the appropriate scaling for the voltage signal V lac , as described further hereinbelow.
  • FIG. 2 is a diagram of the PWM control circuit 20 and PFC control circuit 22 of the power supply 10 of FIG. 1 according to one embodiment of the present invention.
  • the PWM control circuit 20 receives an output signal PFC from the PFC control circuit 22 and, based thereon, outputs a pulse width modulated signal (PWM), which is applied to the conduction control terminal of the power switch 28 to thereby control the switching of the power switch 28 and hence the output voltage V out of the power supply 10 .
  • PWM control circuit 20 also outputs a reference voltage signal V ref and a ramp voltage signal V ramp , both of which are used by the PFC control circuit 22 to generate the signal PFC, as described further hereinbelow.
  • the PWM control circuit 20 may be implemented using one of the UC 3800 series of PWM control ICs available from Texas Instruments such as, for example, a UC 3842 PWM control IC.
  • the PFC control circuit 22 includes a voltage feedback amplifier 40 , a power feedback amplifier 42 , a power multiplier 44 , a current reference multiplier 46 , and a current feedback amplifier 48 . These components, as well as the other components of the PFC control circuit 22 described herein, may be implemented using discrete electrical components or, according to another embodiment, may be integrated into a single device or chip. Each of the amplifiers 40 , 42 , 48 may be embodied as, for example, integrating operational amplifiers (op-amps).
  • the current reference multiplier 46 receives the error voltage signal output from either the voltage feedback amplifier 40 or the power feedback amplifier 42 (denoted in FIG. 2 as V error (t)), and multiplies that output with a scaled product of the rectified AC input voltage (K d ⁇ V ac (t)) to produce a rectified sine wave reference corresponding to the product K m ⁇ V error (t) ⁇ V ac (t).
  • the scaled rectified AC input voltage (K d ⁇ V ac (t)) may be realized by connecting a resistor divider circuit (not shown) to the output of the rectifier 16 to provide the appropriate scaling.
  • the rectified sine wave reference produced by the current reference multiplier 46 is input to an inverting input terminal of the current feedback amplifier 48 along with a current feedback signal generated by an adder 49 from the sum of (i) a voltage signal V lac (t) proportional to the rectified AC input current and (ii) the scaled rectified AC input voltage signal (K d ⁇ V ac (t)), which is supplied to the non-inverting input terminal of the current feedback amplifier 48 .
  • the voltage signal V lac (t) proportional to the rectified AC input current may be obtained from the voltage across the sense resistor 30 of the boost converter 18 , as described hereinbefore.
  • the output of the current feedback amplifier 48 may be summed by an adder 50 with (i) the rectified AC input current signal V lac (t) and (ii) the ramp voltage signal V ramp generated by the PWM control circuit 20 , to generate the output signal PFC, which is supplied to the PWM control circuit 20 to generate the appropriate PWM signal to control the duty cycle of the power switch 28 .
  • the voltage feedback amplifier 40 includes a first inverting input terminal responsive to the output voltage V out of the boost converter 18 via a resistor divider circuit 52 including a resistor 54 and a resistor 56 .
  • a second, non-inverting input terminal of the voltage feedback amplifier 40 may be responsive to the reference voltage V ref generated by the PWM control circuit 20 .
  • the voltage feedback amplifier 40 may function as an integrating error amplifier to regulate the output voltage V out of the boost converter 18 to a desired level.
  • the voltage feedback amplifier 40 may have a sufficiently low bandwidth such that the error voltage signal V error does not have any significant ripple at or above a certain frequency, such as 2 ⁇ (e.g., 120 Hz), to minimize harmonic distortion of the input current.
  • This signal is supplied to a low pass filter 58 to attenuate certain frequency components, such as the 2 ⁇ component.
  • the low pass filter 58 may attenuate the 120 Hz component.
  • the remaining DC signal (V pin ) output from the low pass filter 58 is proportional to the average power (P in ) of the rectified AC input signal which is supplied to the boost converter 18 .
  • This signal (V pin ) is supplied to a first, inverting input terminal of the power feedback amplifier 42 .
  • a second, non-inverting input terminal of the power feedback amplifier 42 may be responsive to the reference voltage V ref generated by the PWM control circuit 20 .
  • the power feedback amplifier 42 may function as an integrating error amplifier having an output error signal V error responsive to a difference between the voltage waveform representative of the average power (V pin ) and the reference voltage V ref .
  • the smaller of the instantaneous error signals V error generated by the voltage feedback amplifier 40 and the power feedback amplifier 42 is supplied to the current reference multiplier 46 by way of, for example, series-connected oring diodes 60 , 62 . Accordingly, the amplifier with the lower output controls the error signal feedback at the next stage (i.e., the current reference multiplier 46 and the current feedback amplifier 48 ).
  • the anode terminals of the oring diodes 60 , 62 may be coupled together as illustrated in FIG. 2, and may be biased with an appropriate bias voltage V bias via a resistor 64 .
  • only one of the outputs of the voltage feedback amplifier 40 and the power feedback amplifier 42 may be operatively connected to the input terminal current reference multiplier 46 by a multiplexer such as, for example, an FET multiplexer.
  • the current reference multiplier 46 multiplies the error voltage signal generated by either the voltage feedback amplifier 40 or the power feedback amplifier 42 , as described hereinbefore, by the scaled rectified AC input voltage waveform (K d ⁇ V ac ).
  • the product of this operation is a rectified sine wave reference corresponding to K m ⁇ V error ⁇ V ac , in which the reference amplitude is controlled by the error voltage V error .
  • the reference waveform is in phase with the rectified AC input voltage V ac .
  • the output of the current reference multiplier 46 as described hereinbefore, is input to an inverting input terminal of the current feedback amplifier 48 .
  • the non-inverting input terminal of the current feedback amplifier 48 is responsive to the sum of the rectified AC input current voltage signal V lac (t) waveform and the scaled rectified AC input voltage (K d ⁇ V ac (t)).
  • the output signal from the current feedback amplifier 48 is the current feedback signal V ifb .
  • FIG. 3 is a diagram of the current reference multiplier 46 according to one embodiment of the present invention.
  • the current reference multiplier 46 is a switching multiplier including a comparator 80 .
  • the rectified AC line voltage V ac is connected to the output terminal of the comparator 80 via a resistor divider circuit 82 including, for example, resistors 84 , 86 , 94 and a diode 88 .
  • the current reference multiplier 46 may also include capacitors 90 , 92 and a resistor 96 connected to the output terminal of the comparator 80 .
  • the comparator 80 includes a first input terminal responsive to the error voltage signal V error generated by either the voltage feedback amplifier 40 or the power feedback amplifier 42 , as described hereinbefore.
  • a second input terminal of the comparator 80 may be responsive to the ramp voltage signal V ramp generated by the PWM control circuit 20 .
  • the ramp voltage V ramp is a linear voltage function having a minimum voltage V min , such as zero volts, and a peak voltage of V pk .
  • the period of the ramp voltage signal V ramp is T sw .
  • the output of the comparator 80 is at a high voltage value.
  • the comparator 80 output voltage falls to a minimum value, such as zero volts.
  • the time T on that the output of the comparator 80 is at the high voltage value during each ramp period T sw varies from zero to T sw .
  • the resistor 86 and the diode 88 cause the charge and discharge time constants of the capacitor 90 to be equal. That is, when the output voltage of the comparator 80 is high, the capacitor 90 charges through the resistor 84 and the resistor 94 in parallel. When the output of the comparator 80 is low (e.g., zero volts), the capacitor 90 discharges through the resistor 86 and the resistor 94 in parallel. Thus, if the resistance value of the resistor 86 is chosen equal to the resistance value of the resistor 84 , then both time constants are the same.
  • Multiplication of the error voltage signal V error and the rectified AC input voltage signal V ac by the current reference multiplier 46 is accomplished as follows.
  • the error voltage signal V error is compared to the ramp voltage signal V ramp with the comparator 80 .
  • T sw is the period of the ramp waveform, as discussed hereinbefore.
  • the duty cycle of the of the comparator 80 is dependent upon the characteristics of the ramp voltage function.
  • the capacitor 90 causes the comparator 80 output voltage to be averaged over time.
  • the value of the capacitor 90 may be chosen such that only the high switching frequency is averaged and not the lower line voltage frequency (i.e., 2 ⁇ ).
  • the average voltage at the output of comparator 80 is equal to the duty cycle times the rectified AC input voltage V ac reduced by the resistor divider circuit 82 .
  • R 84 and R 94 are the resistive values of the resistors 84 , 94 respectively.
  • the capacitors 90 , 92 in conjunction with the resistors 84 , 86 , 94 , 96 form a two-stage low pass filter to remove unwanted high frequency components from the rectified sine wave reference waveform.
  • the switching frequency of the comparator 80 may be on the order of 100 kHz while the low frequency signal will be on the order of 120 Hz (i.e., 2 ⁇ ).
  • the values of the components of the two-stage low pass filter may be chosen such that the filtering does not result in any significant phase shift of the rectified waveform.
  • the frequency of both poles of the low pass filter may be, for example, substantially greater than ten times the fundamental frequency ⁇ of the rectified AC line.
  • the poles may be between 2500 Hz and 10 kHz.
  • FIG. 4 is a diagram of the power multiplier 44 according to one embodiment of the present invention.
  • the power multiplier 44 may be a switching multiplier including a comparator 100 , which has a first input terminal responsive to a voltage signal V lac (t) that is proportional to the input current of the boost converter 18 .
  • a second input terminal of the comparator 100 may be responsive to the ramp voltage signal V ramp generated by the PWM control circuit 20 .
  • the output of the comparator 100 is at a high voltage value.
  • the comparator 100 output voltage falls to a minimum value, such as zero volts.
  • the input current voltage signal V lac varies from a minimum value, such as zero volts, to the peak voltage V pk of the ramp voltage signal V ramp
  • the time T on that the output of the comparator 100 is at the high voltage value during each ramp period T sw varies from zero to T sw .
  • the rectified AC line voltage V ac is connected to the output terminal of the comparator 100 via a resistor divider circuit including, for example, resistors 102 , 104 , 110 and a diode 106 .
  • the power multiplier 44 may also include a capacitor 108 connected to the resistor divide circuit.
  • the resistor 104 and the diode 106 cause the charge and discharge time constants of the capacitor 108 to be equal. That is, when the output voltage of the comparator 100 is high, the capacitor 108 charges through the resistor 102 and the resistor 110 in parallel. When the output of the comparator 100 is low (e.g., zero volts), the capacitor 108 discharges through the resistor 104 and the resistor 110 in parallel. Thus, if the resistive value of the resistor 104 is chosen equal to the resistance value of the resistor 102 , then both time constants are the same.
  • the power multiplier 44 multiplies the input current voltage signal V lac (t) and the rectified AC input voltage signal V ac .
  • the product of these two waveforms produces a power estimation waveform which has a DC component equal to the average output power and an AC (i.e., sine wave) component that has a peak-to-peak amplitude of two times the average power.
  • This waveform may be expressed by the following equation:
  • the low pass filter 58 may be used to attenuate, for example, the 2 ⁇ (e.g., 120 Hz) frequency component.
  • the remaining DC signal may be proportional to the average power (P in ). Therefore, the output of the power multiplier 44 , after filtering by the low pass filter 58 , may be compared to the fixed reference voltage V ref by the power feedback amplifier 42 , as described hereinbefore, to generate an error voltage signal used by the current reference multiplier 46 , as described hereinbefore, to control the average input power.
  • power factor correction may be realized more precisely than in comparison with prior art PFC techniques because switching multipliers (i.e., current reference multiplier 46 and power multiplier 44 ) are used, rather than analog multipliers. Accordingly, with the present invention, the precision of the power limit is limited only by basic component tolerances and the amplitude of the ramp voltage signal V ramp . As such, the power limit accuracy may reasonably be on the order of 5% with the present invention.
  • the adder 49 sums the voltage signal V lac (t) which is proportional to the rectified AC line current and the scaled rectified AC voltage signal V ac (t).
  • the output signal of the adder 49 is input to a non-inverting input terminal of the current feedback amplifier 48 , as discussed hereinbefore, thus forcing the output signal of the adder 49 to equal the rectified sine wave reference output from the current reference multiplier 46 and input to the other (inverting) input terminal of the current feedback amplifier 48 .
  • the adder 49 may be eliminated such that the scaled rectified AC voltage signal V ac (t) is not added to the voltage signal V lac (t).
  • FIG. 5 is a diagram of the current reference multiplier 46 according to one such embodiment of the present invention.
  • the first terminal of the comparator 80 is responsive to the rectified AC input voltage V ac via a resistor divider circuit 120 comprising a resistor 122 and a resistor 124 .
  • the output terminal of the comparator 80 is coupled to an error current signal I error current source 126 .
  • the current reference multiplier 46 may multiply the rectified AC input voltage V ac and the error current signal I error to generate the rectified sine wave reference which is proportional the error signal and in phase with the input AC line voltage.
  • the error signal I error current source 126 may be implemented using a transistor (not shown) such as, for example, a bipolar junction transistor (BJT) having its emitter terminal coupled, through a resistor (not shown), to the output of the voltage feedback amplifier 42 and the power feedback amplifier 40 , its collector terminal coupled to the output terminal of the comparator 80 , and its base terminal biased with a fixed voltage.
  • a transistor such as, for example, a bipolar junction transistor (BJT) having its emitter terminal coupled, through a resistor (not shown), to the output of the voltage feedback amplifier 42 and the power feedback amplifier 40 , its collector terminal coupled to the output terminal of the comparator 80 , and its base terminal biased with a fixed voltage.
  • the current reference multiplier 46 of FIG. 5 is responsive to the output of either the voltage feedback amplifier 42 or the power feedback amplifier 44 (via, e.g., the oring diodes 60 , 62 ) and the rectified AC input voltage V ac .
  • FIG. 6 is a diagram of the power multiplier 44 according to one embodiment of the present invention in which the power multiplier 44 multiplies a voltage waveform and a current waveform.
  • the first terminal of the comparator 100 is responsive to the rectified AC input voltage V ac via a resistor divider circuit 130 comprising a resistor 132 and a resistor 134 .
  • the output terminal of the comparator 100 is coupled to an input current signal I in current source 136 .
  • the power multiplier 44 may multiple the rectified AC input voltage V ac and the input current signal I in to generate a waveform (K p ⁇ P(t)) that is proportional to and in phase with the input power to the boost converter 18 .
  • This waveform may be supplied to an inverting input terminal of the power feedback amplifier 42 .
  • FIG. 7 is a schematic diagram of a circuit for implementing the I in current source 136 according to one embodiment of the present invention.
  • the circuit 136 includes an amplifier 140 and a pair of transistors 142 , 144 .
  • the transistors 142 , 144 maybe, for example, bipolar junction transistors (BJTs), such as PNP transistors as illustrated in FIG. 7 .
  • BJTs bipolar junction transistors
  • the input terminals of the amplifier 140 may be responsive to the voltage across the sense resistor 30 (V lac ) of the boost converter 18 (see FIG. 1) via resistors 146 , 148 respectively.
  • the output terminal of the amplifier 140 may be coupled to the control terminals (e.g., base terminals) of both of the transistors 142 , 144 .
  • the emitter terminals of the transistors 142 , 144 may be biased by a bias voltage source 150 via resistors 152 , 154 respectively.
  • the collector terminal of the first transistor 142 may be coupled to an input terminal of the amplifier 140 . According to such a configuration, the current from the collector terminal of the second transistor 144 may supply the I in current signal for the power multiplier 44 of FIG. 6 .
  • the circuit 136 may be alternatively configured to supply the I in current signal.
  • the power multiplier 40 and the power feedback amplifier 42 may be eliminated from the PFC control circuit 22 .
  • the adder 50 may be eliminated from the PFC control circuit 22 such that the rectified AC input current signal V lac (t) is not added to the current feedback voltage signal V ifb prior to being input to the PWM control circuit 20 .
US09/663,547 2000-09-15 2000-09-15 Power factor correction control circuit and power supply including same Expired - Fee Related US6373734B1 (en)

Priority Applications (5)

Application Number Priority Date Filing Date Title
US09/663,547 US6373734B1 (en) 2000-09-15 2000-09-15 Power factor correction control circuit and power supply including same
EP01971066A EP1364445A2 (fr) 2000-09-15 2001-09-13 Circuit de commande de correction de facteur de puissance et bloc d'alimentation le renfermant
JP2002527026A JP2004509587A (ja) 2000-09-15 2001-09-13 力率補正制御回路および同回路を含む電源
AU2001290997A AU2001290997A1 (en) 2000-09-15 2001-09-13 Power factor correction control circuit and power supply including same
PCT/US2001/028919 WO2002023694A2 (fr) 2000-09-15 2001-09-13 Circuit de commande de correction de facteur de puissance et bloc d'alimentation le renfermant

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
US09/663,547 US6373734B1 (en) 2000-09-15 2000-09-15 Power factor correction control circuit and power supply including same

Publications (1)

Publication Number Publication Date
US6373734B1 true US6373734B1 (en) 2002-04-16

Family

ID=24662297

Family Applications (1)

Application Number Title Priority Date Filing Date
US09/663,547 Expired - Fee Related US6373734B1 (en) 2000-09-15 2000-09-15 Power factor correction control circuit and power supply including same

Country Status (5)

Country Link
US (1) US6373734B1 (fr)
EP (1) EP1364445A2 (fr)
JP (1) JP2004509587A (fr)
AU (1) AU2001290997A1 (fr)
WO (1) WO2002023694A2 (fr)

Cited By (75)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6469917B1 (en) * 2001-08-16 2002-10-22 Green Power Technologies Ltd. PFC apparatus for a converter operating in the borderline conduction mode
US20040150380A1 (en) * 2003-01-30 2004-08-05 Santin Jose A. Control of a power factor corrected switching power supply
US20050017699A1 (en) * 2003-07-24 2005-01-27 Stanley Gerald A. Series interleaved boost converter power factor correcting power supply
US20050017695A1 (en) * 2003-07-24 2005-01-27 Stanley Gerald R. Opposed current converter power factor correcting power supply
US20050057237A1 (en) * 2002-01-11 2005-03-17 Robert Clavel Power factor controller
US6912138B2 (en) 2002-09-03 2005-06-28 Artesyn Technologies, Inc. Synchronous rectifier control circuit
US20060039172A1 (en) * 2004-08-23 2006-02-23 International Rectifier Corporation Circuit to improve capacitor hold-up time in a converter circuit
EP1788697A1 (fr) 2005-11-22 2007-05-23 Schneider Toshiba Inverter Europe SAS Dispositif de correction de facteur de puissance pour variateur de vitesse
US20070145957A1 (en) * 2005-12-27 2007-06-28 Linear Technology Corporation Switched converter with variable peak current and variable off-time control
US20080054874A1 (en) * 2006-08-31 2008-03-06 Sriram Chandrasekaran Power Converter Employing Regulators with a Coupled Inductor
US20080150666A1 (en) * 2005-02-23 2008-06-26 Sriram Chandrasekaran Power Converter Employing a Tapped Inductor and Integrated Magnetics and Method of Operating the Same
US20080315852A1 (en) * 2007-06-19 2008-12-25 Chandrasekaran Jayaraman System and Method for Estimating Input Power for a Power Processing Circuit
US20100067270A1 (en) * 2008-09-15 2010-03-18 Power Integrations, Inc. Method and apparatus to reduce line current harmonics from a power supply
US20100091522A1 (en) * 2002-04-18 2010-04-15 Sriram Chandrasekaran Extended E Matrix Integrated Magnetics (MIM) Core
US20100118571A1 (en) * 2008-11-07 2010-05-13 Power Integrations, Inc. Method and apparatus to control a power factor correction circuit
US20100118573A1 (en) * 2008-11-07 2010-05-13 Power Integrations, Inc. Method and apparatus to increase efficiency in a power factor correction circuit
US20100149838A1 (en) * 2006-12-01 2010-06-17 Artusi Daniel A Power System with Power Converters Having an Adaptive Controller
US20100165667A1 (en) * 2006-12-01 2010-07-01 Artusi Daniel A Power System with Power Converters Having an Adaptive Controller
US20100254168A1 (en) * 2009-03-31 2010-10-07 Sriram Chandrasekaran Magnetic Device Formed with U-Shaped Core Pieces and Power Converter Employing the Same
US20100321964A1 (en) * 2009-06-17 2010-12-23 Antony Brinlee Power Adapter Employing a Power Reducer
US20110032738A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. System and method for power factor correction
US20110031940A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. System and method for power factor correction frequency tracking and reference generation
US20110031920A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. Controller and method for estimating, managing, and diagnosing motor parameters
US20110031943A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. System and method for rejecting dc current in power factor correction systems
US20110031914A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. Controller and method for transitioning between control angles
US20110031941A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. System and method for current balancing
US20110031911A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. Power factor correction with variable bus voltage
US20110031942A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. System and method for reducing line current distortion
US20110038179A1 (en) * 2009-08-14 2011-02-17 Xiaoyang Zhang Power Converter Including a Charge Pump Employable in a Power Adapter
US20110133787A1 (en) * 2009-12-07 2011-06-09 Ball Alan R Circuit and method for determining a current
US20110205763A1 (en) * 2006-12-01 2011-08-25 Artusi Daniel A Power Converter with an Adaptive Controller and Method of Operating the Same
CN102315767A (zh) * 2011-04-08 2012-01-11 安伏（苏州）电子有限公司 抗电磁干扰的大功率系统电源
US20120153906A1 (en) * 2010-12-18 2012-06-21 Harriman Paul J Method for scaling a drive signal and circuit therefor
US20120187927A1 (en) * 2011-01-25 2012-07-26 Freescale Semiconductor, Inc. Voltage regulation circuitry and related operating methods
CN103078488A (zh) * 2012-12-29 2013-05-01 东南大学 一种快速瞬态响应的数字功率因数校正控制器
US20130114308A1 (en) * 2011-01-12 2013-05-09 Richtek Technology Corporation Switching Regulator and Control Circuit and Control Method Thereof
CN103166469A (zh) * 2011-12-12 2013-06-19 立锜科技股份有限公司 切换式电源供应器及其控制电路与控制方法
US8502520B2 (en) 2007-03-14 2013-08-06 Flextronics International Usa, Inc Isolated power converter
US20130207632A1 (en) * 2012-02-13 2013-08-15 Gurjit Singh THANDI System and method for improved line transient response in current mode boost converters
US8514593B2 (en) 2009-06-17 2013-08-20 Power Systems Technologies, Ltd. Power converter employing a variable switching frequency and a magnetic device with a non-uniform gap
US8520420B2 (en) 2009-12-18 2013-08-27 Power Systems Technologies, Ltd. Controller for modifying dead time between switches in a power converter
US8520414B2 (en) 2009-01-19 2013-08-27 Power Systems Technologies, Ltd. Controller for a power converter
US8698433B2 (en) 2009-08-10 2014-04-15 Emerson Climate Technologies, Inc. Controller and method for minimizing phase advance current
US8767418B2 (en) 2010-03-17 2014-07-01 Power Systems Technologies Ltd. Control system for a power converter and method of operating the same
US8787043B2 (en) 2010-01-22 2014-07-22 Power Systems Technologies, Ltd. Controller for a power converter and method of operating the same
US8792257B2 (en) 2011-03-25 2014-07-29 Power Systems Technologies, Ltd. Power converter with reduced power dissipation
US8792256B2 (en) 2012-01-27 2014-07-29 Power Systems Technologies Ltd. Controller for a switch and method of operating the same
US8874053B2 (en) * 2011-07-28 2014-10-28 Skyworks Solutions, Inc. Low variation current multiplier
US8976549B2 (en) 2009-12-03 2015-03-10 Power Systems Technologies, Ltd. Startup circuit including first and second Schmitt triggers and power converter employing the same
CN104660027A (zh) * 2013-11-20 2015-05-27 日月元科技(深圳)有限公司 电流总谐波失真率控制电路及其方法
US9077248B2 (en) 2009-06-17 2015-07-07 Power Systems Technologies Ltd Start-up circuit for a power adapter
US9088216B2 (en) 2009-01-19 2015-07-21 Power Systems Technologies, Ltd. Controller for a synchronous rectifier switch
US9099232B2 (en) 2012-07-16 2015-08-04 Power Systems Technologies Ltd. Magnetic device and power converter employing the same
US9106130B2 (en) 2012-07-16 2015-08-11 Power Systems Technologies, Inc. Magnetic device and power converter employing the same
US20150286230A1 (en) * 2014-04-03 2015-10-08 Supertex, Inc. Current Control Circuit for Linear LED Driver
US9190898B2 (en) 2012-07-06 2015-11-17 Power Systems Technologies, Ltd Controller for a power converter and method of operating the same
US9214264B2 (en) 2012-07-16 2015-12-15 Power Systems Technologies, Ltd. Magnetic device and power converter employing the same
US9240749B2 (en) 2012-08-10 2016-01-19 Emerson Climate Technologies, Inc. Motor drive control using pulse-width modulation pulse skipping
US9240712B2 (en) 2012-12-13 2016-01-19 Power Systems Technologies Ltd. Controller including a common current-sense device for power switches of a power converter
US9246391B2 (en) 2010-01-22 2016-01-26 Power Systems Technologies Ltd. Controller for providing a corrected signal to a sensed peak current through a circuit element of a power converter
US9300206B2 (en) 2013-11-15 2016-03-29 Power Systems Technologies Ltd. Method for estimating power of a power converter
US9379629B2 (en) 2012-07-16 2016-06-28 Power Systems Technologies, Ltd. Magnetic device and power converter employing the same
US20160190912A1 (en) * 2014-12-24 2016-06-30 Infineon Technologies Austria Ag System and Method for Measuring Power in a Power Factor Converter
US9634593B2 (en) 2012-04-26 2017-04-25 Emerson Climate Technologies, Inc. System and method for permanent magnet motor control
US10054647B2 (en) 2014-09-15 2018-08-21 Atmel Corporation Fault detection
WO2018232403A1 (fr) * 2017-06-16 2018-12-20 Tae Technologies, Inc. Régulateurs de tension à hystérésis multi-niveau pour modulateurs de tension, et procédés de commande associés
US10807481B1 (en) 2019-03-29 2020-10-20 Tae Technologies, Inc. Module-based energy systems having converter-source modules and methods related thereto
US10821843B2 (en) 2018-03-22 2020-11-03 Tae Technologies, Inc. Systems and methods for power management and control
CN113078810A (zh) * 2021-04-30 2021-07-06 深圳市龙星辰电源有限公司 一种用于医疗开关电源的智能功率因数双重谐波去除校正方法
US20210316621A1 (en) 2020-04-14 2021-10-14 Tae Technologies, Inc. Systems, devices, and methods for charging and discharging module-based cascaded energy systems
US11201563B2 (en) 2017-06-12 2021-12-14 Tae Technologies, Inc. Multi-level multi-quadrant hysteresis current controllers and methods for control thereof
US11794599B2 (en) 2020-05-14 2023-10-24 Tae Technologies, Inc. Systems, devices, and methods for rail-based and other electric vehicles with modular cascaded energy systems
US11845356B2 (en) 2020-09-30 2023-12-19 Tae Technologies, Inc. Systems, devices, and methods for intraphase and interphase balancing in module-based cascaded energy systems
US11888320B2 (en) 2021-07-07 2024-01-30 Tae Technologies, Inc. Systems, devices, and methods for module-based cascaded energy systems configured to interface with renewable energy sources
US11894781B2 (en) 2020-09-28 2024-02-06 Tae Technologies, Inc. Multi-phase module-based energy system frameworks and methods related thereto

Families Citing this family (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP1043769A1 (fr) 1999-04-07 2000-10-11 STMicroelectronics S.r.l. Procédé pour la production d'une plaquette en matériau semi-conducteur comportant des régions monocristallines séparées par des régions de materiau isolant, notamment pour la fabrication de dispositifs de puissance intégrés, et plaquette ainsi obtenue
US9523756B2 (en) * 2012-08-20 2016-12-20 Texas Instruments Incorporated Systems and methods of input power and current measurement
CN107371299B (zh) * 2017-08-29 2023-09-19 无锡麟力科技有限公司 一种高功率因数的线性恒流led驱动电路和驱动方法
CN111756227A (zh) * 2019-03-29 2020-10-09 株式会社村田制作所 功率因数校正方法
CN114362506B (zh) * 2021-12-21 2024-02-09 中国船舶重工集团公司第七0九研究所 一种功率因数校正电路

Citations (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4437146A (en) 1982-08-09 1984-03-13 Pacific Electro Dynamics, Inc. Boost power supply having power factor correction circuit
US4677366A (en) 1986-05-12 1987-06-30 Pioneer Research, Inc. Unity power factor power supply
US4940929A (en) 1989-06-23 1990-07-10 Apollo Computer, Inc. AC to DC converter with unity power factor
US5003454A (en) * 1990-01-09 1991-03-26 North American Philips Corporation Power supply with improved power factor correction
US5006975A (en) * 1989-11-03 1991-04-09 Cherry Semiconductor Corporation Power factor correction circuit
US5446366A (en) 1994-02-08 1995-08-29 Computer Products, Inc. Boost converter power supply with reduced losses, control circuit and method therefor
US5615101A (en) 1994-12-29 1997-03-25 Lucent Technologies Inc. Power converter with high power factor
US5638265A (en) * 1993-08-24 1997-06-10 Gabor; George Low line harmonic AC to DC power supply
US5777866A (en) 1995-05-26 1998-07-07 Lucent Technologies Inc. Power factor control for switched mode rectifiers with improved representing of currents in EMI capacitive elements
US6034513A (en) 1997-04-02 2000-03-07 Lucent Technologies Inc. System and method for controlling power factor and power converter employing the same

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3727053A1 (de) * 1987-08-13 1989-02-23 Siemens Ag Elektronischer multiplizierer
JP2862322B2 (ja) * 1990-03-28 1999-03-03 株式会社日立製作所 電源装置
JPH0828966B2 (ja) * 1993-02-03 1996-03-21 日本電気株式会社 力率改善回路
KR960013948B1 (ko) * 1993-11-16 1996-10-10 삼성전자 주식회사 역률 보정회로
JPH07194112A (ja) * 1993-12-28 1995-07-28 Nec Corp 電源回路
JP3463865B2 (ja) * 1999-06-10 2003-11-05 Ｔｄｋ株式会社 Ａｃーｄｃコンバータ

Patent Citations (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4437146A (en) 1982-08-09 1984-03-13 Pacific Electro Dynamics, Inc. Boost power supply having power factor correction circuit
US4677366A (en) 1986-05-12 1987-06-30 Pioneer Research, Inc. Unity power factor power supply
US4940929A (en) 1989-06-23 1990-07-10 Apollo Computer, Inc. AC to DC converter with unity power factor
US5006975A (en) * 1989-11-03 1991-04-09 Cherry Semiconductor Corporation Power factor correction circuit
US5003454A (en) * 1990-01-09 1991-03-26 North American Philips Corporation Power supply with improved power factor correction
US5638265A (en) * 1993-08-24 1997-06-10 Gabor; George Low line harmonic AC to DC power supply
US5446366A (en) 1994-02-08 1995-08-29 Computer Products, Inc. Boost converter power supply with reduced losses, control circuit and method therefor
US5615101A (en) 1994-12-29 1997-03-25 Lucent Technologies Inc. Power converter with high power factor
US5777866A (en) 1995-05-26 1998-07-07 Lucent Technologies Inc. Power factor control for switched mode rectifiers with improved representing of currents in EMI capacitive elements
US6034513A (en) 1997-04-02 2000-03-07 Lucent Technologies Inc. System and method for controlling power factor and power converter employing the same

Cited By (151)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US6469917B1 (en) * 2001-08-16 2002-10-22 Green Power Technologies Ltd. PFC apparatus for a converter operating in the borderline conduction mode
US20050057237A1 (en) * 2002-01-11 2005-03-17 Robert Clavel Power factor controller
US7006367B2 (en) * 2002-01-11 2006-02-28 Precisionh2 Power Inc. Power factor controller
US8134443B2 (en) 2002-04-18 2012-03-13 Flextronics International Usa, Inc. Extended E matrix integrated magnetics (MIM) core
US20100091522A1 (en) * 2002-04-18 2010-04-15 Sriram Chandrasekaran Extended E Matrix Integrated Magnetics (MIM) Core
US6912138B2 (en) 2002-09-03 2005-06-28 Artesyn Technologies, Inc. Synchronous rectifier control circuit
US20040150380A1 (en) * 2003-01-30 2004-08-05 Santin Jose A. Control of a power factor corrected switching power supply
US7015682B2 (en) 2003-01-30 2006-03-21 Hewlett-Packard Development Company, L.P. Control of a power factor corrected switching power supply
US7403400B2 (en) 2003-07-24 2008-07-22 Harman International Industries, Incorporated Series interleaved boost converter power factor correcting power supply
US20050017699A1 (en) * 2003-07-24 2005-01-27 Stanley Gerald A. Series interleaved boost converter power factor correcting power supply
US20050017695A1 (en) * 2003-07-24 2005-01-27 Stanley Gerald R. Opposed current converter power factor correcting power supply
US6949915B2 (en) 2003-07-24 2005-09-27 Harman International Industries, Incorporated Opposed current converter power factor correcting power supply
US20060039172A1 (en) * 2004-08-23 2006-02-23 International Rectifier Corporation Circuit to improve capacitor hold-up time in a converter circuit
US20080150666A1 (en) * 2005-02-23 2008-06-26 Sriram Chandrasekaran Power Converter Employing a Tapped Inductor and Integrated Magnetics and Method of Operating the Same
US7876191B2 (en) 2005-02-23 2011-01-25 Flextronics International Usa, Inc. Power converter employing a tapped inductor and integrated magnetics and method of operating the same
EP1788697A1 (fr) 2005-11-22 2007-05-23 Schneider Toshiba Inverter Europe SAS Dispositif de correction de facteur de puissance pour variateur de vitesse
US7528587B2 (en) * 2005-12-27 2009-05-05 Linear Technology Corporation Switched converter with variable peak current and variable off-time control
US20070145957A1 (en) * 2005-12-27 2007-06-28 Linear Technology Corporation Switched converter with variable peak current and variable off-time control
US20080054874A1 (en) * 2006-08-31 2008-03-06 Sriram Chandrasekaran Power Converter Employing Regulators with a Coupled Inductor
US8125205B2 (en) 2006-08-31 2012-02-28 Flextronics International Usa, Inc. Power converter employing regulators with a coupled inductor
US8477514B2 (en) 2006-12-01 2013-07-02 Flextronics International Usa, Inc. Power system with power converters having an adaptive controller
US20100149838A1 (en) * 2006-12-01 2010-06-17 Artusi Daniel A Power System with Power Converters Having an Adaptive Controller
US20100165667A1 (en) * 2006-12-01 2010-07-01 Artusi Daniel A Power System with Power Converters Having an Adaptive Controller
US9197132B2 (en) 2006-12-01 2015-11-24 Flextronics International Usa, Inc. Power converter with an adaptive controller and method of operating the same
US7889517B2 (en) 2006-12-01 2011-02-15 Flextronics International Usa, Inc. Power system with power converters having an adaptive controller
US20110205763A1 (en) * 2006-12-01 2011-08-25 Artusi Daniel A Power Converter with an Adaptive Controller and Method of Operating the Same
US8502520B2 (en) 2007-03-14 2013-08-06 Flextronics International Usa, Inc Isolated power converter
US20080316779A1 (en) * 2007-06-19 2008-12-25 Chandrasekaran Jayaraman System and method for estimating input power for a power processing circuit
US20080315852A1 (en) * 2007-06-19 2008-12-25 Chandrasekaran Jayaraman System and Method for Estimating Input Power for a Power Processing Circuit
US7906941B2 (en) * 2007-06-19 2011-03-15 Flextronics International Usa, Inc. System and method for estimating input power for a power processing circuit
US7923973B2 (en) 2008-09-15 2011-04-12 Power Integrations, Inc. Method and apparatus to reduce line current harmonics from a power supply
US20110157943A1 (en) * 2008-09-15 2011-06-30 Power Integrations, Inc. Method and apparatus to reduce line current harmonics from a power supply
US20100067270A1 (en) * 2008-09-15 2010-03-18 Power Integrations, Inc. Method and apparatus to reduce line current harmonics from a power supply
US8593127B2 (en) 2008-09-15 2013-11-26 Power Integrations, Inc. Method and apparatus to reduce line current harmonics from a power supply
US8207723B2 (en) 2008-09-15 2012-06-26 Power Integrations, Inc. Method and apparatus to reduce line current harmonics from a power supply
US8749212B2 (en) 2008-11-07 2014-06-10 Power Integrations, Inc. Method and apparatus to control a power factor correction circuit
US8040114B2 (en) 2008-11-07 2011-10-18 Power Integrations, Inc. Method and apparatus to increase efficiency in a power factor correction circuit
US8525493B2 (en) 2008-11-07 2013-09-03 Power Integrations, Inc. Method and apparatus to increase efficiency in a power factor correction circuit
US20100118573A1 (en) * 2008-11-07 2010-05-13 Power Integrations, Inc. Method and apparatus to increase efficiency in a power factor correction circuit
US9618955B2 (en) 2008-11-07 2017-04-11 Power Integrations, Inc. Method and apparatus to increase efficiency in a power factor correction circuit
US20100118571A1 (en) * 2008-11-07 2010-05-13 Power Integrations, Inc. Method and apparatus to control a power factor correction circuit
US9116538B2 (en) 2008-11-07 2015-08-25 Power Integrations, Inc. Method and apparatus to increase efficiency in a power factor correction circuit
US8004262B2 (en) 2008-11-07 2011-08-23 Power Integrations, Inc. Method and apparatus to control a power factor correction circuit
US8487601B2 (en) 2008-11-07 2013-07-16 Power Intergrations, Inc. Method and apparatus to control a power factor correction circuit
US8520414B2 (en) 2009-01-19 2013-08-27 Power Systems Technologies, Ltd. Controller for a power converter
US9088216B2 (en) 2009-01-19 2015-07-21 Power Systems Technologies, Ltd. Controller for a synchronous rectifier switch
US9019061B2 (en) 2009-03-31 2015-04-28 Power Systems Technologies, Ltd. Magnetic device formed with U-shaped core pieces and power converter employing the same
US20100254168A1 (en) * 2009-03-31 2010-10-07 Sriram Chandrasekaran Magnetic Device Formed with U-Shaped Core Pieces and Power Converter Employing the Same
US9077248B2 (en) 2009-06-17 2015-07-07 Power Systems Technologies Ltd Start-up circuit for a power adapter
US20100321964A1 (en) * 2009-06-17 2010-12-23 Antony Brinlee Power Adapter Employing a Power Reducer
US8643222B2 (en) 2009-06-17 2014-02-04 Power Systems Technologies Ltd Power adapter employing a power reducer
US8514593B2 (en) 2009-06-17 2013-08-20 Power Systems Technologies, Ltd. Power converter employing a variable switching frequency and a magnetic device with a non-uniform gap
US8264860B2 (en) 2009-08-10 2012-09-11 Emerson Climate Technologies, Inc. System and method for power factor correction frequency tracking and reference generation
US20110031940A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. System and method for power factor correction frequency tracking and reference generation
US8344706B2 (en) 2009-08-10 2013-01-01 Emerson Climate Technologies, Inc. System and method for rejecting DC current in power factor correction systems
US8358098B2 (en) 2009-08-10 2013-01-22 Emerson Climate Technologies, Inc. System and method for power factor correction
US8406021B2 (en) 2009-08-10 2013-03-26 Emerson Climate Technologies, Inc. System and method for reducing line current distortion
US8264192B2 (en) 2009-08-10 2012-09-11 Emerson Climate Technologies, Inc. Controller and method for transitioning between control angles
US9088232B2 (en) 2009-08-10 2015-07-21 Emerson Climate Technologies, Inc. Power factor correction with variable bus voltage
US9154061B2 (en) 2009-08-10 2015-10-06 Emerson Climate Technologies, Inc. Controller and method for transitioning between control angles
US9564846B2 (en) 2009-08-10 2017-02-07 Emerson Climate Technologies, Inc. Power factor correction with variable bus voltage
US8476873B2 (en) 2009-08-10 2013-07-02 Emerson Climate Technologies, Inc. System and method for current balancing
US20110032738A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. System and method for power factor correction
US20110031914A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. Controller and method for transitioning between control angles
US8493014B2 (en) 2009-08-10 2013-07-23 Emerson Climate Technologies, Inc. Controller and method for estimating, managing, and diagnosing motor parameters
WO2011019700A3 (fr) * 2009-08-10 2011-06-23 Emerson Climate Technologies, Inc. Système et procédé de correction du facteur de puissance
US8508166B2 (en) 2009-08-10 2013-08-13 Emerson Climate Technologies, Inc. Power factor correction with variable bus voltage
US9705433B2 (en) 2009-08-10 2017-07-11 Emerson Climate Technologies, Inc. Controller and method for transitioning between control angles
US20110031920A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. Controller and method for estimating, managing, and diagnosing motor parameters
US9912263B2 (en) 2009-08-10 2018-03-06 Emerson Climate Technologies, Inc. Controller and method for transitioning between control angles
US20110031943A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. System and method for rejecting dc current in power factor correction systems
US20110031942A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. System and method for reducing line current distortion
US8547051B2 (en) 2009-08-10 2013-10-01 Emerson Climate Technologies, Inc. Controller and method for transitioning between control angles
US8698433B2 (en) 2009-08-10 2014-04-15 Emerson Climate Technologies, Inc. Controller and method for minimizing phase advance current
US20110031911A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. Power factor correction with variable bus voltage
US20110031941A1 (en) * 2009-08-10 2011-02-10 Emerson Climate Technologies, Inc. System and method for current balancing
US8638578B2 (en) 2009-08-14 2014-01-28 Power System Technologies, Ltd. Power converter including a charge pump employable in a power adapter
US20110038179A1 (en) * 2009-08-14 2011-02-17 Xiaoyang Zhang Power Converter Including a Charge Pump Employable in a Power Adapter
US8976549B2 (en) 2009-12-03 2015-03-10 Power Systems Technologies, Ltd. Startup circuit including first and second Schmitt triggers and power converter employing the same
US8143923B2 (en) 2009-12-07 2012-03-27 Semiconductor Components Industries, Llc Circuit and method for determining a current
US20110133787A1 (en) * 2009-12-07 2011-06-09 Ball Alan R Circuit and method for determining a current
US8520420B2 (en) 2009-12-18 2013-08-27 Power Systems Technologies, Ltd. Controller for modifying dead time between switches in a power converter
US9246391B2 (en) 2010-01-22 2016-01-26 Power Systems Technologies Ltd. Controller for providing a corrected signal to a sensed peak current through a circuit element of a power converter
US8787043B2 (en) 2010-01-22 2014-07-22 Power Systems Technologies, Ltd. Controller for a power converter and method of operating the same
US8767418B2 (en) 2010-03-17 2014-07-01 Power Systems Technologies Ltd. Control system for a power converter and method of operating the same
US20120153906A1 (en) * 2010-12-18 2012-06-21 Harriman Paul J Method for scaling a drive signal and circuit therefor
US8558522B2 (en) * 2010-12-18 2013-10-15 Semiconductor Components Industries, Llc Method for scaling a drive signal and circuit therefor
US20130114308A1 (en) * 2011-01-12 2013-05-09 Richtek Technology Corporation Switching Regulator and Control Circuit and Control Method Thereof
US8780587B2 (en) * 2011-01-12 2014-07-15 Richtek Technology Corporation, R.O.C. Switching regulator and control circuit and control method thereof
US20120187927A1 (en) * 2011-01-25 2012-07-26 Freescale Semiconductor, Inc. Voltage regulation circuitry and related operating methods
US8482266B2 (en) * 2011-01-25 2013-07-09 Freescale Semiconductor, Inc. Voltage regulation circuitry and related operating methods
US8792257B2 (en) 2011-03-25 2014-07-29 Power Systems Technologies, Ltd. Power converter with reduced power dissipation
CN102315767A (zh) * 2011-04-08 2012-01-11 安伏（苏州）电子有限公司 抗电磁干扰的大功率系统电源
US8874053B2 (en) * 2011-07-28 2014-10-28 Skyworks Solutions, Inc. Low variation current multiplier
CN103166469B (zh) * 2011-12-12 2015-10-14 立锜科技股份有限公司 切换式电源供应器及其控制电路与控制方法
CN103166469A (zh) * 2011-12-12 2013-06-19 立锜科技股份有限公司 切换式电源供应器及其控制电路与控制方法
US8792256B2 (en) 2012-01-27 2014-07-29 Power Systems Technologies Ltd. Controller for a switch and method of operating the same
US20130207632A1 (en) * 2012-02-13 2013-08-15 Gurjit Singh THANDI System and method for improved line transient response in current mode boost converters
US9991834B2 (en) 2012-04-26 2018-06-05 Emerson Climate Technologies, Inc. System and method for permanent magnet motor control
US10075116B2 (en) 2012-04-26 2018-09-11 Emerson Climate Technologies, Inc. System and method for permanent magnet motor control
US9634593B2 (en) 2012-04-26 2017-04-25 Emerson Climate Technologies, Inc. System and method for permanent magnet motor control
US9190898B2 (en) 2012-07-06 2015-11-17 Power Systems Technologies, Ltd Controller for a power converter and method of operating the same
US9106130B2 (en) 2012-07-16 2015-08-11 Power Systems Technologies, Inc. Magnetic device and power converter employing the same
US9379629B2 (en) 2012-07-16 2016-06-28 Power Systems Technologies, Ltd. Magnetic device and power converter employing the same
US9099232B2 (en) 2012-07-16 2015-08-04 Power Systems Technologies Ltd. Magnetic device and power converter employing the same
US9214264B2 (en) 2012-07-16 2015-12-15 Power Systems Technologies, Ltd. Magnetic device and power converter employing the same
US9240749B2 (en) 2012-08-10 2016-01-19 Emerson Climate Technologies, Inc. Motor drive control using pulse-width modulation pulse skipping
US9853588B2 (en) 2012-08-10 2017-12-26 Emerson Climate Technologies, Inc. Motor drive control using pulse-width modulation pulse skipping
US9240712B2 (en) 2012-12-13 2016-01-19 Power Systems Technologies Ltd. Controller including a common current-sense device for power switches of a power converter
CN103078488A (zh) * 2012-12-29 2013-05-01 东南大学 一种快速瞬态响应的数字功率因数校正控制器
US9300206B2 (en) 2013-11-15 2016-03-29 Power Systems Technologies Ltd. Method for estimating power of a power converter
CN104660027B (zh) * 2013-11-20 2017-05-17 日月元科技(深圳)有限公司 电流总谐波失真率控制电路及其方法
CN104660027A (zh) * 2013-11-20 2015-05-27 日月元科技(深圳)有限公司 电流总谐波失真率控制电路及其方法
US20150286230A1 (en) * 2014-04-03 2015-10-08 Supertex, Inc. Current Control Circuit for Linear LED Driver
TWI637653B (zh) * 2014-04-03 2018-10-01 微晶片科技公司 用於ｌｅｄ驅動器之電流控制電路
KR20160141823A (ko) * 2014-04-03 2016-12-09 마이크로칩 테크놀로지 인코포레이티드 Led 드라이버용 전류 제어 회로
US10149357B2 (en) 2014-04-03 2018-12-04 Microchip Technology Inc. Current control circuit for linear LED driver
US9575497B2 (en) * 2014-04-03 2017-02-21 Microchip Technology Inc. Current control circuit for linear LED driver
CN106471866A (zh) * 2014-04-03 2017-03-01 微芯片科技公司 用于led驱动器的电流控制电路
CN106471866B (zh) * 2014-04-03 2018-08-17 微芯片科技公司 用于led驱动器的电流控制电路
US10054647B2 (en) 2014-09-15 2018-08-21 Atmel Corporation Fault detection
CN105738689B (zh) * 2014-12-24 2018-08-10 英飞凌科技奥地利有限公司 用于测量功率因数变换器中的功率的系统和方法
US9632120B2 (en) * 2014-12-24 2017-04-25 Infineon Technologies Austria Ag System and method for measuring power in a power factor converter
US20160190912A1 (en) * 2014-12-24 2016-06-30 Infineon Technologies Austria Ag System and Method for Measuring Power in a Power Factor Converter
CN105738689A (zh) * 2014-12-24 2016-07-06 英飞凌科技奥地利有限公司 用于测量功率因数变换器中的功率的系统和方法
US11973436B2 (en) 2017-06-12 2024-04-30 Tae Technologies, Inc. Multi-level multi-quadrant hysteresis current controllers and methods for control thereof
US11201563B2 (en) 2017-06-12 2021-12-14 Tae Technologies, Inc. Multi-level multi-quadrant hysteresis current controllers and methods for control thereof
US11133739B2 (en) 2017-06-16 2021-09-28 Tae Technologies, Inc. Multi-level hysteresis voltage controllers for voltage modulators and methods for control thereof
US11626791B2 (en) 2017-06-16 2023-04-11 Tae Technologies, Inc. Multi-level hysteresis voltage controllers for voltage modulators and methods for control thereof
WO2018232403A1 (fr) * 2017-06-16 2018-12-20 Tae Technologies, Inc. Régulateurs de tension à hystérésis multi-niveau pour modulateurs de tension, et procédés de commande associés
US11881761B2 (en) 2017-06-16 2024-01-23 Tae Technologies, Inc. Multi-level hysteresis voltage controllers for voltage modulators and methods for control thereof
US11840149B2 (en) 2018-03-22 2023-12-12 Tae Technologies, Inc. Systems and methods for power management and control
US11840150B2 (en) 2018-03-22 2023-12-12 Tae Technologies, Inc. Systems and methods for power management and control
US10821843B2 (en) 2018-03-22 2020-11-03 Tae Technologies, Inc. Systems and methods for power management and control
US11597284B2 (en) 2019-03-29 2023-03-07 Tae Technologies, Inc. Module-based energy systems capable of cascaded and interconnected configurations, and methods related thereto
US11603001B2 (en) 2019-03-29 2023-03-14 Tae Technologies, Inc. Module-based energy systems having converter-source modules and methods related thereto
US11884167B2 (en) 2019-03-29 2024-01-30 Tae Technologies, Inc. Module-based energy systems having converter-source modules and methods related thereto
US11964573B2 (en) 2019-03-29 2024-04-23 Tae Technologies, Inc. Module-based energy systems having converter-source modules and methods related thereto
US10807481B1 (en) 2019-03-29 2020-10-20 Tae Technologies, Inc. Module-based energy systems having converter-source modules and methods related thereto
US11135923B2 (en) 2019-03-29 2021-10-05 Tae Technologies, Inc. Module-based energy systems capable of cascaded and interconnected configurations, and methods related thereto
US10807482B1 (en) 2019-03-29 2020-10-20 Tae Technologies, Inc. Module-based energy systems having converter-source modules and methods related thereto
US20210316621A1 (en) 2020-04-14 2021-10-14 Tae Technologies, Inc. Systems, devices, and methods for charging and discharging module-based cascaded energy systems
US11897347B2 (en) 2020-04-14 2024-02-13 Tae Technologies, Inc. Systems, devices, and methods for charging and discharging module-based cascaded energy systems
US11827115B2 (en) 2020-05-14 2023-11-28 Tae Technologies, Inc. Systems, devices, and methods for rail-based and other electric vehicles with modular cascaded energy systems
US11794599B2 (en) 2020-05-14 2023-10-24 Tae Technologies, Inc. Systems, devices, and methods for rail-based and other electric vehicles with modular cascaded energy systems
US11894781B2 (en) 2020-09-28 2024-02-06 Tae Technologies, Inc. Multi-phase module-based energy system frameworks and methods related thereto
US11923782B2 (en) 2020-09-28 2024-03-05 Tae Technologies, Inc. Multi-phase module-based energy system frameworks and methods related thereto
US11845356B2 (en) 2020-09-30 2023-12-19 Tae Technologies, Inc. Systems, devices, and methods for intraphase and interphase balancing in module-based cascaded energy systems
CN113078810A (zh) * 2021-04-30 2021-07-06 深圳市龙星辰电源有限公司 一种用于医疗开关电源的智能功率因数双重谐波去除校正方法
US11888320B2 (en) 2021-07-07 2024-01-30 Tae Technologies, Inc. Systems, devices, and methods for module-based cascaded energy systems configured to interface with renewable energy sources
US11942788B2 (en) 2021-07-07 2024-03-26 Tae Technologies, Inc. Systems, devices, and methods for module-based cascaded energy systems configured to interface with renewable energy sources

Also Published As

Publication number Publication date
AU2001290997A1 (en) 2002-03-26
EP1364445A2 (fr) 2003-11-26
WO2002023694A2 (fr) 2002-03-21
WO2002023694A3 (fr) 2003-09-18
JP2004509587A (ja) 2004-03-25

Similar Documents

Publication Publication Date Title
US6373734B1 (en) Power factor correction control circuit and power supply including same
KR100206143B1 (ko) 고역률 보상회로
KR100599239B1 (ko) 스위칭 전원 장치
US6646848B2 (en) Switching power supply apparatus
US7064527B2 (en) Transition mode operating device for the correction of the power factor in switching power supply units
JP2675509B2 (ja) 力率補正回路
JP3535902B2 (ja) 力率補正回路
KR100221705B1 (ko) 교류.직류 변환용 전원 회로
US6728121B2 (en) Method and apparatus for active power factor correction with minimum input current distortion
JP2005110434A (ja) 力率改善回路
US8503205B2 (en) AC/DC converter with a PFC and a DC/DC converter
WO1993026078A1 (fr) Bloc d'alimentation a courant continu commute et a facteur de puissance eleve
US20120326618A1 (en) Harmonic ripple-current light emitting diode (led) driver circuitry and method
JP4466089B2 (ja) 力率改善回路
JP2515650B2 (ja) 力率改善回路および力率改善回路を用いたスイッチング電源回路
JP3183559B2 (ja) 交流電子負荷装置
JP2005218252A (ja) 力率改善回路及び電源装置
JP4423994B2 (ja) 力率改善回路
KR100415187B1 (ko) 고역률보상회로
JPH02168864A (ja) 直流電源装置
CN110754032A (zh) 交流-直流转换
JP2968670B2 (ja) 保護回路付きｄｃ−ｄｃコンバータ
KR100415186B1 (ko) 역톱니파를이용한역률보상회로
JP3399064B2 (ja) 整流装置
JP3738594B2 (ja) 交流−直流変換装置

Legal Events

Date Code Title Description
AS Assignment

Owner name: ARTESYN TECHNOLOGIES, INC., FLORIDA

Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNOR:MARTINELLI, ROBERT M.;REEL/FRAME:011438/0453

Effective date: 20001215

AS Assignment

Owner name: FLEET CAPITAL CORP., GEORGIA

Free format text: SECURITY INTEREST;ASSIGNOR:ARTESYN TECHNOLOGIES, INC.;REEL/FRAME:013964/0698

Effective date: 20030328

FPAY Fee payment

Year of fee payment: 4

AS Assignment

Owner name: ARTESYN TECHNOLOGIES, INC., FLORIDA

Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNOR:BANK OF AMERICA, N.A.;REEL/FRAME:017706/0454

Effective date: 20060428

REMI Maintenance fee reminder mailed
LAPS Lapse for failure to pay maintenance fees
STCH Information on status: patent discontinuation

Free format text: PATENT EXPIRED DUE TO NONPAYMENT OF MAINTENANCE FEES UNDER 37 CFR 1.362

FP Lapsed due to failure to pay maintenance fee

Effective date: 20100416