TWI451681B - 降壓切換電壓調節器電路及用於調節一降壓切換電壓調節器電路之輸出電壓的方法 - Google Patents

降壓切換電壓調節器電路及用於調節一降壓切換電壓調節器電路之輸出電壓的方法 Download PDF

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TWI451681B
TWI451681B TW098121239A TW98121239A TWI451681B TW I451681 B TWI451681 B TW I451681B TW 098121239 A TW098121239 A TW 098121239A TW 98121239 A TW98121239 A TW 98121239A TW I451681 B TWI451681 B TW I451681B
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voltage regulator
regulator circuit
output
buck switching
switching voltage
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TW201010255A (en
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John L Melanson
Lei Ding
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Cirrus Logic Inc
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/1563—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators without using an external clock
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0016—Control circuits providing compensation of output voltage deviations using feedforward of disturbance parameters
    • H02M1/0019—Control circuits providing compensation of output voltage deviations using feedforward of disturbance parameters the disturbance parameters being load current fluctuations
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0032—Control circuits allowing low power mode operation, e.g. in standby mode
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Description

降壓切換電壓調節器電路及用於調節一降壓切換電壓調節器電路之輸出電壓的方法
本發明大體上係關於遲滯型降壓轉換器控制方案，及更具體言之，係關於一降壓轉換器控制電路，其中一輸出電流的指示被用於動態地調整開啟時序。
在低輸出電流位準下，運送高電流位準的脈衝寬度調變(PWM)控制器與其他類型的切換電源調節器在高負載條件下係沒有效率的。因為對於低輸出電流位準，該脈衝寬度變得非常窄，所以用於操作該等切換電路與控制/感測電路且通常不隨負載電流需求改變的電源支配轉換器的功率消耗，使該轉換器在低需求條件期間非常沒有效率。經常實施替代控制器模式，以在一待機低功率模式下操作該轉換器，其中該全轉換器動態效能係不可用的，但是保持一最小輸出電壓以在該負載電流需求為低時提供所需的電源供應電壓。經常在低功率操作模式下使用脈衝頻率調變(PFM)電路，因為該脈衝頻率可基於負載需求而隨意減小。遲滯型控制電路(其中該輸出電壓保持在兩個預定的設定點之間)已經應用於提供此等低功率操作模式。遲滯型轉換器具有一寬的動態範圍與潛在的低功率消耗，因為其等僅在該輸出電壓下降低於一可接受限制時啟動。
而且，在複雜性或PWM操作所需電源係不合乎需要的低功率應用中，遲滯型控制器有時用於為輸出電流的所有位準提供電源供應控制演算法，因為該控制電路自身可完全 置於待機模式中，僅需要操作該低限電壓感測電路。當必須提高該輸出電壓時，該低限電壓感測電路的輸出可接著啟動該轉換器的剩餘部分。進而，在任何應用中，其中一PWM轉換器的瞬態回應對於回應於負載瞬態是不夠快速的，遲滯型轉換器亦用於對改變負載條件提供一快速回應。
在典型的遲滯型轉換器中，當該輸出電壓下降低於一低限臨界值時，提供一恆定寬度脈衝，注射電荷進入該輸出電容器將該輸出電壓提高一預定數量。然而，若該輸出電流或輸入電壓條件正在變化，則此種轉換器會產生一不良的漣波位準，因為該恆定寬度脈衝不回應於不同位準的負載電流或輸入電壓。在其他類型的遲滯型轉換器中，監視該輸入電壓與其他電源供應條件及控制該輸出脈衝的寬度，使得該漣波位準被控制至一比該等恆定寬度控制器可提供者更高的程度。
然而，由於該轉換器回應所需之時間，以上遲滯型控制器、負載瞬態之各者或輸入電壓下降會導致該低限臨界值的下衝。在該恆定寬度轉換器中，該輸出電壓可能需要一些脈衝以恢復，且在該寬度可控遲滯型轉換器中出現一初始下衝(undershoot)，其藉由已經觸發的脈衝糾正。
因此，提供一種藉由控制下衝而在一遲滯型轉換器中減小漣波的電源供應電路與控制方法將是需要的。
在一降壓切換電壓調節器電路與一操作該降壓切換電壓 調節器電路的方法中提供以上陳述的在一遲滯型轉換器中控制下衝的目的。
該降壓切換電壓調節器電路係藉由預計由於負載電流改變引起的漣波的幅值而提供改良的漣波控制。該電路可為在一切換調節器的待機模式中啟動的一控制電路，例如在更高電流輸出需求期間使用一PWM控制模式及在更低電流輸出需求條件期間進入待機模式的一PWM調節器。一比較電路比較該轉換器的輸出電壓與產生自該轉換器的輸出電流的一指示的波形，使得該轉換器的開啟時間隨著該輸出電流需求增加而提前及調節該更低電壓限制以防止下衝低於規定的較低漣波電壓限制。該轉換器的關閉時間係由限制漣波電壓最大值的一上限臨界值而控制。該輸出電流指示可為輸出電流的一量測，或可為計算自該輸入電壓與該輸出電壓波形的一值。
根據下文對本發明之較佳實施例的更特定描述，如附圖所顯示，本發明之以上與其他的目的、特徵與優點將是顯然的。
本發明涉及用於提供對一降壓切換電壓調節器的控制的電路與方法，其中藉由依照由一負載汲取的輸出電流的一指示而控制開啟臨界值以防止漣波下衝。該輸出電流指示可藉由直接量測該輸出電流而提供，或如將在下文之描述中顯示，可計算自該輸出電壓波形與該輸入電壓值。
現在參考圖1A，其顯示依照本發明之一實施例的一降壓 切換電壓調節器電路。一控制電路，在電晶體P1由控制信號/sa啟動時，控制器10A提供閘極驅動信號至串聯耦合一電感器L1於一輸入電壓源VIN 與輸出端子VOUT 之間的一切換電路SWA。當電晶體N1由控制信號sb啟動時，切換電路SWA在輸出端子VOUT 及與輸入電壓源VIN 和輸出端子VOUT 相關的一通常返回路線(地)之間並聯耦合電感器L1。輸出電容器C1濾波該降壓切換電壓調節器電路的輸出，使得產生在該輸出端子VOUT 的電壓除一漣波電壓外，大致上保持恆量。在低需求，亦即對於供應至一負載ZL 的低電感器電流IL ，控制器10A於不連續導通模式(DCM)下操作，首先啟動電晶體P1以透過電感器L1對輸出電容C1充電，然後釋放電晶體P1及啟動電晶體N1以將儲存於電感器L1的能量釋放至電容上，及然後直到輸出端子VOUT 的電壓下降低於一臨界幅值時最後釋放電晶體N1。在電感器電流IL 的較高位準，控制器10A可作為一遲滯型轉換器於連續導通模式(CCM)下操作，或者可直接轉換至另一CCM控制演算法，例如脈衝寬度調變(PWM)。即使CCM操作經實施用於該轉換器的遲滯操作，PWM或其他操作模式可在電感器電流IL 的一範圍超過遲滯CCM操作所使用者後予以開動。
在本發明之降壓切換電壓調節器中，該臨界幅值用於判定電晶體P1的開啟時間係產生自提供自輸出端子VOUT 至一負載的輸出電流的一指示及產生自提供自電壓源VIN 的輸入電壓幅值的一時間變化波形，使得隨著該輸出電流增加或該輸入電壓減小，電晶體P1的啟動時間在時間上較早發 生，及隨著輸出電流減小或該輸入電壓增加，電晶體P1的啟動時間在時間上較遲發生。該臨界幅值係計算自該輸出電流的一指示，其可為藉由一感測電阻RS 產生的該輸出電流的一量測，其提供不同於該輸出端子VOUT 電壓而正比於輸出電流Io 的一電壓+VILOAD 。(為了闡釋之目的，VOUT 亦指定為-VILOAD 。)控制器10A自由電壓源VIN 提供之輸入電壓與輸出端子VOUT 之電壓計算電晶體P1之關閉時間，其亦為電晶體N1之開啟時間，使得輸出端子VOUT 處的漣波電壓不超過一規定的最大值。最後，如由跨於電阻RL 之電壓(+/-VIL )量測到達一零值或一微小負值，可藉由透過電感器L至電容器C1提供之電感器電流IL 控制電晶體N1的關閉時間，以確保沒有剩餘的能量儲存在電感器L中。
現在參考圖1B，其顯示根據本發明之另一實施例之一降壓切換電壓調節器。圖1B的降壓切換電壓調節器類似於圖1A的降壓切換電壓調節器，因此下文將僅描述其等之間之不同。此外，圖1B之降壓切換電壓調節器中的各種特徵可作為圖解於圖1A之降壓切換電壓調節器之特徵的替代物，且反之亦然。切換電路SWB使用兩個N型電晶體N2與N1及接收自一控制器10B的對應閘極控制信號sa與sb。藉由對閘極控制信號/sa之極性的合適改變，一N通道對亦可用於圖1A的降壓切換電壓調節器。控制器10B僅接收兩種控制輸入值：輸入源VIN 的電壓與輸出端子VOUT 的電壓。控制器10B依照由各自的輸入源VIN 及自輸出端子VOUT 提供的兩個控制輸入信號值(Vout ,Vin )來實現所有切換控制，以產生 閘極控制信號sa與sb。藉由對閘極控制信號sa之極性的合適改變，可使用一P-N切換級，例如圖1A所顯示之切換電路SWA。由於該輸出電流與輸出端子VOUT 的電壓波形及電壓源VIN 的電壓關聯，電晶體N1的開啟時間可由兩個輸入控制信號值(Vout ,Vin )判定，如下文將更詳細描述者。
現在參考圖2A，其顯示圖1A之控制器之詳情。當輸出電流IO 下降低於一臨界值時，或者當PWM控制器24經由一外部控制信號置於待機狀態時，一對三態緩衝器26A與26B藉由PWM控制器24提供之一控制信號模式啟動。當控制信號模式為啟動時，PWM控制器24的閘極控制輸出被置於一高阻抗狀態，使得控制器10A內由電路平衡實施的遲滯型控制器提供閘極控制輸出信號/sa與sb。一臨界值產生器與控制電路20A提供一臨界電壓至一比較器K1，其設定一臨界幅值(電壓信號Vlow )，使其低於該幅值時輸入控制信號Vout 啟動一開始信號，其藉由啟動觸發器22A的設定輸入而觸發閘極控制信號/sa的起始邊緣。當輸入控制信號Vout 的幅值上升超過另一臨界電壓VHIGH 時，另一比較器K2啟動觸發器22A的重設輸入與一觸發器22B的設定輸入，其觸發閘極控制信號/sa的後沿與閘極控制信號sb的前沿。當電感器電流IL 下降低於一零值或微小負值時，臨界值產生器與控制電路22A亦提供一控制信號至觸發器22B重設輸入，以觸發閘極控制信號sb的後沿。
現在參考圖2B，其顯示圖1B之控制器10B之詳情。控制器10B類似於圖2A的控制器10A，因此下文將僅描述其等 之間的不同。控制器10B係提供作為一最小輸入控制器之一實例，及同時例示在遲滯模式下提供所有控制之一控制器。然而，當然該最小輸入組態可與另一控制器類型(例如圖2A所示的PWM控制器24)用於待機模式。臨界值產生器與控制電路20B接收控制輸入信號(Vout ,Vin )及藉由自控制輸入信號(Vout ,Vin )計算臨界電壓VLOW 與VHIGH 產生臨界電壓VLOW 與VHIGH ，如下文將更詳細描述者。提供一計時器28，其大體上是操作自一時脈信號之一計數器鏈，以為閘極控制信號sa之持續時間計時，用於計算閘極控制信號sb之一合適寬度，因為控制器20B不直接量測電感器電流IL 。
現在參考圖3A，其顯示用於不連續導通模式(DCM)在圖2A的臨界值產生器與控制電路20A及圖2B的臨界值產生器與控制電路20B內的計算。需要確保輸出端子VOUT 上的漣波電壓不下降低於一規定的最小值VMIN 的臨界電壓幅值VLOW 的值，可或者使用如顯示於圖2A的控制電路20A的輸出電流IO 的一量測值或者藉由使用如顯示於圖2B的控制電路20B的計算自控制信號值(Vin ,Vout )的輸出電流IO 的一指示予以判定。假定輸出端子電壓VOUT 為恆量，同時閘極控制信號sa係啟動的，則電感器電流可估計為：IL (t)=(Vin -Vout )(t-t0 )/L其中L為電感器L1的電感值，及因此在t1 時刻：IL (t1 )=I0 =(Vin -Vout )(t1 -t0 )/L因此， t1 -t0=I0 L/(Vin -Vout )假定一電感器電流IL ，則輸出端子VOUT 自時刻t0 至時刻t1 的實際電壓下降由△V=IL △t/2C給出，其中C為輸出端子VOUT 處總的輸出電容值。為了保持輸出端子VOUT 處的電壓高於最小電壓VMIN ，閘極控制信號sa應在不遲於控制信號Vout 下降至一臨界位準的時刻予以啟動。
VLOW =VMIN +△V=VMIN +I0 (t1 -t0 )/2C因為t1 -t0 =I0 L/(Vin -Vout )在以上對恆量電感器電流IL 估計中，臨界幅值VLOW 可計算為：VLOW =I0 2 L/2C(Vin -Vout )因此，一旦已知該電感器與電容器的值，即可由輸入電壓信號Vin 與控制信號Vout 及電感器電流IL 判定臨界電壓VLOW 之一波形，因為係在臨界幅值VLOW 相交的時刻，IL (t1 )=I0 。
為了判定用於由VLOW =I0 2 L/2C(Vin -Vout )計算臨界幅值VLOW 的負載電流，可直接量測該負載電流或藉由估計為之。因為跨電容器C1自時刻t0 至時刻t2 的電壓變化為VHIGH -VLOW ，故添加至該電容器的電荷可表示為：C(VHIGH -VLOW )=[(Vin -Vout )(t2 -t0 )2 ]/2L-I0 (t2 -t0 )藉由量測該充電切換(例如圖1A的電晶體P1或圖1B的電晶 體N2)處於開啟的時刻之間的時間(例如計數時脈週期)，可計算I0 及將其用作電感器電流IL 之一估計，因為I0 與IL 之間的不同除在非常輕的負載情況下以外大體上係小的。或者，可由自時刻t2 延伸至時刻t5 的時間週期計算I0 ，其係根據下列公式計算：C(VHIGH -VLOW )=(Vin -Vout )(t4 -t2 )2 /2L-I0 (t5 -t2 )其引起：I0 =Vout (t4 -t2 )2 /2L(t5 -t2 )-C(VHIGH -VLOW )/(t5 -t2 )
為了判定輸出端子VOUT 上的電壓幅值VHIGH 在何值時閘極控制信號sa應予以失效及閘極控制信號sb應予以生效，另一計算予以實現。t2 時刻輸出端子VOUT 處的電壓，此時VOUT =VHIGH 為VMAX -Q(t3 -t2 )/C，其中Q(t3 -t2 )為在閘極控制信號sa失效及閘極控制信號sb生效後加至電容C1的總電荷，其等於VMAX -(IMAX -I0 )(t3 -t2 )/2C，其中最大電流IMAX 為峰值電感器電流。因此，設定VHIGH =VMAX -(IMAX -I0 )(t3 -t2 )/2C將提供需要的切換時間。臨界幅值VHIGH 亦可根據VMIN 表示：VHIGH =VMIN +(IMAX -I0 )(t2 -t1 )/2C該峰值電流IMAX 可由IMAX =I0 +(Vin -Vout )(t2 -t1 )/L及IMAX =I0 +Vout (t3 -t2 )/L判定，其假定該輸出電壓大致上不變化，及該電感器電流 在充電與放電期間係恆定的。因此，(Vin -Vout )(t2 -t1 )/L=Vout (t3 -t2 )/L其引起：t3 -t2 =(t2 -t1 )(Vin -Vout )/Vout 可將以上t3 -t2 的運算式代入以上VHIGH 的運算式，得到：VHIGH =VMAX -[(IMAX -I0 )(t2 -t1 )(Vin -Vout )]/2CVout 可由臨界幅值VHIGH 的運算式根據最小電壓VMIN 判定IMAX -I0 ，以得到：IMAX -I0 =2C(VHIGH -VMIN )/(t2 -t1 )最後，結合以上兩個方程式得到：VHIGH =VMAX -(VHIGH -VMIN )(Vin -Vout )/Vout 及因此VHIGH =VMIN +(VMAX -VMIN )Vout /Vin 以上運算式可用於基於控制信號Vin 與Vout 的先前值產生或計算對於作為一離散值的臨界幅值VHIGH 的一個值，或產生一連續波形以控制該上限臨界幅值。
在以上計算之各者中，假定該電路於不連續導通模式(DCM)下操作，亦即經操作使得儲存在電感器L1中的所有能量在時刻t0 與t5 得以釋放。然而，在較高負載條件下，本發明之電路可於連續導通模式(CCM)下操作及對於最佳操作，對該較低臨界幅值VLOW 的計算發生變化。然而，對該上限臨界幅值VHIGH 的計算與以上描述相同。現在參考圖3B，其顯示此種操作。在圖3B的信號圖中，時刻t4 係缺失的，因為不存在兩個切換電晶體(充電及放電)都關閉的 重要時段。在連續導通模式下，假定輸出電壓Vout 係恆定的，dIL /dt=(Vin -Vout )/L在該充電電晶體(例如圖1A的電晶體P1或圖1B的電晶體N2)開啟後，給出一較低電流IMIN ，其為在開啟時刻的初始非零電流，然後IL (t)=(Vin -Vout )(t-t0 )/L+IMIN 其根據以上對於不連續導通模式的定義I0 =IL (t)，引起：t-t0 =(I0 -IMIN )L/(Vin -Vout )因此，為了確保輸出端子VOUT 的電壓不下降低於最小電壓VMIN ，臨界幅值VLOW 應設定為：VLOW= VMIN +L(I0 -IMIN )2 /2C(Vin -Vout )
為了判定CCM下的負載電流，如以上對DCM之描述，可直接量測或估計該負載電流。因為跨電容器C1自時刻t0 至時刻t2 的電壓變化為VHIGH -VLOW ，加至該電容器的電荷可表示為：C(VHIGH -VLOW )=(Vin -Vout )(t2 -t0 )2 /2L-(I0 -IMIN )(t2 -t0 )
而I0 -IMIN 可表示為：I0 -IMIN =(Vin -Vout )(t2 -t0 )/2L-C(VHIGH -VLOW )/(t2 -t0 )其與DCM中的I0 運算式相同。因為以上用於判定VLOW 的必需量為I0 -IMIN ，可使用與在DCM下用於估計I0 相同的計算式在CCM下估計I0 -IMIN 的值。亦可替代地使用基於自時刻t2 至時刻t4 的替代運算式，如下I0 -IMIN =Vout (t4 -t2 )2 /2L(t3 -t2 )-C(VHIGH -VLOW )/(t5 -t2 )
在CCM下，進一步最佳化臨界幅值VLOW 的控制係可能的。因此，對於時刻t5 與時刻t6 之間的時段，自電容器C1失去的總電荷由(I0 -IMIN )(t6 -t5 )/2給出。因此較低臨界幅值VLOW 由VLOW =VMIN +(I0 -IMIN )(t6 -t5 )/2給出。較低臨界幅值VLOW 亦可表示為VLOW =VMAX -(I0 -IMIN )(t5 -t3 )/2在時刻t5 該電感器電流IL =IMIN ，其在Vout =VLOW 時發生，可表示為：IMIN =IO -(Vin -Vout )(t6 -t5 )/L=IO -Vout (t5 -t3 )/L及因此(Vin -Vout )(t6 -t5 )=Vout (t5 -t3 )結合以上關係以得到：VLOW =VMIN +Vout (I0 -IMIN )(t5 -t3 )/2(Vin -Vout )=VMAX -(I0 -IMIN )(t5 -t3 )/2及然後，VLOW =VMIN +(VMAX -VMIN )Vout /Vin 其與CCM及DCM兩者中的VHIGH 運算式相同。因此對於CCM，VLOW =VHIGH 。
現在參考圖4A與圖4B，其顯示對圖1A與圖1B的降壓切換電壓調節器電路、圖2A的控制器10A與圖1B的控制器10B的操作，及下文更加詳細地描述上文所描述的在控制器10A與10B中使用以判定切換時間的計算。其只顯示 DCM，但是該說明同樣適用於CCM操作。圖4A顯示本發明之遲滯型轉換器電路回應於輸出電流IO 的一變化的操作。隨著輸出電流IO 增加，臨界電壓VLOW 根據以上公式增加，引起該充電電晶體漸進地提早開啟。類似地，圖4B顯示該遲滯型轉換器電路回應於輸入源VIN 處的一下降電壓的操作，例如操作自一正在放電的電池。該放電速率經放大以顯示該下降輸入電壓對臨界電壓VLOW 的影響，其經增加以引起該充電電晶體提早開啟，補償輸入源VIN 的電壓下降。
雖然已經參考本發明之較佳實施例特定顯示及描述本發明，但是熟習此項技術者將認識到，在不脫離本發明的精神與範圍下可在形式與細節上作出以上及其他變化。
10A、10B‧‧‧控制器
20A、20B‧‧‧臨界值產生器與控制電路
22A、22B‧‧‧觸發器
24‧‧‧PWM控制器
26A、26B‧‧‧三態緩衝器
28‧‧‧計時器
C1‧‧‧電容器
K1、K2‧‧‧比較器
L1‧‧‧電感器
圖1A至1B為描述根據本發明之實施例之功率切換電路的方塊圖。
圖2A為圖1A的控制電路10A的一簡化示意圖。
圖2B為圖1B的控制電路10B的一簡化示意圖。
圖3A為顯示在不連續導通模式(DCM)下實現於臨界值產生器及圖2A的控制電路20A及臨界值產生器及圖2B的控制電路20B內的計算的一信號波形圖。
圖3B為顯示在連續導通模式(CCM)下實現於圖2A的臨界值產生器與控制電路20A及圖2B的臨界值產生器與控制電路20B內的計算的一信號波形圖。
圖4A至4B為描述圖1A至1B及圖2A至2B所述的電路中的 信號的信號波形圖。
10A‧‧‧控制器
20A‧‧‧臨界值產生器與控制電路
22A、22B‧‧‧觸發器
24‧‧‧PWM控制器
26A、26B‧‧‧三態緩衝器
K1、K2‧‧‧比較器

Claims (24)

  1. 一種降壓切換電壓調節器電路，其包括：一比較電路，用於當該降壓切換電壓調節器電路之一輸出電壓未超過一第一臨界幅值時提供一第一指示，及在該降壓切換電壓調節器電路之該輸出電壓超過一第二臨界幅值時提供一第二指示，其中該第二臨界幅值大於該第一臨界幅值；一電感性儲存元件；一切換電路，用於回應於該第一指示而在該降壓切換電壓調節器電路之一輸入與該降壓切換電壓調節器電路之一輸出之間耦合該電感性儲存元件，及回應於該第二指示而在該降壓切換電壓調節器電路之該輸出與該降壓切換電壓調節器電路之該輸出之一返回線路之間耦合該電感性儲存元件；及一控制電路，用於產生該第一臨界幅值與該第二臨界幅值，使得該第一臨界幅值隨由該降壓切換電壓調節器電路之該輸出提供至一負載之一輸出電流的增加而增加及隨該輸出電流的減小而減小，且其中該控制電路計算該輸出電流之一指示及依照其設定該第一臨界幅值。
  2. 如請求項1之降壓切換電壓調節器電路，其中該控制電路依照該輸出電流之一值進一步設定該第二臨界幅值。
  3. 如請求項1之降壓切換電壓調節器電路，其中該控制電路自該降壓切換電壓調節器電路之一輸出電壓及延伸自該切換電路之一給定週期中該第二指示之一起始與該切 換電路之一下一週期中該第一指示之一起始的時段，計算該輸出電流的該指示。
  4. 如請求項3之降壓切換電壓調節器電路，其中該控制電路根據下列公式計算該輸出電流的該指示：(Vin -Vout )(t2 -t0 )/2L-C(VHIGH -VLOW )/(t2 -t0 )其中Vin 為該降壓切換電壓調節器電路之一輸入電壓，Vout 為該降壓切換電壓調節器電路之該輸出電壓，C為該降壓切換電壓調節器電路在該輸出處之一電容值，L為該電感性儲存元件之電感值，t2 為在該給定週期中該第二指示之該起始之一時刻，t0 為在該給定週期中該第一指示之該起始之一時刻，VHIGH 為一最大漣波電壓值，及VLOW 為一最小漣波電壓值。
  5. 如請求項3之降壓切換電壓調節器電路，其中該控制電路根據下列公式計算該輸出電流的指示：Vout (t4 -t2 )2 /2L(t5 -t2 )-C(VHIGH -VLOW )/(t5 -t2 )，其中Vout 為該降壓切換電壓調節器電路之該輸出電壓，C為該降壓切換電壓調節器電路在該輸出處之一電容值，L為該電感性儲存元件之電感值，t2 為在該給定週期中該第二指示之該起始之一時刻，t5 為在該下一週期中該第一指示之該起始之一時刻，VHIGH 為一最大漣波電壓值，及VLOW 為一最小漣波電壓值，及t4 為在該給定週期中該第二指示末尾之一時刻。
  6. 如請求項1之降壓切換電壓調節器電路，其中該控制電路量測該輸出電流以提供該輸出電流的指示。
  7. 如請求項1之降壓切換電壓調節器電路，其中該控制電路進一步依照該降壓切換電壓調節器電路之一輸入電壓與該降壓切換電壓調節器電路之該輸出電壓之間的差值來計算該第一臨界幅值。
  8. 如請求項7之降壓切換電壓調節器電路，其中該控制電路根據下列公式計算該第一臨界幅值：I0 2 L/2C(Vin -Vout )，其中Vin 為該降壓切換電壓調節器電路之一輸入電壓，Vout 為該降壓切換電壓調節器電路之該輸出電壓，C為該降壓切換電壓調節器電路在該輸出處之一電容值，L為該電感性儲存元件之電感值，及I0 為該輸出電流之該指示。
  9. 如請求項1之降壓切換電壓調節器電路，其中該控制電路係於一連續導通模式下操作，且該輸出電流之指示為傳送至該降壓切換電壓調節器電路之該輸出之一電流與該電感性儲存元件中之一最小電流之間的差值。
  10. 如請求項1之降壓切換電壓調節器電路，其中該控制電路自該降壓切換電壓調節器電路之該輸出電壓與該降壓切換電壓調節器電路之一輸入電壓，計算該第二臨界幅值。
  11. 如請求項10之降壓切換電壓調節器電路，其中該控制電路根據下列公式計算該第二臨界幅值：VHIGH =VMIN +(VMAX -VMIN )Vout /Vin ，其中Vin 為該降壓切換電壓調節器電路之一輸入電壓， Vout 為該降壓切換電壓調節器電路之該輸出電壓，VHIGH 為一最大漣波電壓值，及VLOW 為一最小漣波電壓值。
  12. 一種降壓切換電壓調節器電路，其包括：一比較電路，用於當該降壓切換電壓調節器電路之一輸出電壓未超過一第一臨界幅值時提供一第一指示，及當該降壓切換電壓調節器電路之該輸出電壓超過一第二臨界幅值時提供一第二指示，其中該第二臨界幅值大於該第一臨界幅值；一電感性儲存元件；一切換電路，用於回應於該第一指示而在該降壓切換電壓調節器電路之一輸入與該降壓切換電壓調節器電路之輸出之間耦合該電感性儲存元件，及回應於該第二指示而在該降壓切換電壓調節器電路之該輸出與該降壓切換電壓調節器電路之該輸出之一返回線路之間耦合該電感性儲存元件；及一控制電路，用於隨著速率大於或等於該切換電路之一切換週期之一波形而產生該第一臨界幅值，其中該第一指示係重複產生以控制該切換週期之一開始，且其中產生該波形使得該第一指示隨著由該降壓切換電壓調節器電路之該輸出提供至一負載之一輸出電流的增加而在該切換週期內於時間上提早發生，及隨著該輸出電流減小而在該切換週期內於時間上延遲發生。
  13. 一種用於調節一降壓切換電壓調節器電路之輸出電壓的方法，其包括： 首先比較該降壓切換電壓調節器電路之一輸出電壓與一第一臨界幅值；其次比較該降壓切換電壓調節器電路之該輸出電壓與一第二臨界幅值，其中該第二臨界幅值大於該第一臨界幅值；當該第一比較表明該降壓切換電壓調節器電路之該輸出電壓未超過該第一臨界幅值時，在該降壓切換電壓調節器電路之一輸入與該降壓切換電壓調節器電路之該輸出之間藉由一切換電路耦合一電感性儲存元件；當該第二比較表明該降壓切換電壓調節器電路之該輸出電壓超過該第二臨界幅值時，在該降壓切換電壓調節器電路的該輸出與該切換電壓調節器電路之該輸出之一返回線路之間藉由一切換電路耦合該電感性儲存元件；及控制該第一臨界幅值與該第二臨界幅值的值，使得藉由計算由該降壓切換電壓調節器電路之該輸出提供至一負載之一輸出電流之一指示及依照其設定該第一臨界幅值，該第一臨界幅值隨著由該降壓切換電壓調節器電路之該輸出提供至一負載之輸出電流的增加而增加及隨著該輸出電流的減小而減小。
  14. 如請求項13之方法，其中該控制進一步包括依照該輸出電流的值來設定該第二臨界幅值。
  15. 如請求項13之方法，其中該控制自該降壓切換電壓調節器電路之一輸出電壓與延伸自在該降壓切換電壓調節器 電路之一給定週期中該第二指示之一起始與在該降壓切換電壓調節器電路之一下一週期中該第一指示之一起始的時段，計算該輸出電流的該指示。
  16. 如請求項15之方法，其中該控制根據下列公式計算該輸出電流的該指示：(Vin -Vout )(t2 -t0 )/2L-C(VHIGH -VLOW )/(t2 -t0 )其中Vin 為該降壓切換電壓調節器電路之一輸入電壓，Vout 為該降壓切換電壓調節器電路之該輸出電壓，C為該降壓切換電壓調節器電路在該輸出處之一電容值，L為該電感性儲存元件之電感值，t2 為在該給定週期中該第二指示之該起始之一時刻，t0 為在該給定週期中該第一指示之該起始之一時刻，VHIGH 為一最大漣波電壓值，及VLOW 為一最小漣波電壓值。
  17. 如請求項15之方法，其中該控制根據下列公式計算該輸出電流的該指示：Vout (t4 -t2 )2 /2L(t5 -t2 )-C(VHIGH -VLOW )/(t5 -t2 )其中Vout 為該降壓切換電壓調節器電路之該輸出電壓，C為該降壓切換電壓調節器電路在該輸出處之一電容值，L為該電感性儲存元件之電感值，t2 為在該給定週期中該第二指示之該起始之一時刻，t5 為在該下一週期中該第一指示之該起始之一時刻，VHIGH 為一最大漣波電壓值，及VLOW 為一最小漣波電壓值，及t4 為在該給定週期中該第二指示末尾之一時刻。
  18. 如請求項13之方法，進一步包括量測該輸出電流以提供 該輸出電流的該指示。
  19. 如請求項13之方法，其中該控制進一步依照該降壓切換電壓調節器電路之一輸入電壓與該降壓切換電壓調節器電路之該輸出電壓之間的差值來計算該第一臨界幅值。
  20. 如請求項19之方法，其中該控制根據下列公式計算該第一臨界幅值：I0 2 L/2C(Vin -Vout )，其中Vin 為該降壓切換電壓調節器電路之一輸入電壓，Vout 為該降壓切換電壓調節器電路之該輸出電壓，C為該降壓切換電壓調節器電路在該輸出處之一電容值，L為該電感性儲存元件之電感值，及I0 為該輸出電流之指示。
  21. 如請求項13之方法，其中該降壓切換電壓調節器電路於一連續導通模式下操作，且該輸出電流指示係傳送至該降壓切換電壓調節器電路之該輸出之一電流與該電感性儲存元件中之一最小電流之間的差值。
  22. 如請求項13之方法，其中該控制自該降壓切換電壓調節器電路之該輸出電壓與該降壓切換電壓調節器電路之一輸入電壓計算該第二臨界幅值。
  23. 如請求項22之方法，其中該控制根據下列公式計算該第二臨界幅值：VHIGH =VMIN +(VMAX -VMIN )Vout /Vin ，其中Vin 為該降壓切換電壓調節器電路之一輸入電壓，Vout 為該降壓切換電壓調節器電路之該輸出電壓，VHIGH 為一最大漣波電壓值，及VLOW 為一最小漣波電壓值。
  24. 一種用於調節一降壓切換電壓調節器電路之輸出電壓的方法，其包括：首先比較該降壓切換電壓調節器電路之一輸出電壓與一第一臨界幅值；其次比較該降壓切換電壓調節器電路之該輸出電壓與一第二臨界幅值，其中該第二臨界幅值大於該第一臨界幅值；當該第一比較表明該降壓切換電壓調節器電路之該輸出電壓未超過該第一臨界幅值時，在該降壓切換電壓調節器電路之一輸入與該降壓切換電壓調節器電路之該輸出之間藉由一切換電路耦合一電感性儲存元件；當該第二比較表明該降壓切換電壓調節器電路之該輸出電壓超過該第二臨界幅值時，在該降壓切換電壓調節器電路之輸出與該切換電壓調節器電路之該輸出之一返回線路之間藉由一切換電路耦合該電感性儲存元件；及隨著速率大於或等於該切換電路之一切換週期之一波形而產生該第一臨界幅值，其中該第一指示係重複產生以控制該切換週期之一開始，及其中產生該波形使得該第一指示隨著由該降壓切換電壓調節器電路之該輸出提供至一負載之一輸出電流的增加而在該切換週期內於時間上提早發生，及隨著該輸出電流減小而在該切換週期內於時間上延遲發生。
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US8008902B2 (en) 2011-08-30
US20090322300A1 (en) 2009-12-31
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