EP3208934A1 - Verfahren zur ansteuerung eines wechselstrommotors durch zweiphasenstrom und stromerzeugungsverfahren - Google Patents

Verfahren zur ansteuerung eines wechselstrommotors durch zweiphasenstrom und stromerzeugungsverfahren Download PDF

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Publication number
EP3208934A1
EP3208934A1 EP17156473.5A EP17156473A EP3208934A1 EP 3208934 A1 EP3208934 A1 EP 3208934A1 EP 17156473 A EP17156473 A EP 17156473A EP 3208934 A1 EP3208934 A1 EP 3208934A1
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Prior art keywords
phase
stator
motor
magnetic field
currents
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EP17156473.5A
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English (en)
French (fr)
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EP3208934B1 (de
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Ghing-Hsin Dien
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P23/00—Arrangements or methods for the control of AC motors characterised by a control method other than vector control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
    • H02P6/10—Arrangements for controlling torque ripple, e.g. providing reduced torque ripple
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P9/00—Arrangements for controlling electric generators for the purpose of obtaining a desired output
    • H02P9/14—Arrangements for controlling electric generators for the purpose of obtaining a desired output by variation of field

Definitions

  • the present invention relates to a method for driving an AC motor and a power generation method, especially about using two-phase alternating currents to drive an AC motor and using the motor to generate power.
  • the multiphase currents could be square-wave currents or sine-wave currents.
  • Brushless DC motors usually use square-wave currents to drive, while permanent magnet synchronous motors (PMSM) or AC-induction motors usually use sine-wave currents to drive.
  • Square-wave (or trapezoidal-wave) current driver generates larger magnetic field ripples but has a relatively simple driver circuit.
  • Sine-wave current driver generates smaller magnetic field ripples so the motor has a smoother rotation and lower noise, and so sine-wave drivers are used in many applications with higher requirements.
  • the three-phase sine-wave currents drive three sets of coils of the motor and generate three sets of magnetic fields (vectors) to combine into one set of rotating magnetic field sum (vector sum).
  • the rotor then rotates with the combined magnetic field sum (vector sum).
  • this kind of three-phase sine-wave driving method implicitly generates some invalid and useless magnetic fields (vectors) that are reverse to the direction of rotation and cancel with other magnetic fields (vectors), which results in the waste of power.
  • a typical conventional two-phase motor uses two sine-wave currents with 90-degree phase difference to drive a four-pole stator (i.e. with four sets of stator teeth and coils, or with 90-degree stator pole pitch) to generate a substantially no-ripple (or with the smallest ripple) and steadily rotating magnetic field for its rotor. Due to the characteristics of the two-phase sine-wave currents, the two-phase motor must have four stator poles or the stator pole pitch must equal to 90 degrees if a substantially no-ripple (or smallest-ripple) rotating magnetic field sum is required.
  • an objective of the present invention is to provide a method for driving a two-phase or multiphase AC motor with alternating currents to reduce the invalid magnetic fields in the conventional motor, lower the power consumption, and create a steady and substantially no-ripple (or smallest-ripple) rotating magnetic field to drive the rotor to rotate or move. It is also an objective to provide a substantially no-ripple (or smallest-ripple) drive method for a two-phase motor with more than four stator poles or with a stator pole pitch smaller than 90 degrees. To make it easier to understand, it is preferred to assume the motors in the following descriptions use concentrated windings.
  • Another objective of the invention is to provide a motor generator to generate power with two-phase currents and with higher efficiency.
  • the invention discloses a method for driving an AC motor using two-phase alternating currents.
  • a controller with software or hardware or software/hardware techniques is used to generate at least two alternating currents with different phases to drive the AC motor.
  • the AC motor has a rotor, a stator and at least two sets of stator coils, and the stator generates a plurality of stator poles when the stator coils are energized.
  • the angular distance between two adjacent stator poles is smaller than 90 degrees.
  • the method comprising: driving the two sets of stator coils by the two alternating currents with different phases and generate two sets of magnetic fields which combine into one set of magnetic field sum so as to drive the rotor.
  • the magnetic field sum substantially has no ripples and its change rate of rotation angle or movement is proportional to the change rate of the phase angle of the two alternating currents, and each cycle of each of the two alternating currents has a positive half cycle and a negative half cycle.
  • the positive half cycle comprises a positive curved-triangle current waveform
  • the negative half cycle comprises a negative curved-triangle current waveform.
  • the phrase "substantially has no ripples" represents that with theoretical ideal values it can be completely ripple free
  • the said positive or negative curved-triangle current represents a current waveform wherein the rising slope and falling slope falls between a sine-wave waveform and a triangle-wave waveform of the same peak point.
  • the invention further discloses a method for driving an AC motor which uses a controller with software or hardware or software/hardware techniques to generate at least two alternating currents with different phases to drive the AC motor.
  • the AC motor has a rotor, a stator and at least two sets of stator coils.
  • the stator generates a plurality stator poles when the stator coils are energized, and the angular distance between two adjacent stator poles is smaller than 90 degrees.
  • the method comprising: driving the two sets of stator coils with the two alternating currents with different phases to generate two sets of magnetic fields which combine into one set of magnetic field sum so as to drive the rotor.
  • the magnetic field sum substantially has no ripples and its change rate of rotation angle or movement is proportional to the change rate of the phase angle of the two alternating currents.
  • the invention further discloses a method for generating electric power with an AC motor generator.
  • the AC motor generator has a rotor, a stator and two sets of stator coils.
  • the rotor generates at least one set of rotating magnetic fields when the rotor rotates, and each set of the rotating magnetic fields drives the two sets of the stator coils, and generates two phases of induction currents with 90 degrees of phase difference in the two sets of stator coils.
  • the angular distance between two adjacent stator poles is less than 90 degrees.
  • ⁇ is the included angle between the rotating magnetic field and the stator pole direction
  • ⁇ is the angular distance between two adjacent stator poles
  • R is the strength of a rotating magnetic field.
  • a two-phase AC drive method for a motor which applies two phases of currents to drive the motor coils and generate two sets of magnetic fields (vectors), and the two sets of magnetic fields (vectors) are combined into one set of magnetic field sum (vector sum) that rotates steadily and substantially has no ripples (or has the smallest ripples), and the rotating magnetic field sum drives the rotor to rotate, so the anti-rotation magnetic field vectors (vectors that are opposite to the direction of rotation) or the invalid vectors that cancels each other in a three-phase system are not generated, so as to save the power.
  • a two-phase or multiphase motor drive method that drives a motor which has more than four stator poles or has a stator pole pitch which is smaller than 90 degrees.
  • a control circuit controls two-phase currents to drive the motor stator coils, and three parameters are used for calculating current values.
  • the first parameter is the included angle between the rotating magnetic field sum and the stator pole direction
  • the second parameter is the angular distance between two adjacent stator poles
  • the third parameter is the target strength of the rotating magnetic field.
  • the control circuit uses real-time calculation or lookup tables or other software or hardware techniques with the equations to get the respective reference current values for any rotating position, so as to drive the motor based on the respective reference current values to get a substantially rippleless rotation.
  • a power generation method for an AC motor generator to generate two-phase currents.
  • the rotor of the AC motor generator generates at least one set of rotating magnetic field when the rotor rotates.
  • Each set of the rotating magnetic field drives at most two sets of stator coils at one time, and generates two curved-triangle induction currents with 90 degrees in phase difference in those two sets of stator coils with higher efficiency.
  • the invention uses two-phase currents with specially designed waveforms to drive motors without generating invalid magnetic fields which is usually generated in conventional multiphase sine-wave driven motors, so as to save power.
  • the invention provides a driving method for two-phase AC motors with more than four stator poles or with a stator pole pitch of smaller than 90 degrees to generate substantially ripple free rotation, so as to save power. Therefore, the invention can expand the applications of the two-phase motors. Furthermore, the same principle can be used reversely to generate power.
  • each rotating magnetic field generated by the rotating rotor of the motor generator drives at most two sets of stator coils at one time, and generates two curved-triangle currents. Accordingly, the magnetic flux can be used to generate power more efficiently.
  • each stator tooth generates one stator pole, but it is not to limit the invention to concentrated winding motors.
  • the drive method of the invention still can be used with distributed winding motors.
  • FIG. 1A is a circuit diagram of a conventional three-phase motor driver, the driver uses controller 93 to output Pulse Width modulation (PWM) signals (PWM1 ⁇ PWM6) to control six (6) transistor switches (M1 ⁇ M6) to generate three-phase sine-wave currents (phase A, phase B and phase C) to drive the motor 91 to rotate, and uses position detector 92 to detect the rotor position of motor 91 and generates a position signal feedback to controller 93.
  • PWM Pulse Width modulation
  • FIG. 1B and FIG. 1C the waveforms of a conventional three-phase sine-wave currents for a motor is shown in FIG. 1B . Please note that the strength of the magnetic field sum R equals 1.5 all the time (with no ripples).
  • FIG. 1C shows the magnetic field vectors generated by the three-phase sine-wave currents in FIG. 1B at the time t1.
  • the three-phase currents A, B and C generate the three magnetic field vectors Va, Vb and Vc of FIG. 1C respectively.
  • the included angle of the three vectors is 120 degrees.
  • the Va has its maximum value, and Vb and Vc are negative.
  • Vabc is the magnetic field vector sum of Va, Vb and Vc, and Vabc rotates counterclockwise.
  • the q-axis represents the axis perpendicular to the direction of the magnetic field vector sum Vabc
  • d-axis represents the axis parallel to the direction of the vector sum Vabc.
  • FIG. 1C shows that at time t1.
  • Vb has a component Vbl (points to the right) on the q-axis
  • Vc also has a component Vc1 (points to the left) on the q-axis.
  • the direction of Vb1 is opposite to the rotation. Therefore, Vbl and Vcl cancel each other, so they are basically invalid magnetic field vectors, and the currents used to generate Vbl and Vcl are basically wasted, which causes excessive power consumption and redundant, useless and invalid magnetic fluxes.
  • Vb1 and Vcl cancels each other, which means that Vbl and Vc1 are invalid vectors and their power is wasted.
  • the method of the present embodiment uses only two curved-triangle currents to drive the AC motor. In a multiphase system, two phases out of multiphase are used. Or, in a two-phase system, two curved-triangle currents are used to drive the motor, providing the same no-ripple rotation with higher efficiency. The two curved-triangle currents are calculated from two equations of the embodiment. The total power consumption compared to a conventional three-phase sine-wave system is improved by 30% (with a motor of 30-degree stator pole pitch).
  • FIG. 2A ⁇ 3E shows how the invention uses two magnetic field vectors ( A ⁇ and B ⁇ ) to combine into one magnetic field vector sum R ⁇ .
  • FIG. 2A shows the contour circle of the magnetic field vector sum R ⁇ that rotates counterclockwise, vector sum R ⁇ is the sum of (magnetic) vector A ⁇ and (magnetic) vector B ⁇ .
  • Vector A ⁇ along the a-axis represents the magnetic flux vector generated from the A-phase current driving the A-phase stator tooth.
  • Vector B ⁇ along the b-axis represents the magnetic flux vector generated from the B-phase current driving the B-phase stator tooth.
  • ⁇ is the included angle between the two magnetic pole centers of stator teeth of A-phase and B-phase (angular distance of stator poles, stator pole pitch).
  • 0 equals to 60 degrees
  • the angle ⁇ represents the included angle between the vector sum R ⁇ and the direction of A-phase stator tooth's magnetic pole (i.e. R ⁇ vs. a-axis).
  • Four angle positions are shown as vector R ⁇ rotates from b-axis to a-axis (i.e.
  • ⁇ is the angular distance of adjacent stator poles (stator pole pitch). ⁇ is the included angle between the rotating magnetic field vector sum and the stator pole direction.
  • R is the strength of the magnetic field vector sum R ⁇ .
  • A is the strength of A-phase magnetic field vector A ⁇ .
  • B is the strength of B-phase magnetic field vector B ⁇ .
  • the inductance of the stator coil is supposed to be L. Since the ⁇ , R are known values, and the A-phase and B-phase's magnetic field vectors are proportional to the A-phase and B-phase's currents in the coils respectively, therefore the equations (3) and (4) can be used to represent the relations between the driving currents of A-phase and B-phase and the included angle ⁇ .
  • stator pole pitch ⁇ is equal to the angular distance between centers of adjacent stator slots, or equals to the included angle of centers of adjacent stator teeth, or equals to the angular distance between adjacent stator poles. If the motor is using distributed windings, ⁇ equals to the angular distance between adjacent stator poles.
  • FIGS. 3A to 3E show the vector sum R ⁇ rotating from a-axis to the next b-axis. Please refer to the previous descriptions relating to FIGS. 2A to 2E , and the similar details are not repeated here.
  • Table 1 and in FIG. 4A to FIG. 4D are the drive current table and the current waveform and vector diagram for an embodiment according to the invention.
  • the current values of each phase in Table 1 are shown and are calculated according to the equations (3) and (4).
  • phase A current values along the time-axis from phase angle of zero to 180 degrees are listed, only the current values of the positive-half cycle are listed, the negative-half cycle (180 ⁇ 360 degrees) is omitted because it is symmetric to the positive-half cycle, in row 1 of Table 1 it is the phase angle of the driving current, i.e.
  • the time-axis in row 2 it is the angle Alpha ( ⁇ ) which varies from zero to 60 degrees repeatedly, ⁇ represents the included angle between the direction of the magnetic field sum and the salient direction of the stator pole, and when ⁇ changes from zero to 60 degrees, it represents the included angle's change when the magnetic field sum rotates and directs from one stator tooth magnetic pole center to the next, in row 3 ⁇ 5 are the phase A, B and C driving current values calculated from the equations (3) and (4), in row 6 it is the magnetic field sum's strength calculated from the three phase currents, the strength is kept at a value of 1.5 steadily as expected, in row 7 it is the calculated rotation angle of the magnetic field sum, in a half-cycle time the direction changes and rotates steadily from -60 degrees to 120 degrees (i.e.
  • the magnetic field vector sum is rotating and its rotation angle is increasing or decreasing with a change rate proportional to the change rate of the phase angle of the power source).
  • the magnetic field sum's strength substantially has no ripples (i.e. with the theoretical ideal values it can be completely ripple free), and its change rate of rotation angle or movement is proportional to the change rate of the phase angle of the driving currents.
  • FIGS. 4A to 4D the waveforms and vectors are shown according to the embodiments of the disclosure.
  • FIG. 4A are current waveforms drawn from the current values in Table 1 according to the first embodiment of the invention, including the phase A current 3a, phase B current 3b, phase C current 3c, the strength 3d of the magnetic field sum and the rotation angle 3e of the magnetic field sum.
  • the phase B current is lagged for 1 ⁇ /3 to the phase A current.
  • the phase C current is lagged for 2 ⁇ /3 to the phase A current.
  • the magnetic field sum angle 3e rotates steadily from -60 to 300 degrees (please refer to the right side Y axis scale).
  • the driving waveform according to the embodiment comprises a current waveform with a curved-triangle shape (triangle with two curved sides) and a zero current period.
  • the current waveform of the embodiment is referred as a "curved-triangle" waveform, and it is characterized in that its rising and falling slopes fall between a sine-wave and a triangle-wave of the same peak point.
  • in the three-phase currents at any time there are at most only two phases of currents are overlapped in time, which means at any time there is only two phases of currents at most that are outputting to drive the motor stator coils.
  • the rest phases of currents are substantially zero or being shut off, and different two phases of currents are sequentially grouped into a series of two-phase pairs and driving the motor coils pair by pair.
  • FIG. 4A from left to right there are two-phase current pairs of (-C,A), (A,B), (B,C), (C,-A), (-A,-B), and (-B,-C). These two-phase pairs all drive the motor one by one with overlap.
  • Each phase's positive current time is overlapped with another phase's positive current time.
  • the first phase's (phase A's) positive-rising current time is overlapped with the last phase's (phase C's) negative current time (i.e.
  • phase B's positive current time (ex. phase B's 1 ⁇ /3 ⁇ time) is only overlapped with the positive current time of its preceding and succeeding phases (i.e. phase A & C)
  • phase B's negative current time (ex. phase B's 4 ⁇ /3 ⁇ 2 ⁇ time) is overlapped only with the negative current time of its preceding and succeeding phases (i.e. phase A & C).
  • the positive current time is from 1 ⁇ /3 to ⁇ , and the time 1 ⁇ /3 to 2 ⁇ /3 is overlapped with the preceding phase A's positive current time (i.e. group A,B), and the time 2 ⁇ /3 to ⁇ is overlapped with the succeeding phase C's positive current time (i.e. groups B and C).
  • the negative current time is symmetric to the positive time, forming the two overlapped time sets of (-A,-B) and (-B,-C). Since the magnetic field vector sum of the embodiment uses the sum of only two phases of magnetic field vectors, the mutual cancellation of multiphase vectors resulted from the invalid anti-rotation magnetic fields (vectors) is eliminated or reduced. So, in a multiphase (three phases or more) system, the current used to generate the invalid magnetic fields is therefore saved. Both the copper loss and iron loss are also reduced and the goal of saving power is achieved.
  • FIGS. 4B to 4D show the magnetic field vector sum at three different time points of FIG. 4A .
  • Phase A current 3a generates the magnetic vector Va.
  • Phase B current 3b generates the magnetic vector Vb.
  • Va and Vb are combined to form the magnetic field vector sum Vabc.
  • FIGS. 4B to 4D show that, during the rotation of the magnetic field vector sum Vabc, the mutual vector cancellation is reduced to the lowest level, which means the invalid magnetic fields are at the lowest level, and the wasted current is saved.
  • the sine wave's peak value is 1, the strength of the magnetic field sum of the three-phase sine-wave currents equals to 1.5L (L is the coil's inductance). So, for the embodiment, if the curved-triangle current's peak value is set to 1.5 (as shown in FIG. 3B ), we can generate the same magnetic field sum strength (i.e. 1.5L) as the conventional three-phase sine waves of an amplitude 1.0 in FIG. 1B .
  • the current consumption of the curved-triangle waveform is equal to its area.
  • two curved-triangle phase currents are used to replace the conventional sine-wave currents to drive a motor with a smaller stator pole pitch. It is shown that, compared to two-phase sine-wave currents with 90-degree stator pole pitch, lesser current is required to generate the same magnetic strength whereas the same steady and substantially no-ripple rotation is still kept.
  • the two-phase motors now can have a stator pole pitch of less than 90 degrees (i.e. it's no longer limited to 90 degrees), and the number of stator poles can be greater than 4. And, still the magnetic field sum can be kept at the same strength and rotate steadily and substantially without ripples.
  • Table 2 shows a current table of an embodiment of the disclosure that is used to drive a three-phase motor with a stator pole pitch of 30 degrees or with twelve stator poles.
  • FIG. 5 shows the curved-triangle waveforms according to the data of Table 2.
  • Table 2 is similar to Table 1, but has a different stator pole pitch of 30 degrees, which means two different phases of curved-triangle currents generate two magnetic field vectors with an included angle of 30 degrees. Comparing the average of the curved-triangle currents with the average of sine-wave currents, the required drive currents are lower. And, after comparing the data in Table 2 and Table 1, it is shown that smaller stator pole pitch leads to a smaller current. This result can be expected and seen from the equation (3) and (4), and reduced copper loss and iron loss and motor heat could also be expected.
  • FIG. 6 shows the four-phase curved-triangle current waveform of an embodiment according to the disclosure which is used to drive a four-phase AC motor with a stator pole pitch of 30 degrees and twelve stator poles.
  • the four-phase curved-triangle currents must have a peak of 2.0 to generate the same magnetic field strength of three-phase sine-wave currents with a peak of 1.0. Comparing with the average three-phase sine-wave currents, the required drive currents are lower.
  • FIG. 7 shows the curved-triangle waveform of an embodiment of the disclosure which is used to drive a two-phase AC motor with a stator pole pitch of 30 degrees and twelve stator poles.
  • the power consumption of a conventional two-phase sine-wave four-stator-pole (or 90-degree-stator-pole-pitch) motor is 1.5 times of a sine-wave three-phase six-stator-pole motor.
  • the method of the embodiment not only can make a more-than-four-stator-pole two-phase motor to have a rippleless rotation, but also can make the two-phase motor to use lesser power than a three-phase sine-wave motor while generating the same torque output.
  • a zero current time is inserted to each half cycle of each phase current so that at any time no more than two phases currents are outputting to drive the motor. So, in a driving cycle of each phase current, there are one curved-triangle current time and one zero current time in each positive-half or negative-half cycle time. Or, in each half cycle there is a zero current time. For example, if the multiphase power source has N phases, in each half cycle time of each phase current, the curved-triangle current occupies 2/N of the half cycle time, and the rest (N-2)/N of the half cycle time is zero current.
  • the other phase currents are substantially zero.
  • phase difference between the phase currents is 180/N.
  • phase currents when N phases of currents are used to drive the motor, two different phases of currents are sequentially grouped into a series of phase pairs and driving the motor pair by pair.
  • Each phase current's positive current time is overlapped with another phase current's positive current time
  • the first phase's (Phase A) positive-rising current time is overlapped with the last phase's (Phase N) negative current time.
  • the last phase's (Phase N) positive-falling current time is overlapped with the first phase's (Phase A) negative current time.
  • N-2 phases' Phase B to Phase N-1 positive current time is only overlapped with its preceding and succeeding phases' positive current time.
  • N-2 phases' (Phase B to Phase N-1) negative current time is only overlapped with its preceding and succeeding phases' negative current time.
  • the phase A, B and C's positive current time is two by two overlapped.
  • Phase A's positive-rising current time is overlapped with phase C's negative current time
  • phase C's positive-falling current time is overlapped with phase A's negative current time.
  • phase's i.e. phase B's
  • phase B's positive current time is only overlapped with its preceding phase A's and its succeeding phase C's positive current time
  • phase B's negative current time is only overlapped with its preceding phase A's and its succeeding phase C's negative current time.
  • FIG. 8 shows a circuit diagram for a three-phase curved-triangle current driver of an embodiment of the invention. Comparing to the conventional driver circuits as shown in FIG. 1A , in order to generate the curved-triangle current of the invention, two driving signals PWM7 and PWM8 and two transistor switches M7 and M8 are added to the circuits depicted in FIG. 8 , and the transistor switches' outputs are connected to the center of the Y-connected stator coils of the motor 91. So, the circuits can now provide two phases of positive current and/or negative current at the same time, and meanwhile force the third phase to output zero current.
  • three back-EMF detectors Sa, Sb and Sc are added to the circuits depicted in FIG. 8 .
  • the three back-EMF detectors are connected to phase A, B and C's coils, and output the detected back-EMF signals S1, S2 and S3 respectively to the control circuit (i.e. controller 93 in FIG. 8 ).
  • the detectors Sa, Sb and Sc can detect the back-EMF from the coils during the zero current time of the stator coils, so the controller 93 can estimate the rotor's position with the detected back-EMF, and to use the position data as a parameter to modify the driving currents.
  • the controller 93 performs real-time calculation or uses look-up tables or other software or hardware techniques with the equations (3) and (4) of the invention to get the current values, and drives the motor based on the current values.
  • Table 3 a reference current value table for a two-phase twelve-stator-pole motor of an embodiment of the invention is listed. The reference values of each phase are shown and are calculated according to the equations (3) and (4).
  • the values in the row 3 "Phase A” and in the row 4 "Phase B” are the reference current values for the A and B phases, respectively.
  • phase A current values along the time-axis from phase angle of zero to 180 degrees are listed. Only the current values of the positive-half cycle are listed, and the negative-half cycle (180 ⁇ 360 degrees) is omitted because it is symmetric to the positive-half cycle.
  • the values in row 1 of Table 3 are the phase angles of the driving current, i.e. the time-axis.
  • the values in row 2 are the angles Alpha ( ⁇ ) which varies from zero to 30 degrees repeatedly. ⁇ represents the included angle between the direction of the magnetic field sum and the salient direction of the stator pole. When ⁇ changes from zero to 30 degrees, it represents the changing of the included angles during the rotation of the direction of the magnetic field sum from one stator tooth magnetic pole center to the next.
  • the values in row 3 and 4 are the reference values of driving current phase A and B respectively calculated from the equations (3) and (4).
  • the values in row 5 are the strength of the magnetic field sum calculated from the three phase currents. The strength is kept at a value of 0.5 steadily as expected.
  • the values in row 6 are the calculated rotation angles of the magnetic field sum. In a half-cycle time, the rotation angle changes and rotates steadily from -30 degrees to 30 degrees (i.e. rotates 120 degrees in one cycle). It means the magnetic field vector sum rotates and its rotation angle is increasing or decreasing with a change rate proportional to the change rate of the phase angle of the power source. In other words, the strength of the magnetic field sum substantially has no ripples (i.e. with the theoretical ideal values it can be completely ripple free), and its change rate of rotation angle or movement is proportional to the change rate of the phase angle of the two-phase currents.
  • the magnetic field vector sum of the invention comes from the sum of only two phases of magnetic field vectors, the mutual cancellation of conventional three-phase vectors resulted from the invalid anti-rotation magnetic fields (vectors) is eliminated or reduced. So, in a multiphase (three phases or more) system, the current used to generate the invalid magnetic fields is saved, and therefore the power is saved.
  • the two-phase currents are used to drive an AC motor with twelve stator teeth.
  • FIG. 9 is the current waveform drawn from the current values in Table 3 according to the embodiment of the disclosure, including the phase A current 9a, phase B current 9b, the strength 9d of the magnetic field sum, and the rotation angle 9e of the magnetic field sum. Please compare the two-phase curved-triangle waveform in FIG. 9 and the three-phase sine-wave in FIG. 1B . It is supposed that they are used to drive an AC motor with twelve stator teeth.
  • the strength of the magnetic field sum of the three-phase sine-wave currents from the six stator coils is equal to 1.5L ( FIG. 11 , L is the coil's inductance).
  • the two-phase curved-triangle current's peak value is 0.5, and the 2-phase 6 stator coils can generate 3 rotating magnetic fields.
  • the input power of the three-phase sine-wave system is proportional to the sum of the square of the sine-wave currents in the six stator coils (sine-wave 0.5*0.5*6).
  • the input power of the two-phase curved-triangle system is proportional to the sum of the square of the curved-triangle currents in the six stator coils (curved-triangle 0.5*0.5*6). So, by comparing the square of the curved-triangle current values in Table 3 with the square of the sine-wave current (both have the same peak current of 0.5), the estimated power saving rate of the embodiment would be 30%.
  • the method of the present embodiment not only can make a more-than-four-stator-pole two-phase AC motor to generate ripple free rotation, it also can improve a two-phase AC motor to have a higher efficiency than a three-phase AC motor while the torque output are kept the same.
  • the method of the embodiment of the disclosure uses two-phase currents to drive the AC motor, and the phase difference between the two curved-triangle currents is 90 degrees.
  • each rotating magnetic field generated from the rotation of the rotor drives at most two sets of coils, and induces two phases of curved-triangle currents with 90 degrees of phase difference in the coils.
  • R is the rotating magnetic field.
  • the induced currents of phase A and B are generated in the two sets of coils.
  • the reference values A and B of the induction currents in the two coils can be calculated with the equations (3) and (4). Therefore, with the same principles of the disclosure, the AC motor or the AC motor generator can be used to generate power more efficiently.
  • the driving method of the disclosure can reduce or eliminate the invalid magnetic flux generated in the conventional multiphase motors. It is low cost, easy to implement, and saves power.
  • the method of the disclosure is used in two-phase AC motors in which the stator pole number is no longer limited to four or the stator pole pitch is smaller than 90 degrees, no magnetic field ripples are generated, and lesser power is required than a conventional three-phase sine-wave driven motor. So, the method of the present disclosure can expand the applications of two-phase motors. It is also possible to replace the three-phase motors in a cost effective way.
  • the method of the disclosure is used in an AC motor generator to generate power, the magnetic flux can be used more efficiently and the generator efficiency is improved.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Ac Motors In General (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)
  • Synchronous Machinery (AREA)
EP17156473.5A 2016-02-17 2017-02-16 Verfahren zur ansteuerung eines wechselstrommotors durch zweiphasenstrom Active EP3208934B1 (de)

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CN110880820A (zh) * 2019-11-29 2020-03-13 西安交通大学 一种两相直流偏置电流游标磁阻电机
TWI806784B (zh) * 2022-09-30 2023-06-21 台達電子工業股份有限公司 用於驅動馬達的電源轉換電路及其控制方法

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CN107093972B (zh) 2021-07-09
US20170237378A1 (en) 2017-08-17
TWI701901B (zh) 2020-08-11
US9973130B2 (en) 2018-05-15
TW201731206A (zh) 2017-09-01
JP2017200426A (ja) 2017-11-02
CN107093972A (zh) 2017-08-25
EP3208934B1 (de) 2021-06-02

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