EP2171793B1 - Schleifenrichtkoppler - Google Patents

Schleifenrichtkoppler Download PDF

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Publication number
EP2171793B1
EP2171793B1 EP08784853A EP08784853A EP2171793B1 EP 2171793 B1 EP2171793 B1 EP 2171793B1 EP 08784853 A EP08784853 A EP 08784853A EP 08784853 A EP08784853 A EP 08784853A EP 2171793 B1 EP2171793 B1 EP 2171793B1
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Prior art keywords
network
coupling
signal
input
factor
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EP08784853A
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German (de)
English (en)
French (fr)
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EP2171793A1 (de
Inventor
Thomas Zelder
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Rosenberger Hochfrequenztechnik GmbH and Co KG
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Rosenberger Hochfrequenztechnik GmbH and Co KG
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/12—Coupling devices having more than two ports
    • H01P5/16—Conjugate devices, i.e. devices having at least one port decoupled from one other port
    • H01P5/18—Conjugate devices, i.e. devices having at least one port decoupled from one other port consisting of two coupled guides, e.g. directional couplers

Definitions

  • the present invention relates to a Schleifenrichtkoppler with a waveguide, in particular a waveguide, a planar conductor or a coaxial conductor, in the form of a half loop antenna, which has a first antenna arm and a second antenna arm, for contactless decoupling of a running on a waveguide signal a and a on This waveguide returning signal b, according to the preamble of claim 1.
  • the directional coupler is one of the most commonly used components in high frequency and microwave circuits. It is a reciprocal four-door component in which ideally two gates are decoupled from each other when all gates are completed without reflection.
  • Tor 1 is the input gate to which a signal is fed. All gates are completed without reflection.
  • the gate 4 is the isolation gate to which no portion of the injected power is coupled.
  • the other two goals are called Transmission Gate and Coupling Gate.
  • the directivity is the ratio of the performance of the docking gate to the performance of the isolation gate when all gates are completed without reflection.
  • the optimal directivity of a directional coupler, consisting of two coupled lines, is after KW Wagner, "Induction effect of traveling waves in neighboring lines," Elektrotechnische Zeitschrift, volume 35, pages 639-643; 677-680; 705-708, 1914 achieved when the ratio of the inductive to the capacitive coupling factor is equal to the product of the characteristic impedance of the individual lines.
  • Directional couplers are often used in measuring systems for the separate determination of the incoming and returning waves.
  • directional couplers are used as decoupled power dividers in attenuators, phase shifters, mixers and amplifiers.
  • Directional couplers are constructed, for example, of coaxial conductors, waveguides and / or planar waveguides.
  • a loop-wise coupler consists of a conductor loop which is positioned over or in a waveguide. In this case, any waveguide such as hollow lines, planar strip lines or coaxial cables can be used.
  • Schleifenrichtkopplers The application of a Schleifenrichtkopplers is varied. For example, use F. De Groote, J. Verspecht, C. Tsironis, D. Barataud and J.-P. Teyssier, "An improved coupling method for time domain load-pull measurements", European Microwave Conference, Vol. 1, p. 4ff, October 2005 and K. Yhland, J. Stenarson, "Noncontacting Measurement of Power in Microstrip Circuits" in 65th ARFTG, pp. 201-205, June 2006 a Schleifenrichtkoppler as a component in a contactless measuring system.
  • Inductive and / or capacitive coupling structures are used to determine the scattering parameters of a test object (DUT - D evice U nder T est) with a contactless, mostly vectorial measuring system.
  • a test object DUT - D evice U nder T est
  • a contactless, mostly vectorial measuring system By means of these coupling structures, the current and / or the voltage of a signal line, which is connected directly to the test object, determined.
  • the back and forth waves are measured on the signal line, then directional couplers are used as coupling structures for the separation of the two waves.
  • the accuracy of an uncalibrated and calibrated measuring system for determining the back and forth waves by means of directional couplers depends i.a. from the directivity of the coupler.
  • the directivity can be optimized by the positioning and angle of the loop relative to the signal line, as well as by changing the loop geometry.
  • a broadband optimization of the directional coupling (over several octaves) is not possible.
  • the geometry of the configuration must be re-optimized. This requires a very precise loop positioning unit, which enormously increases the complexity of the directional coupler.
  • the invention has for its object to provide a Schleifenrichtkoppler the o.g. To simplify its use in terms of its application and at the same time to improve the directivity.
  • the first antenna arm is connected to a first input of a first network and the second antenna arm to a second input of the first network, wherein the first network at the first input a first Power divider and at the second input has a second power divider, which divide the respective voltage applied to the antenna arms signal, wherein the first network a first adder, which adds the signals of the first and second power divider together and the resulting signal K c (a + b) , wherein K c is a capacitive coupling factor of the Schleifenrichtkopplers, to a first output of the first network, and a first subtractor, which subtracts the signals of the first and second power divider from each other and the resulting signal K i (ab), where K i a inductive coupling factor of the Schleifenrichtkopplers is on a second output of the first network is, has a third network with a first input, which
  • a second network having a first input connected to the first output of the first network, a second input connected to the second output of the first network, a first output, which is connected to a first input of a third Network, and a second output, which is connected to the second input of the third network, provided, wherein the second network has at least one coupling factor matching device, the magnitude and / or the phase of the signal at the first input of the second network and / or changed at the second input of the second network such that at the second adder and at the second subtracter signals with respect to magnitude and phase respectively identical coupling factor K 1 , K 2 are present for addition or subtraction.
  • a first switch and between the second output of the second Network and the second input of the third network, a second switch is arranged and configured such that these switches either the coming of the first and second output of the second network signal optionally respectively to the first and second input of the third network or bypassing the third Forward network.
  • a fifth power divider which applies the signal coming from the first output of the second network to the first input of the third network and to a third switch and between the second output of the second network and the second input of the third network
  • a sixth power divider which applies the signal coming from the second output of the second network to the second input of the third network and to a fourth switch, the switches being arranged and are formed so that they give the coming of the power dividers signal either to a receiver or a terminator.
  • VFO variable frequency oscillator
  • the receiver is connected to the control for the coupling factor matching means, the receiver being preferably arranged to control the coupling factor matching means such that the coupling factor matching means control of the coupling factor matching means supplies such parameters that the coupling factor matching device changes the magnitude and / or the phase of the signal at the first input of the second network and / or at the second input of the second network such that an identical coupling factor K is present at both outputs of the second network.
  • the receiver is arranged to control the controller for the coupling factor matcher such that the controller for the coupling factor matcher supplies the coupling factor matcher with such parameters that the coupling factor matcher determines the magnitude and / or the phase of the signal at first input of the second network and / or the second input of the second network changed such that at inputs of second adder a first coupling factor K 1 and at the inputs of the second subtractor, a second coupling factor K 2 is present.
  • the first preferred embodiment of a Schleifenrichtkopplers invention for coupling out on a waveguide 11 between a signal source 13 and a test object (DUT) 15 running wave a and a returning wave b comprises a half loop antenna 10 with a first antenna arm 12 and a second Antenna arm 14.
  • Reference numeral 17 denotes a reference plane.
  • the two antenna arms 12, 14 are connected to a configurable network 16.
  • the configurable network 16 is a first network 18 having a first input 20, a second input 22, a first output 24 and a second output 26, a second network 28 having a first input 30, a second input 32, a first output 34 and a second output 36 and a third network 38 having a first input 40, a second input 42, a first output 44 and a second output 46.
  • the second network 28 forms signal paths 128 and 130 between the outputs 24, 26 of the first network 18 and the inputs 40, 42 of the third network.
  • the first antenna arm 12 is connected via a first mixer 48 and a first filter 50 to the first input 20 of the first network 18.
  • the second antenna arm 14 is connected via a second mixer 52 and a second filter 54 to the second input 22 of the first network 18.
  • the first network 18 has a first power divider 56 at the first input 20 and a second power divider 58 at the second input 22. Furthermore, in the first network 18, a first adder 60, which adds the signal from the first power divider 56 and second power divider 58 together and to the first output 24 of the first network 18, and a first subtractor 62, which receives the signal from the first power divider 56 and second power divider subtracted from each other 58 and to the second output 26 of the first network 18 are arranged.
  • the signal K i * (ab) is multiplied by a complex factor F by a coupling factor equalizer 64, which determines the amount and the phase of this signal K i * (ab) changes.
  • the resulting signal K i * F * (ab) is given by the coupling-factor matching means 64 to the second output 36 of the second network 28 .
  • the signal K c * (a + b) is looped through by the second network 28 to the second output 34 of the second network 28. It should be emphasized that this approximation of magnitude and phase of the two coupling factors K i and K c is merely exemplary.
  • the third network 38 has a third power divider 66 at the first input 40 and a fourth power divider 68 at the second input 42. Furthermore, in the third network 38, a second adder 70, which adds the signal from the third power divider 66 and fourth power divider 68 together and to the first output 44 of the third network 38, and a second subtractor 72, which receives the signal from the third power divider 66 and fourth power divider 68 subtracted from each other and to the second output 46 of the third network 38 are arranged.
  • the signal 2K 1 * a is obtained at the first output 44 of the third network 38, and the signal 2K 2 * b at the second output 46 of the third network 38, where K 1 is the coupling factor at the two inputs of the second adder 70 and K 2 is the coupling factor at the two inputs of the second subtractor 72.
  • the resulting coupling factors for the outgoing wave a and the returning wave b are identical, namely K.
  • the third network 38 has a first capacitive signal path 120 extending from the third power divider 66 to the second adder 70, one from the third power divider 66 to the second subtractor 72 extending first inductive signal path 122, one of the fourth power divider 68 to the second adder 70 extending second capacitive signal path 124 and a second inductive signal path 126 extending from the fourth power conductor 68 to the second subtracter 72.
  • the mixers 48, 52 and filters 50, 54 serve to convert the signals coming from the antenna arms 12 and 14 to a predetermined intermediate frequency, so that the subsequent components need only be optimized to this predetermined intermediate frequency.
  • a VFO (variable frequency oscillator) or a phase locked loop 74 is provided with a local oscillator or a reference oscillator, which gives a corresponding reference signal or mixing signal 76 to the mixers 48 and 52, of the mixers 48 and 52 with the respective output signal of the two Antenna arms 12, 14 is mixed.
  • the phase-locked loop 74 is further connected to a controller 78 for the coupling factor equalizer 64 and passes this the current frequency 80 of the reference signal 76.
  • the controller 78 selects a frequency-individual complex factor F or complex factors F 1 , F 2 and transfers this or these to the second network 28 or to the coupling factor matching device 64 in the second network 28.
  • an intermediate frequency signal 110 is transferred to the phase locked loop 74. This intermediate frequency signal 110 is taken either before the first input 20 or before the second input 22 of the network 18.
  • the directivity of the directional coupler according to the invention without position or geometry change can be optimized for each frequency.
  • the loop antenna 10 together with the network 16 it is possible to realize an optimized loop-directional coupler with the additional use of any signal conductor, such as a coaxial line or microstrip line, without changing the loop geometry and arrangement relative to the signal conductor 11.
  • the configurable network 16 consists of the three subnetworks 18, 28 and 38, wherein the first network 18 and the third network 38 may be identical.
  • the integration of the mixers 48, 52 and filters 50, 54 into the network 16 is not mandatory, however, this creates some advantages.
  • the half conductor loop 10 inductively and capacitively decouples a portion of the energy present, for example, in the near field of the signal conductor 11.
  • a small compared to the wavelength of the electrical signal conductor loop 10 is added in the first antenna arm 12 of the inductively and capacitively induced current, wherein in the other second antenna arm 14 subtract the currents due to a phase difference of 180 °.
  • the first network 18 comprises the two power splitters 56, 58, which are, for example, two 3 dB couplers, and one add and subtract network 62 each.
  • the addition network 60 is, for example, a "twisted" 3 dB coupler (combiner) and as a subtraction network 62, for example, a balun (balun) is provided.
  • the change of magnitude and phase of the signal is effected, for example, by means of an amplifier or an attenuator in combination with a phase shifter. It is preferred to use electronically controllable components, so that the complex-valued factor F by means of electrical control signals quickly and easily a change in the measurement configuration can be adjusted.
  • the placement of the multiplication unit or the coupling factor matching device 64 is arbitrary. As in Fig. 1 As shown, it is possible to perform the multiplication only in one path, it being unimportant which of the two available paths is used.
  • controllable components can also be provided in both paths, or in one path only the phase and in the other path only the amount is controlled.
  • the coupling loss can be adjusted with the help of the second network 28 without having to change the tube attenuation or raw coupling loss of the simple conductor loop 10.
  • the signals are recombined by the third network 38 so that only one outgoing wave a and one output 44 depending on the coupling factor K are used returning wave b yields. To ensure this, the individual paths of the network are formed absolutely identical.
  • the necessary components such as the subtracters 62, 72 (balun) and the power dividers 56, 58, 66, 68, only function with frequency limitation. This contradicts a broadband use of the system.
  • the system is optionally extended by one or more heterodyne mixers including the mixers 48, 52 and the filters 50 54.
  • the signals of the loop 10 are mixed with the reference signal 76 to a low, fixed (predetermined) intermediate frequency.
  • a fixed intermediate frequency it is possible to integrate the configurable network 16 as a circuit, since the requirements for the individual components with respect to the frequency bandwidth fall significantly.
  • the system can be optimized for any signal bandwidths.
  • the necessary reference signal 76 is generated, for example, by means of a control loop and a local and reference oscillator 74.
  • the network 16 represents a hardware calibration of the loop 10 with the aim of increasing the directivity.
  • the configuration of the network 16 is equivalent to the control of the second network 28.
  • the aim is first to determine the complex factor F and then to control the components of the second network 28 so that they correspond to the factor F.
  • a reflection-free, ideally a reflection-free termination is connected to the reference plane 17 as a DUT (test object).
  • the traveling wave a then exists on the signal line 11.
  • the traveling wave a can be multiplied by the capacitive coupling factor K c * a and multiplied by the inductive coupling factor K i * a.
  • Um To measure the output signals of the second network 28, the connection between the second network 28 and the third network 38 must be disconnected so that the second network 28 can be connected directly to vectorial receivers. Since there is no anechoic closure in reality, a low-reflection finish must be used to set the F factor. The lower the reflectivity, the higher directivity values can be achieved with the overall arrangement. In addition, the magnitude of the directivity depends on whether the transfer functions of the paths of the third network 38 are identical. The greater the differences in the transfer functions, the lower the directivity values can be achieved.
  • second preferred embodiment of the Schleifenrichtkopplers invention functionally identical parts are designated by the same reference numerals, as in Fig. 1 so that their explanation to the above description of Fig. 1 is referenced.
  • two, for example, electronic switches 84 and 86 are arranged between the second network 28 and the third network 38 and two additional switches 88, 90 are provided above the third network 38, which are each actuated by a controller 92, 94. These serve to simplify the calibration described above with respect to the reference plane 17 shown.
  • the control 78 of the second network 28 and the switches 84, 86, 88, 90 are performed manually or completely automatically. Instead of the switches 84, 86, 88, 90, two identical couplers can also be used.
  • a fifth power divider 96 is arranged, which outputs the signal to the first input 40 of the third network 38 and to a first switch 98.
  • a sixth power divider 100 is arranged, which outputs the signal to the second input 42 of the third network 38 and to a second switch 102.
  • the two switches 98, 102 pass the signal either to low reflection terminations 104, 106 or to a receiver 108.
  • the receiver 108 controls the controller 78 in such a way that the latter transmits corresponding parameters for the change of magnitude and phase to the second network 28, so that by means of the coupling factor matching device 64 the coupling factors abut each other in the manner described above be aligned.
  • the coupling factor matching devices 112 and 114 which are connected directly in front of the adder 70 and subtractor 72, optionally take over the equalization of the coupling factors K i and K c that differ in magnitude and phase in addition to the compensation of attenuation and phase shift in the four paths of the third network then to the coupling factor matching device 64 according to the first three embodiments Fig. 1 to 3 can be dispensed with, as in Fig. 4 shown.
  • the coupling factor equalizer 112 multiplies in an inductive path of the Third network 38, the coupling factor K i * D 2 (coupling factor with transfer function) with a factor F 4 and the coupling factor match device 114 multiplied in the other inductive path of the third network 38, the coupling factor K i * D 4 (coupling factor with transfer function) with a Factor F 4 .
  • the transfer functions (attenuation and phase shift) D 1 , D 2 , D 3 and D 4 of the individual signal paths of the third network 38 and the paths between the outputs 34, 36 of the second network 28 and the adder 70 and the subtractor 72 or between the outputs 24, 26 of the first network 18 and the adder 70 and the subtracter 72 are determined by measurement, for example. If they are known, the coupling factors are adjusted by means of the second network 28 in such a way that the complex amplitudes of the signals at the inputs of the adder 70 and subtractor 72 are identical, and the various configurations of the second network 28 described above are still possible. In the first three embodiments of Fig.
  • the known transmission factors D 1 , D 2 and D 3 , D 4 are loaded from the memory and multiplied to the received signals (K c * F 1 * D 1 , K i * F 2 * D 2 or K c * F 1 * D 3, K i * F 2 * D 4).
  • the two coupling factor matching devices 112, 114 are provided in the third network 38, as in FIG Fig. 4 shown. These coupling factor matching devices 112, 114 increase the directivity under consideration of the path losses D 1 to D 4 . Up to four coupling factor matching devices may be provided for all four paths of the third network 38. Four configurations come into question, either two coupling factor matchers 112, 114 are used in the two capacitive or inductive paths, or four coupling factor matchers, one in each path of the third network 38, or three coupling factor matchers are used ,
  • the Fig. 4 shows a variant with two coupling factor matching devices 112, 114 in the inductive (K i -) path.
  • the coupling factor equalizers 112, 114 multiply the complex factors F 3 , F 4 , F 5 , and / or F 6 to the signal amplitudes.
  • the four signals before the adder 70 and the subtractor 72 are coupled to a vectorial receiver, for example by means of switches or power dividers / couplers (similar to US Pat Fig. 2 and 3 ) using a low-reflection DUT, so controlled / calibrated that the output amplitudes are identical.
  • Fig. 4 can also be done in a similar way as in Fig. 2 and Fig. 3 shown to be extended. Also for the system in Fig. 4 can for the Calibration or determination of the factors F 1 to F 4 between the coupling factor matching devices 112, 114 and the second adder 70 and the second subtracter 72 switch and / or power divider may be provided, which are each connected at one output to a (vectorial) receiver are.
  • the network 16 it is also possible for the network 16 to have both two, three or four coupling factor matching devices 112, 114 in the third network 38 as well as one or two coupling factor matching devices 64 in the second network 28.

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EP08784853A 2007-07-24 2008-07-17 Schleifenrichtkoppler Active EP2171793B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE202007010239U DE202007010239U1 (de) 2007-07-24 2007-07-24 Schleifenrichtkoppler
PCT/EP2008/005873 WO2009012937A1 (de) 2007-07-24 2008-07-17 Schleifenrichtkoppler

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EP2171793A1 EP2171793A1 (de) 2010-04-07
EP2171793B1 true EP2171793B1 (de) 2010-12-01

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US (1) US8121574B2 (xx)
EP (1) EP2171793B1 (xx)
JP (1) JP4914936B2 (xx)
CN (1) CN101809808B (xx)
AT (1) ATE490570T1 (xx)
CA (1) CA2695462C (xx)
DE (2) DE202007010239U1 (xx)
HK (1) HK1147601A1 (xx)
TW (1) TWM349635U (xx)
WO (1) WO2009012937A1 (xx)

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DE202007010784U1 (de) * 2007-08-03 2007-10-04 Rosenberger Hochfrequenztechnik Gmbh & Co. Kg Kontaktloses Messsystem
EP2360776B1 (en) * 2010-02-16 2017-07-12 Whirlpool Corporation Microwave directional coupler
CN102505729A (zh) * 2011-12-19 2012-06-20 王景满 地面街道延伸雨水收集系统
CN102420351B (zh) * 2012-01-04 2014-06-11 镇江中安通信科技有限公司 功分移相器
US9312592B2 (en) 2013-03-15 2016-04-12 Keysight Technologies, Inc. Adjustable directional coupler circuit
US11586956B2 (en) 2013-05-28 2023-02-21 Keysight Technologies, Inc. Searching apparatus utilizing sub-word finite state machines
US9608305B2 (en) * 2014-01-14 2017-03-28 Infineon Technologies Ag System and method for a directional coupler with a combining circuit
CN106100595B (zh) * 2015-11-20 2019-04-26 厦门宇臻集成电路科技有限公司 一种带宽带耦合器的功率放大器
CN106505288B (zh) * 2016-12-05 2022-02-11 安徽四创电子股份有限公司 一种三十二路波导e面功分器
KR102139769B1 (ko) * 2018-10-16 2020-08-11 삼성전기주식회사 위상보상 기능을 갖는 방향성 커플러 회로 및 파워 증폭 장치

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US5926076A (en) * 1997-08-07 1999-07-20 Werlatone, Inc. Adjustable broadband directional coupler
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CN101809808A (zh) 2010-08-18
WO2009012937A1 (de) 2009-01-29
JP4914936B2 (ja) 2012-04-11
ATE490570T1 (de) 2010-12-15
US8121574B2 (en) 2012-02-21
DE502008001958D1 (de) 2011-01-13
CN101809808B (zh) 2013-08-21
HK1147601A1 (en) 2011-08-12
DE202007010239U1 (de) 2007-09-20
CA2695462C (en) 2015-11-24
JP2010534436A (ja) 2010-11-04
CA2695462A1 (en) 2009-01-29
US20100271150A1 (en) 2010-10-28
EP2171793A1 (de) 2010-04-07
TWM349635U (en) 2009-01-21

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